CN102957319B - Power inverter pulse-width modulation control circuit and method - Google Patents
Power inverter pulse-width modulation control circuit and method Download PDFInfo
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- CN102957319B CN102957319B CN201110250707.4A CN201110250707A CN102957319B CN 102957319 B CN102957319 B CN 102957319B CN 201110250707 A CN201110250707 A CN 201110250707A CN 102957319 B CN102957319 B CN 102957319B
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Abstract
The invention discloses a power inverter pulse-width modulation control circuit and a power inverter pulse-width modulation control method. The power inverter pulse-width modulation control circuit comprises a virtual current ripple pulse width modulation circuit, a phase synthesis unit and a dual-track reference voltage level generating unit, wherein the virtual current ripple pulse width modulation circuit is provided with an integral and direct current bias eliminating unit and is used for inputting a phase node voltage signal and an output voltage reflecting signal and generating a virtual current ripple parameter signal positioned in a direct current reference voltage level; the phase synthesis unit is used for synthesizing the virtual current ripple parameter signal and an output voltage signal slope vector into a pulse width modulation parameter signal; and the dual-track reference voltage level generating unit is used for generating an upper direct current reference voltage level and a lower direct current reference voltage level and comparing the pulse width modulation parameter signal with the upper direct current reference voltage level and the lower direct current reference voltage level to generate a pulse width modulation signal to be input to a driver. According to the invention, the manufacturing cost of a power inverter can be reduced, and the volume of a power supplier can be shortened.
Description
Technical field
The present invention relates to a kind of power supply changeover device pulse width modulating control circuit and control method thereof, espespecially a kind ofly exempt from pulse width modulating control circuit and the control method thereof that compensation adjustment is stablized in loop circuit.
Background technology
Power supply changeover device, for general electronic equipment, occupies very important status, required voltage when its conversion electric power is to provide electronic equipment start.And for user, the vitality of electronic device works time, often becomes when buying electronic equipment, how one of major consideration, therefore allow electronic equipment can be in running order for a long time, become the main design goal of current power supply changeover device.
The design of current power supply changeover device is mainly based on exchange type power transducer (Switching Power Supplies), exchange type power transducer is by judging power output needed for load, output voltage or output current, utilize the means of pulse width modulation (PWM Pulse-width modulation), make power supply changeover device when exporting electric energy, can more precisely control to export to load electric energy and for load.Therefore more not easily produce unnecessary waste of energy when exchange type power transducer uses, and saved the loss of electric energy.
Refer to the Patent Case of U.S. Patent Bulletin US6433525, it is proposed a kind of exchange type power transducer by Intersil company, whether the polarity mainly utilizing the circuit of detecting inductive current to carry out detecting current changes, and the current status that collocation utilizes counter to carry out sensing lead starts the time of change, and select the output mode of electric energy, therefore, when this exchange type power transducer is in high current loads state, pulse-width modulation adjusting control circuit can be selected control the electric energy exported; And when low current load state, sluggishness (ripples) control circuit can be selected to control the electric energy exported; Thus reach the object of saving electric energy and exporting, to extend the time of electronic equipment continuous firing.
But, the counter of this kind of exchange type power transducer changes at the current status of detecting load, between the electric energy output mode selecting to be applicable to, have a time drop, and cause exchange type power transducer cannot the current status of accurate fit load, applicable electric energy is provided, such as: when load is transformed into low current condition by high current status, can because of time error during counter works, this AC system power supply changeover device is caused still to use sluggishness (ripples) adjusting control circuit to control the electric energy exported, cause the electric energy of output cannot coordinate needed for load, and then cause electric loss of energy.Therefore, this kind utilizes the exchange type power transducer of counter, poor for the regulating effect exporting electric energy, and can produce unnecessary electric energy loss.
Add the design of this kind of exchange type power transducer, pulse width modulating control circuit is in order to be able to stable out-put supply to load, adjustment must be compensated to the power supply of input load, and need arrange in pairs or groups sluggishness (ripples) adjusting control circuit or other circuit, cannot only use single control circuit to reach the effect of stability contorting output voltage, and cause that the design cost of this kind of exchange type power transducer is higher, volume is larger, for under the trend that present electronic product volume constantly reduces, the design of this kind of power supply changeover device is real the necessity that must improve.
Summary of the invention
One can reduce transducer outlet side inductance to object of the present invention, capacitance characteristic affects pulse-width modulation control signal providing, and can have accurately control, cost reduces effect.
The transducer that the present invention relates to comprises at least one upper axle assemble, axle assemble once, and on this, lower axle assemble is electrically connected input power, and on this, lower axle assemble connects through phase node, and phase node is subject to the driver action controlled by pulse-width modulation signal to make, lower axle assemble does switching over action, this phase node connects outputting inductance again, output capacitance, and control outputting inductance electric current to output capacitance charging generation output voltage, wherein pulse width modulating control circuit of the present invention comprises virtual current ripple PWM circuit, this virtual current ripple PWM circuit has integration and direct current (DC) bias eliminates unit, the accurate generation unit of phase measurements unit and double track reference voltage position, this integration and direct current (DC) bias eliminate the signal that unit inputs aforementioned phase node voltage signal and reaction output voltage, and produce the virtual current ripple parameter signal being positioned at DC reference voltage position standard, this phase measurements unit makes this virtual current ripple parameter signal and output voltage signal slope vector synthesize pulse-width modulation parameter signal, the accurate generation unit in this double track reference voltage position produces, lower DC reference voltage position is accurate, and this pulse-width modulation parameter signal and upper, lower DC reference voltage position standard compares generation pulse-width modulation signal input aforementioned drives.
Virtual ripple current PWM circuit of the present invention comprises an accurate unit in DC reference voltage position, an integration and direct current (DC) bias and eliminates unit, a phase measurements unit, an accurate generation unit in double track reference voltage position, a pulse-width modulation generation unit, and wherein the accurate unit in DC reference voltage position provides one with reference to direct voltage position standard, this integration and direct current (DC) bias are eliminated unit input and are connected aforementioned phase node voltage signal, and connect the accurate unit in reference voltage position, and make the square wave of phase node voltage signal eliminate to form the triangular wave being positioned at DC reference position standard through integration and direct current (DC) bias, and this triangular wave slope can reacting phase node voltage signal intensity, the integrated waveform voltage that this phase measurements unit receives integration and the output of direct current (DC) bias elimination unit superposes with converter output voltage the approximate triangle wave voltage producing and synthesize as ratio, and this voltage is as pulse-width modulation parameter signal, the input side of this accurate generation unit in double track reference voltage position connects the accurate unit in DC reference voltage position again, and export pulse-width modulation generation unit to, this accurate generation unit in double track reference voltage position is just producing the accurate voltage in corresponding reference voltage position again, negative is with on the double track of difference, lower DC reference voltage, this pulse-width modulation generation unit input side connects phase measurements unit output and the accurate generation unit output in double track reference voltage position again, and make the upper DC reference position of the accurate generation unit of pulse-width modulation parameter signal and double track reference voltage position inputted by phase measurements unit accurate, lower DC reference position standard compares, and produce pulse-width modulation signal, and this pulse-width modulation signal enter drive is to control, lower axle assemble action.
Like this, the present invention carrys out designing power supply transducer by this virtual ripple current PWM circuit, do not need accurate control outputting inductance and the component characteristic impedance of filter capacitor and the frequency response characteristic of additional line adjustment error amplifier to reach high stability and easy-to-use power converter design completely, no matter this power supply changeover device can be made to be in high load condition, or during low load condition, this virtual ripple current PWM circuit all can reach the object that stabilized power supply exports, not only be minimized the cost of manufacture of power supply changeover device, also the volume of power supply unit can be reduced, and solve the weak point of prior art.
The present invention also provides a kind of and exempts from the pulse-width modulation control method that compensation adjustment is stablized in loop circuit, comprises the following steps:
A. get the square wave voltage signal of phase node, and establish DC reference voltage position accurate, this signal produces through integration and direct current (DC) bias Processing for removing the virtual current ripple parameter signal being positioned at DC reference voltage position standard again;
B. reaction output voltage signal is superposed with virtual current ripple parameter signal the pulse-width modulation parameter signal synthesizing and have approximate triangular wave;
C. detect pulse-width modulation parameter signal and produce pulse-width modulation signal to control upper and lower axle assemble action.
Wherein the detection mode of aforementioned step c establishes the upper and lower DC reference voltage position of the accurate identical positive and negative voltage difference in corresponding DC reference voltage position accurate, and the position that the rising of this pulse-width modulation parameter signal, decline ripple lay respectively at upper and lower DC reference position calibration signal can produce pulse-width modulation signal on time.
Accompanying drawing explanation
Fig. 1 is circuit framework schematic diagram of the present invention.
Fig. 2 is virtual current ripple PWM circuit block schematic diagram of the present invention.
Fig. 3 is virtual current ripple PWM circuit of the present invention and action waveforms view.
Fig. 4 is action waveforms schematic diagram of the present invention.
Fig. 5 is that embodiments of the invention integration and direct current (DC) bias eliminate element circuit schematic diagram.
Fig. 5 A is the waveform schematic diagram of corresponding diagram 5 of the present invention.
Fig. 6 is that another embodiment of the present invention direct current (DC) bias eliminates partial circuit schematic diagram.
Fig. 6 A is the waveform schematic diagram of corresponding diagram 6 of the present invention.
Fig. 6 B is the waveform schematic diagram of corresponding diagram 6 of the present invention.
Fig. 7 is embodiments of the invention phase measurements element circuit schematic diagram.
Fig. 8 is the accurate generation unit circuit diagram in embodiments of the invention double track reference voltage position.
Fig. 9 is embodiments of the invention PWM unit circuit diagram.
Figure 10 is the heterogeneous application schematic diagram of the present invention.
In figure:
Axle assemble under the upper axle assemble Q2 of Q1
A phase node 91 driver
92 outputting inductance 93 output capacitances
94 resistance 95 resistance
1 virtual current ripple PWM circuit
The 2 accurate unit in DC reference voltage position
3 integrations and direct current (DC) bias eliminate unit
4 phase measurements unit
The 5 accurate generation units in double track reference voltage position
6 pulse-width modulation generation units
61 soft starting circuit 31 integral parts
32 direct current (DC) biases are eliminated part 33 direct current (DC) bias and are eliminated part.
Embodiment
In order to explain technical scheme of the present invention further, below by specific embodiment, the present invention will be described in detail.
Please refer to shown in Fig. 1, it is the converter circuit Organization Chart that the present invention relates to, and the transducer that the present invention relates to comprises axle assemble Q1 on, axle assemble Q2 once, and on, lower axle assemble Q1, Q2 is electrically connected input power VIN, and on this, lower axle assemble Q1, Q2 connects through phase node A, and phase node A is subject to driver 91 action to make, lower axle assemble Q1, Q2 does switching over action, and aforementioned lower axle assemble Q2 also can be diode (not indicating in figure), and this phase node A connects outputting inductance 92 again, output capacitance 93, and control outputting inductance 92 electric current to output capacitance 93 charging generation output voltage VO UT, and in the present embodiment, get divider resistance 94, the branch pressure voltage of 95 is to detect output voltage VO UT change, the present invention has a virtual current ripple PWM circuit 1 again, and this virtual current ripple PWM circuit 1 inputs aforementioned phase node A voltage signal and reaction output voltage VO UT signal, and export driver 91 to control, lower axle assemble Q1, Q2 does switch motion.
Please with reference to shown in Fig. 1 to Fig. 4, virtual current ripple PWM circuit 1 of the present invention comprises an accurate unit 2 in DC reference voltage position, one integration and direct current (DC) bias eliminate unit 3, one phase measurements unit 4, the one accurate generation unit 5 in double track reference voltage position, one pulse-width modulation generation unit 6, wherein the accurate unit in DC reference voltage position 2 provides one with reference to the accurate VREF in direct voltage position (with reference to Fig. 4), integration and direct current (DC) bias eliminate unit 3 input connection phase node A voltage VSW signal again, and connect the accurate unit 2 in DC reference voltage position, and tool integral part 31, direct current (DC) bias eliminates part 32.
As shown in Figure 3 and Figure 4, the square wave of this phase node A voltage signal is eliminated unit 3 through integration and direct current (DC) bias and is formed the triangular wave Vint being positioned at DC reference position standard, its waveform as shown in Figure 4, and this triangular wave slope can reacting phase node A voltage signal intensity, and Vint waveform shown in the present embodiment Fig. 4 is anti-phase kenel, also can be homophase kenel.
Phase measurements unit 4 receives integration and direct current (DC) bias and eliminates integrated waveform voltage that unit 3 exports and transducer and feedback and detect output voltage VFB and superpose as ratio and synthesize triangle wave voltage, its waveform is as the VEA in Fig. 4, and this VEA voltage is as pulse-width modulation parameter signal, and in figure, VEA is the corresponding VSW phase wiggles of the anti-phase rear formation of Vint.
Double track reference voltage position accurate generation unit 5 input side connects the accurate unit 2 in DC reference voltage position, and exporting pulse-width modulation generation unit 6 to, this double track reference voltage position accurate generation unit 6 produces double track upper and lower DC reference position accurate VREF+, the VREF-as the positive and negative identical difference of the corresponding reference voltage position accurate VREF voltage of Fig. 4 again.
Pulse-width modulation generation unit 6 input side connects phase measurements unit 4 output and double track reference voltage position accurate generation unit 5 output, and the upper accurate VREF+ in DC reference position, the lower accurate VREF-in DC reference position that the pulse-width modulation parameter signal VEA inputted by phase measurements unit 4 and the accurate generation unit in double track reference voltage position 5 input compare, and produce pulse-width modulation signal, and this pulse-width modulation signal enter drive 91 is to control upper and lower axle assemble Q1, Q2 action.
Refer to Fig. 4, transducer reset voltage of the present invention is VFB, and this VFB voltage when the T1 time reduces on axle assemble Q1 conducting, and the voltage of VSW raises, and make, lower axle assemble Q1, the VSW voltage of Q2 phase node A is VIN voltage, T2 time output voltage VO UT raises axle assemble Q2 conducting at present again, and namely VSW voltage reduce, and phase node A voltage is earth potential, and because the internal resistance (not indicating in figure) of output capacitance 93 characteristic is by outputting inductance 92 current charges, the ripple of this back coupling VFB is to should the different peak value of output capacitance 93 characteristic tool, this Vint is that integration and direct current (DC) bias eliminate unit 3 output voltage again, and may correspond to the triangle wave voltage that VSW voltage produces tool reference voltage VREF position standard, and the triangle wave voltage of the present embodiment is the anti-phase of VSW voltage, also can be homophase design, VEA is phase measurements unit 4 input converter reset voltage VFB and Vint voltage superposition and reverse pulse-width modulation parameter voltages again, and because of this VEA be by anti-phase again for aforementioned Vint waveform, thus corresponding VSW arc in phase waveform can be produced, this VREF+ again, VREF-is for being just positioned at reference voltage VREF, the accurate voltage in negative DC reference position, and VEA voltage waveform slope of the present invention more can react the change in voltage of VFB, and approximate triangular wave can be produced, can make during the C position that the B position thus joined when VEA voltage drop to the T1 time and VREF-or VEA voltage rise to T2 time and VREF+ join PWM unit produce pulse-width modulation signal with control and drive system 91 and on, lower axle assemble Q1, Q2 action, and make the present invention accurately can react the change of output pressure to promote output voltage stability.
The integration that the present invention relates to and direct current (DC) bias eliminate unit 3, phase measurements unit 4, the accurate generation unit 5 in double track reference voltage position, pulse-width modulation generation unit 6 can be variously reaches aforementioned Functional Design, as shown in Figures 1 to 5, the integration that the present invention relates to and direct current (DC) bias are eliminated unit 3 and are had integral part 31 and direct current (DC) bias elimination part 32, and integral part 31 tool first operational amplifier OP1, and its inverting input connects the first resistance R1 is electrically connected with phase node a-signal SW, inverting input connects the second resistance R2 and is connected with the output bias that direct current (DC) bias eliminates part 32 again, again the first operational amplifier OP1 output be connected the first electric capacity C1 between inverting input, and integration time constant is by R1, C1 determines, and its in-phase input end connects DC reference voltage position accurate unit 2 output contact REF, and the phase node A voltage VSW integration of square wave can be formed triangular signal, bias produces voltage adjustable and exports direct current position standard again, direct current (DC) bias eliminates part 32 tool integrating circuit again, error amplifying circuit, and this integrating circuit input connects the output of integral part 31, error amplifying circuit connects output and the DC reference voltage position accurate unit output contact REF of integrating circuit again, the duty cycle square wave of integral part 31 corresponding phase node a-signal VSW is made to form the accurate triangular wave in different direct current positions (consulting Fig. 3), and corresponding direct current position quasi wave shape can be formed through integrating circuit, and by error amplifying circuit, this direct current position quasi wave shape is compared with the accurate VREF in DC reference voltage position of the accurate unit in DC reference voltage position 2 again, and its DC error amount is through amplifying input integral part 31 again, make integral part 31 export the accurate triangle wave voltage in different direct current positions and can be adjusted to the triangular wave Vint being positioned at the accurate VREF in DC reference voltage position, and this direct current (DC) bias elimination part 32 has the second operational amplifier OP2, 3rd operational amplifier OP3, 3rd resistance R3, 4th resistance R4, 5th resistance R5, 6th resistance R6, second electric capacity C2, and the inverting input of this second operational amplifier OP2 connection the 3rd resistance R3 is connected with the output of the first operational amplifier OP1, and the 4th resistance R4 in parallel and the second electric capacity C2 between its inverting input with output, its in-phase input end connects the output contact REF of the accurate unit 2 in DC reference voltage position again, and make the second operational amplifier OP2 form integrating circuit, inverting input connection the 5th resistance R5 of the 3rd operational amplifier OP3 is connected with the output of the second operational amplifier OP2 again, and between its inverting input with output, being connected the 6th resistance R6, its in-phase input end connects the output contact REF of the accurate unit 2 in DC reference voltage position again.
See also Fig. 5 and Fig. 5 A, when Vint of the present invention exports without DC error, Vint exports VCR (in the output capacitance 93 resistance voltage) triangular wave after for VSW integration and adds that VREF position is accurate, VCR can be eliminated via the anti-phase integration of the second operational amplifier OP2 when the triangular signal making integral part 31 input the second operational amplifier OP2 when aforementioned circuit again has a DC error form corresponding DC waveform signal Vdet and export, again this second operational amplifier OP2 export DC waveform voltage input the 3rd operational amplifier OP3 and with reference level voltage compare, and after error is amplified, become the first operational amplifier OP1 inverting input of Vbias voltage feed-in integral part 31 again, thus the VCR triangular wave after making integration and direct current (DC) bias elimination unit 3 export VSW integration adds that the position standard of VREF forms the virtual ripple current triangular signal Vint of corresponding DC reference voltage position standard.
Refer to Fig. 1 to Fig. 6, same Fig. 5 of integral part 31 of another embodiment of the present invention, and direct current (DC) bias eliminates part 33 by comparison circuit, anti-phase integrator forms, and the comparison circuit of the present embodiment has four-operational amplifier OP4, and its inverting input connects the output of integral part 31, its in-phase input end connects DC reference voltage position accurate unit 2 output contact REF again, integrating circuit has the 7th resistance R7 again, 3rd electric capacity C3, large device OP5 is imitated in 5th computing, and the inverting input of the 5th operational amplifier OP5 connects the 7th resistance R7 exports with the four-operational amplifier OP4 of comparison circuit and be connected, this inverting input connection the 3rd electric capacity C3 is connected with the output of the 5th operational amplifier OP5 again, the in-phase input end of the 5th operational amplifier OP5 connects DC reference voltage position accurate unit 2 output contact REF again, make when Vint exports without DC error, Vint exports the VCR triangular wave after for VSW integration and adds that the position of VREF is accurate, and for example Fig. 6, shown in Fig. 6 A and Fig. 6 B, the integrated waveform that integral part 31 receives when Vint output has DC error is accurate for the accurate VREF in DC reference position with DC reference voltage position, compare with the accurate VREF in DC reference position through comparison circuit, the square wave produced is as shown in Fig. 6 A dotted line, if direct current root-mean-square value is identical with reference level voltage, the duty ratio of this square wave is 50%, it is 2x reference level voltage that this comparison circuit exports Vcomp, wherein K=2, the Vbias voltage of corresponding Vint DC error amount is produced again after integrating circuit integration, and as shown in Fig. 5 and Fig. 6 B, this Vbias voltage can input the bias end points of aforementioned integral part 31, the DC error that its phase place can offset Vint exports direct current position standard to adjust integral part 31, and form the triangular wave Vint signal being positioned at corresponding DC reference voltage position standard.
Please refer to Fig. 1 to Fig. 4 and Fig. 7, phase measurements unit 4 has error amplifier, and input side input integral and direct current (DC) bias eliminate unit 3 output voltage Vint and transducer reset voltage VFB, and through superposition synthesis output pulse width modulation parameter signal, and the present embodiment tool the 6th operational amplifier OP6, and the inverting input of the 6th operational amplifier OP6 connects the 8th resistance R8 and integration direct current (DC) bias eliminates unit 3 output contact Vint, this inverting input connection the 9th resistance R9 is connected with the output of the 6th operational amplifier OP6 again, and this inverting input and the 8th resistance R8, tool phase node between the 9th resistance R9, the in-phase input end of the 6th operational amplifier OP6 connects transducer reset voltage point FB again, and adjustable the 8th resistance R8, the resistance of the 9th resistance R9 gets output voltage proper proportion and the transducer reset voltage VFB of corresponding integration and direct current (DC) bias elimination unit 3, the corresponding VFB voltage of the desirable Vint of preferably 1/20, and this aforesaid voltage is superposed with transducer reset voltage VFB synthesize, and make integration and direct current (DC) bias eliminate the output voltage triangular signal slope of unit 3 and the change slope vector of transducer reset voltage VFB to synthesize and form output pulse width parameter signal VEA.
Refer to Fig. 1 to Fig. 4 and Fig. 8, this accurate generation unit 5 in double track reference voltage position has two comparison circuits, and an input of this two comparison circuit connects DC reference position calibration signal, and this two comparison circuits contact resistance, and exported the upper and lower DC reference position standard of the accurate identical positive negative difference in corresponding DC reference voltage position respectively by the resistance setting of resistance.In the present embodiment, it has the 7th operational amplifier OP7, 8th operational amplifier OP8, and the 7th operational amplifier OP7, the in-phase input end of the 8th operational amplifier OP8 connects DC reference voltage position accurate unit 2 output contact REF, and the inverting input of the 7th operational amplifier OP7 connects the tenth resistance R10 ground connection, and inverting input connection the 11 resistance R11 is connected with output, and the 7th operational amplifier OP7 output produces the upper accurate VREF+ in DC reference position, inverting input connection the 12 resistance R12 of the 8th operational amplifier OP8 is connected with the output of the 7th operational amplifier OP7 again, and this inverting input connection the 13 resistance R13 is connected with the 8th operational amplifier OP8 output, and the inverting input of the 12 resistance R12 and the 13 resistance R13 and the 8th operational amplifier OP8 has phase node, and make the output of the 8th operational amplifier OP8 produce the lower accurate VREF-in DC reference position, and accurate VREF+ in DC reference voltage position is VREF+ (VREF * R11/R10) on this, the accurate VREF-in DC reference voltage position is descended again to be [(VREF+-VREF) *-1]+VREF, if set reference level VREF voltage as 1V, tenth resistance R10 is 99K, 11 resistance R11 resistance is 1K, then VREF+=1+ (1 * 1K/99K)=1.01V, VREF-=[(1.01V-1V) *-1]+1V=0.99V again.
Please refer to Fig. 1 to Fig. 4 and Fig. 9, pulse-width modulation generation unit 6 tool two comparison circuit of the present invention, and this comparison circuit input connects pulse-width modulation parameter signal EA and the upper accurate REF+ in DC reference position, another comparison circuit input connects pulse-width modulation parameter with signal EA and the lower accurate REF-in DC reference position, and two comparison circuits export the square-wave signal of forming reactions pulse-width modulation parameter signal slope variation, and this square-wave signal can amplify through flip-flop and coordinate soft starting circuit produce pulse-width modulation signal, and the present embodiment has the 9th operational amplifier OP9, tenth operational amplifier OP10, RS flip-flop, soft starting circuit 61, and this soft starting circuit 61 is the known techniques of power supply changeover device, no longer give stating more, the in-phase input end of the 9th operational amplifier OP9 connects the pulse-width modulation parameter signal EA that phase measurements unit 4 inputs again, the inverting input of the 9th operational amplifier OP9 connects the upper accurate REF+ in DC reference position again, and the tenth operational amplifier OP10 inverting input connects the pulse-width modulation parameter signal EA that phase measurements unit 4 inputs, and its in-phase input end connects the lower accurate REF-in DC reference position, 9th operational amplifier OP9 again, the output of the tenth operational amplifier OP10 connects the R end of RS flip-flop respectively, S holds, the Q end of RS flip-flop is connected AND lock with the output of soft starting circuit 61 again, and this AND lock exports generation pulse-width modulation signal PWM, make the voltage waveform slope of VEA rise to the punctual 9th operational amplifier OP9 in VREF+ position and export a high potential square wave, and make RS flip-flop output Q be that electronegative potential is to reduce converter output voltage, the voltage waveform slope of VEA is reduced to the punctual tenth operational amplifier OP10 in VREF-position and exports a high potential square wave again, and make RS flip-flop output Q be that high potential is to promote converter output voltage.
Please refer to Figure 10, tool of the present invention is by the pulse-width modulation framework of virtual current ripple PWM circuit 1 and driver 91 and upper and lower axle assemble Q1, Q2, and each pulse-width modulation framework input links same reaction output voltage signal, and each pulse-width modulation framework connects a corresponding outputting inductance respectively, and this each corresponding outputting inductance connects same output capacitance respectively does heterogeneous configuration, and make the present invention that loading demand can be coordinated to promote output current, and be that two groups of pulse-width modulation frameworks are in parallel shown in figure, the pulse-width modulation framework that load also can be coordinated to do more than two groups is arranged in parallel.
Aforementioned circuit of the present invention is illustration of the present invention, not limits as claim of the present invention, and all change according to the equivalence shown in spirit of the present invention also should belong to the contained lid of the present patent application the scope of the claims.
Claims (10)
1. a power supply changeover device pulse width modulating control circuit, this power supply changeover device comprises at least one upper axle assemble, once axle assemble, and this upper and lower axle assemble is electrically connected input power, and this upper and lower axle assemble connects through phase node, and phase node does switching over action by the driver action controlled by pulse-width modulation signal to make upper and lower axle assemble, this phase node connects outputting inductance, output capacitance again, and controls outputting inductance electric current to output capacitance charging generation output voltage, it is characterized in that, this pulse width modulating control circuit comprises virtual current ripple PWM circuit, and this virtual current ripple PWM circuit has integration and direct current (DC) bias eliminates unit, the accurate generation unit of phase measurements unit and double track reference voltage position, this integration and direct current (DC) bias eliminate the signal that unit inputs aforementioned phase node voltage signal and reaction output voltage, and produce the virtual current ripple parameter signal being positioned at DC reference voltage position standard, this phase measurements unit makes this virtual current ripple parameter signal and output voltage signal slope vector synthesize pulse-width modulation parameter signal, the accurate generation unit in this double track reference voltage position produces, lower DC reference voltage position is accurate, and this pulse-width modulation parameter signal and upper, lower DC reference voltage position standard compares generation pulse-width modulation signal input aforementioned drives.
2. power supply changeover device pulse width modulating control circuit as claimed in claim 1, it is characterized in that, this virtual current ripple PWM circuit also comprises an accurate unit in DC reference voltage position and a pulse-width modulation generation unit, and this accurate unit in DC reference voltage position provides one with reference to direct voltage position standard; This integration and direct current (DC) bias are eliminated unit input and are connected aforementioned phase node voltage signal, and connect the accurate unit in reference voltage position, and make the square wave of phase node voltage signal eliminate to form the triangular wave being positioned at DC reference position standard through integration and direct current (DC) bias, this triangular wave slope can reacting phase node voltage signal intensity, the integrated waveform voltage that this phase measurements unit receives integration and the output of direct current (DC) bias elimination unit superposes with converter output voltage the approximate triangle wave voltage producing and synthesize as ratio, and this voltage is as pulse-width modulation parameter signal; The input side of this accurate generation unit in double track reference voltage position connects the accurate unit in DC reference voltage position, and exports pulse-width modulation generation unit to; This accurate generation unit in double track reference voltage position produces the double track DC reference voltage unit of the positive and negative identical difference of the accurate voltage in corresponding reference voltage position; This pulse-width modulation generation unit input side connects phase measurements unit output and the accurate generation unit output in double track reference voltage position, and make that the upper DC reference position of the pulse-width modulation parameter signal that inputted by phase measurements unit and the accurate generation unit in double track reference voltage position is accurate, lower DC reference position standard compares, and produces pulse-width modulation signal.
3. power supply changeover device pulse width modulating control circuit as claimed in claim 2, it is characterized in that, this integration and direct current (DC) bias are eliminated unit and are had integral part and direct current (DC) bias elimination part, this integral part is by upper, the signal integration of the square wave of lower axle assemble phase node forms triangular signal, this direct current (DC) bias elimination part has integrating circuit and error amplifying circuit, this integrating circuit input connects the output of integral part, the accurate unit of output and DC reference voltage position that this error amplifying circuit connects integrating circuit exports, and make integral part export in correspondence, lower axle assemble phase node signal can form corresponding direct current position quasi wave shape through integrating circuit, and by error amplifying circuit, this direct current position quasi wave shape is compared with the DC reference voltage position standard of the accurate unit in DC reference voltage position again, and its DC error piezometric is through amplifying input integral part again, make integral part export the accurate triangle wave voltage in different direct current positions and can be adjusted to the triangular wave being positioned at DC reference voltage position standard.
4. power supply changeover device pulse width modulating control circuit as claimed in claim 2, it is characterized in that, this integration and direct current (DC) bias are eliminated unit and are had integral part and direct current (DC) bias elimination part, this integral part is by upper, the signal integration of the square wave of lower axle assemble phase node forms triangular signal, this direct current (DC) bias elimination part is made up of comparison circuit and integrating circuit, this comparison circuit input connects the accurate element output signal of output signal and DC reference voltage position of integral part, this integrating circuit input connects comparison circuit and the accurate element output signal in DC reference voltage position, the integrated waveform that integral part is received is accurate for DC reference position standard with DC reference voltage position, through the accurate voltage compare of comparison circuit and DC reference position, the DC error output voltage of the accurate corresponding reference level voltage in the corresponding DC reference voltage position produced after integrating circuit integration again, and this voltage input aforementioned integral part exports direct current position standard to adjust integral part, and form the triangular wave being positioned at corresponding DC reference voltage position standard.
5. power supply changeover device pulse width modulating control circuit as claimed in claim 2, it is characterized in that, this phase measurements unit has error amplifier, the input side input integral of this error amplifier and direct current (DC) bias eliminate unit and transducer reset voltage, and through superposition synthesis output pulse width modulation parameter signal.
6. power supply changeover device pulse width modulating control circuit as claimed in claim 2, it is characterized in that, this accurate generation unit in double track reference voltage position has two comparison circuits, and this two comparison circuit one input connects DC reference position standard, and this two comparison circuits contact resistance, and exported the upper and lower DC reference position standard of the accurate identical positive negative difference in corresponding DC reference voltage position respectively by the resistance setting of resistance.
7. power supply changeover device pulse width modulating control circuit as claimed in claim 2, it is characterized in that, this pulse-width modulation generation unit has two comparison circuits, and a wherein comparison circuit input of this two comparison circuit connects pulse-width modulation parameter signal and upper DC reference position calibration signal, wherein another comparison circuit input of this two comparison circuit connects pulse-width modulation parameter signal and lower DC reference position calibration signal, and two comparison circuits export the square-wave signal of forming reactions pulse-width modulation parameter signal slope variation.
8. power supply changeover device pulse width modulating control circuit as claimed in claim 2, it is characterized in that, comprise the pulse-width modulation framework be made up of virtual current ripple PWM circuit and driver and upper and lower axle assemble, and each pulse-width modulation framework input links same reaction output voltage signal, and each pulse-width modulation framework connects a corresponding outputting inductance respectively, and this each corresponding outputting inductance connects same output capacitance respectively does heterogeneous configuration.
9. a power supply changeover device pulse-width modulation control method, this power supply changeover device comprises at least one upper axle assemble, once axle assemble, and this upper and lower axle assemble is electrically connected input power, and this upper and lower axle assemble connects through phase node, and phase node does switching over action by the driver action controlled by pulse-width modulation signal to make upper and lower axle assemble, this phase node connects outputting inductance, output capacitance again, and controls outputting inductance electric current to output capacitance charging generation output voltage; It is characterized in that, this pulse-width modulation control method, comprises the following steps:
A. get the square wave voltage signal of phase node, and establish DC reference voltage position accurate, this signal results from the virtual current ripple parameter signal of DC reference voltage position standard through integration and direct current (DC) bias Processing for removing again;
B. reaction output voltage signal is superposed with virtual current ripple parameter signal the pulse-width modulation parameter signal synthesizing and have approximate triangular wave;
C. detect pulse-width modulation parameter signal and produce pulse-width modulation signal to control upper and lower axle assemble action.
10. power supply changeover device pulse-width modulation control method as claimed in claim 9, it is characterized in that, the upper and lower DC reference voltage position that the detection mode of aforementioned step c is provided with the accurate identical positive and negative voltage difference in corresponding DC reference voltage position is accurate, and the position that the rising of this pulse-width modulation parameter signal, decline ripple lay respectively at upper and lower DC reference position calibration signal can produce pulse-width modulation signal on time.
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| CN104283451B (en) * | 2013-07-05 | 2018-05-15 | 研能科技股份有限公司 | Polarity switching circuit |
| US9600063B2 (en) * | 2015-03-18 | 2017-03-21 | Intersil Americas LLC | Enhanced peak current-mode pulse-width-modulated (PWM) switching regulators |
| CN107846049B (en) * | 2016-09-20 | 2020-03-31 | 立锜科技股份有限公司 | Charging circuit, capacitive power supply conversion circuit thereof and charging control method |
| CN106656193A (en) * | 2016-12-08 | 2017-05-10 | 天津天喜国瑞科技发展有限公司 | Sigma-delta modulator and pulse width modulation tracking quantizer |
| CN107239052B (en) * | 2017-05-23 | 2019-09-24 | 中国电子科技集团公司第四十一研究所 | A kind of triggering level automatic calibrating method realized based on FPGA |
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