CN1711696B - Transmitting stage - Google Patents
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- CN1711696B CN1711696B CN200380103176.XA CN200380103176A CN1711696B CN 1711696 B CN1711696 B CN 1711696B CN 200380103176 A CN200380103176 A CN 200380103176A CN 1711696 B CN1711696 B CN 1711696B
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/02—Transmitters
- H04B1/04—Circuits
- H04B1/0475—Circuits with means for limiting noise, interference or distortion
Abstract
Disclosed is a transmission stage that is designed according to polar loop technology and comprises an amplitude-regulating device (16), a phase-regulating device (17), a VCO (14), and a feedback path (19). A variable amplifier (19b) is arranged in the feedback path. The amplitude-regulating device (16) is configured so as to be triggered by a control device (22) according to a request for a variation in power of the output signal of the amplifier, allowing an amplitude control signal for the power amplifier (13) to be varied accordingly. The control device is configured so as to trigger the variable feedback path amplifier accordingly such that the amplitude of the output signal of the variable feedback path amplifier remains within a narrowly limited predetermined range, whereby variations in power of the output signal of the amplifier that is operated in the non-linear range are kept away from the phase-regulating loop such that the phase-regulating device can be implemented in an inexpensive manner while operating in a reliable fashion.
Description
Technical field
The invention relates to transmitting stage and particularly about the transmitting stage that comprises amplitude locked loop and phase-locked loop with amplify via nonlinear power amplifier through amplitude and through the signal of phase modulated and, if be fit to, transmit this signal via wireless transmission channel.
Background technology
To the mobile communication service, only a limited number of frequency band exists.Required channel width and possible data rate in transfer of data are the deciding factor of characterization transmission system validity.Thereby in this frequency range, target is to obtain maximum data rate, exists different impelling to allow the method for High Data Rate more and make more thus that effective information stream can carry out at the same channel frequency range.
In recent years, in the field of mobile communication, GSM (Global System for Mobile Communication) standard becomes establishment.In this, use GMSK (Guassian Minimum Shift Keying GMSK) modulation, GMSK counts in general CPM (Continuous Phase Modulation) modulator approach that claims, and it is the non-linear, digital modulator approach of tool fixed amplitude and continuous phase.
The increase of information flow can be by the change start of modulator approach, in this, use 3 π/8-8PSK (phase shift keying) modulation of GSM EDGE (the enhancing data transfer rate of GSM) standard or QPSK (quadriphase PSK) modulation of UTMS (Universal Mobile Telecommunications System) standard to replace the GMSK modulation.These 3 π/8-8PSK modulation and QPSK modulation also comprise the amplitude composition except phase modulated.By this, the transmission that increases the extraneous information of data transfer rate can be used the same channel frequency range.
A vital point at movable terminal device is that the RF transmission amplifier is about transmitting the transmission performance of the RF signal that is used for EDGE and UMTS standard.Opposite with the GMSK modulation, in these 3 π/8-8PSK modulation and this QPSK modulation, phase place and amplitude are modulated, the spectrum that the result is respectively the output signal after the nonlinear power amplifier is widened or the obvious distortion of transmission signals, and this causes the increase of the bit error rate (BER) of the identical received field intensity of tool.
For minimizing these distortions, in fact need the use of linear power amplifier, yet, to compare with reaching the nonlinear power amplifier that surpasses 50% to 60% efficient, the efficient of about 35% linear amplifier is obviously relatively poor.
Because of the high energy of this system that poor efficiency caused of assembly opposite with the purpose that reaches long as far as possible mobile radio station operating time.
Signal reconstruction technology such as polar loop make and also can use nonlinear power amplifier in EDGE standard and UMTS standard.
The general polar loop transmission circuit that claims is to be described in as United States Patent (USP) the 4th, 481,672, WO02/47249A2, United States Patent (USP) the 4th, 630,315 or GB 2368214A.
European patent 1211801A2 also discloses a kind of suitable polar loop transmission circuit that is used for other mobile radio system, and this mobile radio system comprises that phase place and Modulation and Amplitude Modulation and its also can be used for the previous system according to this GSM standard.This polar loop transmission circuit comprises the power amplifier of the VCO received signal of comfortable input side, and the control signal of VCO is by the low-pass filter after relatively reaching as the amplitude of the transmission signals of nominal signal and by the subsequent phase of the amplitude of actual signal, constrained signal and gain.
The amplitude control signal of may command nonlinear power amplifier is by revising transmission signals as nominal signal, revise actual signal, forming and follow-up low-pass filter and producing by the follow-up difference of differential amplifier.
Actual signal is to tell being used for the amplitude adjustment and being used for the phase place adjustment from the output of this nonlinear power amplifier, is mixed to intermediate frequency, is supplied to and jumps the may command amplifier and then be fed to the rectifier of amplitude adjustment on the one hand and be fed to the limiter that phase place is adjusted on the other hand but be fed to processing amplifier and then fall.
But control end points at processing amplifier, the main feed-in of telling from output of feedback signal is in this, use control signal, power level in the output of polar loop transmission circuit can be adjusted, thus, but processing amplifier is a kind of linear amplifier, and its linearity weakens will be at the signal of its input supply, yet, the voltage of its high-frequency signal of being provided of output not for linearity according to the least significant bit variation that will decide and be 2 decibels of every adjustment signals at the adjustment signal that the control end points provides.
The typical polar loop transmission circuit that is disclosed in European patent 1211801A2 is suitable to be used for according to the honeycomb wireless telephone of GSM standard and suitablely to be used for carrying out phase place and amplitude-modulated alternative modulator approach.
The cellular mobile radio system tool of this kind amplifies adjustment automatically as organizing that part makes in the base station separately and/or implementing field intensity at moving-member and measure then upwards to regulate and control through-put power mobile phone and/or the base station and be based on low received field intensity (transmission channel that exists is satisfied at present) and determine when it.Because current drain is critical to moving-member only, power consumption is often regulated and is only implemented at this moving-member.
So wish on the one hand for low bit error rate thus automatically use unusual large transmission power as the signal/noise of this receiver when thereby this bit error rate reduce.On the other hand, large transmission power for do not desire because from user's increase impedance.And, large transmission power make the sub-district only can with the mode construction of suitable coarse net shape tissue or carrier frequency may be not for normal " reusing " as far as possible in the fact of sub-district grid, so that the user of high number can be arranged at limited frequency band.
Particularly when using nonlinear amplifier, large transmission power comprises the problem that the side channel disturbance may increase, that is in fact specify the conveyer that is used for carrier frequency because in fact its non-linear power of also sending to the side channel, should not transmit any amount or be lower than limiting value in this its.When the side channels transmit of general title is higher than certain specification, this kind transmitting device is according to adjusting.So to mentioned EDGE standard need be to be less than-54dBc at the spectrum of the output signal of the wireless device of the archives frequency that is relevant to carrier frequency+/-200 kilo hertz, and be to be less than-60dBc at the spectrum of the output signal of the wireless device of the offset frequency frequency that is relevant to carrier frequency+/-300 kilo hertz in addition.
The spectrum that the UMTS standard needs output signal whole adjacent channel-45dBc is good.
As if all these standards show that the signal power of mobile phone must be low as far as possible, that is the so little feasible just rough required bottom line bit error rate that satisfies.
In addition, mobile phone existed be necessary for cheap specific (special) requirements,, wherein can survive for the little saving system that makes because this Mobile Phone Market has developed into the market of extreme competition, that is it is accepted by market, but other system is not accepted by market.
To mobile phone, in being to use responsive as far as possible through-put power adjustment, it reaches minimizing through-put power as much as possible as far as possible fast under the situation of good transmission channel, yet it also can reach very apace and particularly increase through-put power very doughtily at main only generally poor channel.Thereby the very high dynamic range that is relevant to amplitude locked loop and PLL (it forms polar loop together) must be operated and handle on the other hand to the polar loop transmission circuit on the one hand with the dynamic range of quite high power amplifier.
But the shortcoming of European patent idea that 1211801A2 discloses is the setting of power output is to implement via the sequencing at the processing amplifier of feedback branch.The operational amplifier thereby must provide a kind of tool high dynamic output signal but jump in program and downstream, under a situation, that is the maximum output transmission power of tool, it is very little, and under another situation, that is the tool minimum output power, so it is very high and especially near the amplitude of the output signal of this transmission signals generator.
Found the fact that causes the rectifier detector of decision actual signal amplitude very expensively to carry out at the too high dynamic signal of feedback path tool, even more seriously produce the required amplitude limiter of actual signal phase place and also must very expensively carry out, because, when input signal becomes very hour within it, it needs very high amplification to reach amplitude so that the actual signal phase place to be provided, yet, this must be guaranteed in any situation, because no longer provide any defined output signal in case produce the amplitude limiter of actual signal phase place, the phase-locked loop of this polar loop takes place phase-locked, it causes the loss fully of transfer of data, change speech, the inefficacy of the phase-locked loop of this polar loop causes information to connect to be interrupted immediately reaching must wait for the new synchronized fact, this waits for for burden and intolerable, because it can easily be seen.
Summary of the invention
The object of the invention for provide a kind of safety and reliably operation through improvement transmission idea and wherein some assembly the time demand reduce and make conveyer low-costly to make.
This purpose can reach by following transmitting stage.
The present invention is based on and can implement the through-put power adjustment and make the phase-locked loop of polar loop circuit cross the discovery that is affected doughtily.But, according to the present invention, actual signal (the actual signal phase place obtains thus) is to maintain limited range, and this scope is preferably quite little, makes the power output of actual signal (the actual signal phase place obtains thus) and amplifier for not interdependent and be essentially fixing.Amplify to adjust but be used for the actual signal of amplitude adjustment or be preferably the nominal signal that is used for the amplitude adjustment reaching with the signal that obtains tool higher-wattage position standard or in the fact of the signal of the output device lower-wattage position of power amplifier standard by improvement accordingly.Change speech, this polar loop circuit may command amplifier of the present invention that is illustrated in feedback path provide for the operation make its output signal at preset range and be preferably be essentially fixing, and the amplitude adjustment apparatus that the amplitude that can implement to form polar loop circuit of the present invention is adjusted the loop some makes at outlet side to change accordingly at the actual signal of this amplitude adjustment apparatus and/or in the nominal signal of this amplitude adjustment apparatus, that is, exist tool corresponding through changing the signal of power level in the output of the signal of power amplifier.
An advantage of the present invention be present the actual signal that enters this phase adjusting apparatus be present in good definition dynamic range (it is preferably quite little) and in the good specific embodiment of spy, decrease to being essentially fixing value, thereby it guarantees that the phase-locked loop can not be locked in that strong position is accurate to be changed, but easily keeps operation to export in transferring to through amplifying signal with the phase data of printing in the signal by power amplifier.
Reliable functional security requirement that in addition advantage of the present invention is the phase-locked loop can be easily by the parts of phase adjusting apparatus, and particularly produce the fact that the amplitude limiter of actual signal phase place can carry out in a simple manner and satisfy from actual signal.Because the input signal of the limiter before phase place-frequency detector is to be positioned at the not dynamic range of strong variations of good definition, in this reasonable limits device that can provide the total cost of polarization ring transmission circuit to reduce, wherein this total cost reduces the reliability that can not cause any quality reduction fully but produce this idea increases.
In addition advantage of the present invention is for only providing one the may command amplifier is to amplify this actual signal or to amplify this nominal signal in addition for carrying out variable power, and wherein the requirement of this amplifier also is not harsh.If a kind of amplifier provides and is used to amplify the actual signal that enters this amplitude adjustment apparatus, the input dynamic range that then enters this amplifier is for knowing, because it is present in preset range and is preferably or even fixes.Preferable, this preset range comprises the deviation of the nominal value of the signal amplitude of thinking the signal flow behind this feedback path amplifier, and any power level is changed, and is in+/-10% variation frequency range.
So, can use special development to be used for the amplifier of this purpose, its unnecessary dynamically reaching about it is particularly designed about the strong variations input signal.In addition, this amplifier only needs to be audio frequency amplifier, if polar loop circuit of the present invention comprise frequency mixer in feedback branch with conversion tool transmission frequency f
2Feedback signal be the IF frequency f that is easy to control
1, because Amplifier Design can easily be carried out.
Yet, implement with the corresponding requirement of field intensity measurement mechanism if be to use in the nominal signal of this amplitude adjustment apparatus in the power adjustment of the outlet line of a preferred embodiment intermediate power amplifier of the present invention, then must be implemented without any the intervention that enters phase-locked loop itself, but, this transmitting device, its quotient of amplitudes and average power position standard are known or can adjust arbitrarily, nominal signal can easily be enhanced, make to this one or two in addition amplifier operate in respectively with amplifier and be " consistent " at feedback branch, need to expect without any the essence cost.
Description of drawings
Hereinafter, preferred embodiment of the present invention explains in detail with reference to correlative type, wherein:
Fig. 1 shows the calcspar of transmitting stage of the present invention;
Fig. 2 shows the calcspar according to the transmitting stage of the present invention of a preferred embodiment;
Fig. 3 is presented at the tabulation overview of control of amplifier of the different preferable uses of amplitude adjustment apparatus;
Fig. 4 A shows the equational explanation of dependence of amplifier control signal of certain amplification of the feedforward branch be used for the nominal signal improvement;
Fig. 4 B show the feedforward branch be used for the actual signal improvement certain amplify the example explanation of the equation relevant connection of V;
Fig. 5 A is presented at the comparison of preceding EDGE spectrum of this polar loop of optimization and polar loop spectrum; And
Fig. 5 B is presented at the comparison of use EDGE spectrum and polar loop spectrum behind this polar loop of amplification optimization of the different amplifiers of amplitude adjustment apparatus.
Embodiment
Fig. 1 shows that transmitting stage of the present invention is to provide input signal in the calcspar of importing with the amplifier of 10 expressions at Fig. 1.This amplifier comprises amplifier output 11 and control input 12 in addition, and this represents amplifier with 13 in Fig. 1.
This amplifier is preferably the amplifier with the nonlinear operation operation, if this amplifier is a bipolar transistor, then this amplification control is voltage-operated via supply, and the amplification control signal that is applied to this amplification control input in the case can cause the supply voltage differences.Yet, if this amplifier is the field-effect transistor amplifier, then be preferably the amplification of controlling this amplifier via this operating point, thus should control input 12 be exercisable with according to the example of foundation tabular or also by the feedback variation in characteristic source electrode-drain voltage or grid-source voltage or the two.
This transmitting stage is included in the may command oscillator that Fig. 1 represents with VCO.Be preferably, voltage-controlled oscillator is preferential.Perhaps, also can use certainly as current control oscillator.Under the situation of current control oscillator, the control signal of importing this oscillator 14 of 15 feed-ins in control is an electric current, is voltage-controlled yet work as this VCO 14, and the control signal of this VCO 14 of feed-in is a voltage.
To the polar loop circuit, other provides amplitude adjustment apparatus 16 and phase adjusting apparatus 17 as habitually in the past.When this phase adjusting apparatus 17 is coupled to control input 15 at this may command oscillator 14 of outlet side, this amplitude adjustment apparatus 16 is the amplification control inputs that are coupled at this amplifier 13 of outlet side.This phase adjusting apparatus 17 and this amplitude adjustment apparatus 16 all receive the actual signal 18 of the output that is applied to feedback path 19.This feedback path 19 comprises branch unit 19a, exports 11 branches through a part of input signal thus at amplifier.RF is used, that is be included in the frequency of RF scope when the output signal of this amplifier 11, can use thus as corresponding enforcement directional coupler with strips.
This feedback path 19 comprises in addition can import the variation feedback path amplifier 19b of control via control, that is uses and amplify control signal GS1.In the output of this feedback path amplifier 19b, exist through amplifying feedback signal, it is the amplitude at preset range, as narrating hereinafter.Optionally, provide other frequency translation device 19c to operate this phase adjusting apparatus 17 or this amplitude adjustment apparatus 16 respectively at intermediate frequency range at this feedback path 19.In the case, the output signal frequency of this amplifier 19b, it is as f
2, be converted to than Low Medium Frequency f
1,, can use normal frequency mixer/local oscillator combination at block 19c for reaching this purpose.
Whether being present in this feedback path 19 with this frequency translation device 19c has nothing to do, output at this feedback path 19, that is in the signal flow downstream of this feedback path amplifier 19b, actual signal is used, and this actual signal this phase adjusting apparatus 17 of feed-in on the one hand reaches this amplitude adjustment apparatus 16 of feed-in on the other hand.As carrying out hereinafter, this actual signal is processed as the actual signal at this phase adjusting apparatus.Be similar to this, this actual signal 18 is treated to the actual amplitude signal at this amplitude adjustment apparatus 16.
This amplitude adjustment apparatus 16 and this phase adjusting apparatus 17 receive the nominal signal 20 that is applied to signal input 21 (be provided for receiving and will be transmitted signal) all in addition.This nominal signal 20 is handled to obtain nominal phase signal at this phase adjusting apparatus 17.Accordingly, this nominal signal 20 is to handle to obtain the nominal amplitude signal at this amplitude adjustment apparatus 16.
As known in this skill, this amplitude adjustment apparatus 16 and this phase adjusting apparatus 17 are all operated and are made when being connected with this VCO 14 or this amplifier 13 respectively, and the difference between this nominal signal 20 and this actual signal 18 does not become littler or vanishing in the ideal case.In the case, this VCO 14 phase property of printing the signals that will transmit in input 21 is in the output signal in the output of this amplifier 11.Be similar to this, these amplifier 13 printings will transmit the amplitude characteristic of signal in the output signal in this amplifier output 11, yet, on the one hand, use another frequency, that is the RF transmission frequency, and in addition use in fact more high amplitude, that is RF transmission amplitude (its typical case goes up and wants the amplitude of transmission signals far above being applied to this input 21).
Transmitting stage of the present invention comprises control device 22 in addition, when control device 22 was imported requiring of 23 reception change outputting levels via the request of reception, control device was carried out to control this feedback path amplifier 19b via feedback path control amplifier control output 24 and reaches via amplitude adjustment apparatus input 25 these amplitude adjustment apparatus 16 of control.For reaching this purpose, should amplify control signal GS1 on the one hand via output 24 outputs, on the other hand, amplify control signal GS2 and/or amplify control signal GS3 and present and enter this amplitude adjustment apparatus 16 via output 25.
Finally being responsible for " error signal " in 16 outputs of this amplitude adjustment apparatus in this nominal signal 20 of this amplitude adjustment apparatus 16 and the difference between this actual signal 18 has muchly, and this signal is to import 12 by this control to be supplied to this amplifier.According to the present invention, this nominal signal 20 in this amplitude adjustment apparatus 16 and the difference between this actual signal 18 are according to being changed by these request input 23 resulting values, so this phase adjusting apparatus 17 can say so do not use its nominal signal 20 and actual signal 18 " attentions " thereof this through change request, it is not influenced by requirement through the change outputting level and always show that correct performance is to the degree that surpasses its limit " upsets " and phase-locked as if using generation that this phase adjusting apparatus 17 operates in.The phase-locked communicating interrupt that causes between conveyer and the receiver of generation by this phase adjusting apparatus 17, this VCO 14 and this feedback path 19 formed these phase-locked loops unavoidablely.
So do not take place, implement the average power position standard of this control device 22 with the signal of the signal output 11 that is controlled at this amplifier 13, require 23 these amplitude adjustment apparatus 16 of control to change this actual signal 18 and/or this nominal signal 20 in this amplitude adjustment apparatus 16 and to change the amplification (GS1) of this feedback path amplifier 19b simultaneously by the accurate change in foundation average power position, make the amplitude of output signal of this amplifier 19b, that is maintain the signal flow downstream of this feedback path amplifier 19b in preset range at the amplitude of the signal of this feedback path 19.It should be noted if not have any frequency inverted, the output signal of this amplifier 19b be directly to equal this actual signal 18, but that under the situation that frequency inverted 19c exists this actual signal 18 is that the output signal by this amplifier 19b obtains.
If in the requirement of this requirements input 23 is to make that exporting 11 output signal at the signal of this amplifier accepts more high-average power position standard, then this amplifier 19b less amplifies the signal from this branch unit 19a branch, make that the output amplitude at this amplifier 19b is at preset range once more, this scope be preferably " moving back " to a fixed value or put in known signal concussion very among a small circle.For in fact obtaining of the signal output 11 of this amplification increment in this amplifier 13, this control device 22 is to make the differential signal in the output of this amplitude adjustment apparatus increase via output 25 these amplitude adjustment apparatus 16 of control, to knowing this skill person for being apparent that this direction, that is towards the negative or positive direction, it is indicatrix according to this amplifier 13, that is being connected between the actual amplification V of amplifier control signal and this amplifier 13, how to form and decide.
The difference of this amplitude adjustment apparatus 16 outputs can by as when with this actual signal 18 compare this nominal signal 20 of being increased in this amplitude adjustment apparatus 16 in or by when with this nominal signal 20 compare minimizing in this amplitude adjustment apparatus 16 this actual signal 18 or by this nominal signal of increase and reduce this actual signal and increase.
Yet, if in the requirement of the input 23 of this control device 22 is to make the signal level in the output of this amplifier 13 be reduced, this is as determining to the situation of the good connection of base station when mobile phone, the amplifier 19b that then is controlled at this feedback path 19 is to increase its amplification, and this amplitude adjustment apparatus 16 is to control to reduce the error signal in this output via the output 25 of this control device 22, this can implement when comparing when reducing this nominal signal 20 with this actual signal, when comparing when increasing this actual signal with this nominal signal 20 or be similar to previous situation when two signals changing on the contrary.
Be noted that this moment also can implement as the decay assembly wherein negative in the case the amplification at the amplifier 19b of this feedback path 19 and in the amplifying device of hereinafter being discussed in this amplitude adjustment apparatus 16 corresponding to decay.Only based on representing clearly reason, amplify in hereinafter mentioning, wherein amplification also comprises negative the amplification, that is decay.
In addition be noted that in the output signal of the illustrated block of Fig. 1 it is that " operatively coupling " is to following block shown in Figure 1, this expression is unactual in entity component, as output as this VCO 14, be couple directly to the transistor input in this amplifier 13 and be present in without any other circuit during." operatively be coupled " but expression, match circuit with the impedance inverter circuit form can be provided between this VCO output and the output of this amplifier, it does not change relevant this any content through the information content of transmission signals, yet, its good really input impedance that changes this amplifier 13 that " escorts " as this VCO 14.Accordingly, output at device 16 and 17 still can provide other amplifier, turn one's coat device or other signal processing circuit, yet, it makes the signal improvement can not change anything about the fact, and for example the output of this amplitude adjustment apparatus 16 is " operatively coupling " amplitude control inputs 12 to this amplifier 13.
Hereinafter, with reference to figure 2, explain preferred embodiment of the present invention in detail.This phase adjusting apparatus 17 comprises that first limiter 171 is to be limited in Fig. 2 with S
In(t) Biao Shi this nominal signal 20.And, second limiter means 172 is provided, it is to implement to limit this actual signal 18.So there is nominal phase signal in the output at device 171, and the actual phase signal is applied to the output of device 172, these two signal feed-in phase/frequency detectors 173, its at a time between the some t with this actual signal difference feed-in also be expressed as this skill loop filter and Fig. 2 with 174 the expression low pass filters.Then be illustrated in the control signal of this VCO 14 by the differential phase signal of these low pass filter 174 filtering.
In specific embodiment shown in Figure 2, this amplitude adjustment apparatus 16 comprises the nominal signal amplifier 161 of the variable amplification of tool, and wherein the amplification control signal of this nominal signal amplifier 161 is to represent with GS3.Be similar to this, this amplitude adjustment apparatus 16 of Fig. 2 comprises that the actual signal amplifier 162 drawn with the variable attenuation device and its amplify control signal GS2 control for using.161 outputs of this nominal signal amplifier through amplifying nominal signal feed-in nominal amplitude demodulator 163.Accordingly, 162 outputs of this actual signal amplifier through amplifying also feed-in actual amplitude demodulator 164 of actual signal.This amplitude demodulator 163 and 164 is also implemented as the rectifier diodes circuit or can also any alternate manner be carried out amplitude envelope with the input signal that obtains being applied to it.
The nominal amplitude signal is applied to the output of this amplitude demodulator 163 of nominal signal, and the nominal amplitude signal is the noninverting input of this differential amplifier 165 of feed-in.The amplitude actual signal that is applied to the output of this amplitude demodulator 164 is the anti-phase input of this differential amplifier 165 of feed-in, be applied to this differential amplifier 165 output follow the low pass filter 166 of feed-in in this amplitude adjustment apparatus 16 through amplifying differential signal.This low pass filter 166 then provides and amplifies the outlet side of control signal in the amplification control input 12 that is fed to this power amplifier 13.In preferred embodiment of the present invention, be preferably this differential amplifier 165 and also comprise and can set amplification, wherein the amplification of this differential amplifier 165 is for can be by amplifying control signal GS4 control.
In preferred embodiment shown in Figure 2, provide frequency translation device 19c to comprise that be intermediate frequency f1 as known way carried out in this skill frequency mixer M1 and local oscillator LO with the signal of downward mixing tool RF frequency f 2 at this feedback path 19.
In preferred embodiment of the present invention shown in Figure 2, connect the signal generator of being formed by EDGE or UTMS modulator 211 and IQ modulator 212 in this input 21, wherein implement the signal component that this IQ modulator 212 is produced by this EDGE or UTMS modulator 211 with conversion, that is I signal and Q signal, be plural alternating signal at this intermediate frequency f1.
Be idea operation in circuit shown in Figure 2,, use PLL (phase-locked loop) and ALL (amplitude locked loop) in this according to polar loop signal reconstruction method.The i/q signal of EDGE or UTMS signal source upwards is modulated to the carrier frequency f1 at this IQ modulator 212.High frequency is through modulation signal S
In(t) amplitude information is eliminated in this limiter 171, and this makes that signal only comprises phase information after this limiter 171.Carry out at the input signal of this limiter 171 output and in the phase bit comparison between partly of the feedback of the output signal of these limiter 172 outputs at this phase-frequency detector PFD 173.Be fed to this VCO (voltage-controlled oscillator) by the corresponding error signal that T represents via this loop filter 174 that comprises the logical character of low strap at Fig. 2, so this VCO uses central frequency f2 to turn to the phase place of supplying from extraneous synchronously.
In preferred embodiment of the present invention shown in Figure 2, be converted to f1 in this frequency mixer M1 from f2 in the output signal frequency of transducer 13 outputs at this feedback path 19, wherein this signal is amplified accordingly respectively or is weakened by this feedback path amplifier 19b before this frequency mixer in preferred embodiment of the present invention.Perhaps, this amplifier 19b also can be arranged in after this frequency mixer.
After the amplitude information that is the feedback loop output signal of this limiter 172 was eliminated, this signal provision was to second input of this phase-frequency detector 173.
The PLL loop of this phase adjusting apparatus 17 of tool and this feedback path 19 thereby make this phase difference revise continuously because of result in the AM/PM of this power amplifier 13 distortion.
The result is for using linear R F power amplifier 13, and it be as at the power amplifier that grade C operates, and do not cause at the spectrum of the input signal of the output 11 of this power amplifier 13 to widen.
By this ALL loop, it is that this is through modulating input signal S by this amplitude adjustment apparatus 16 and this feedback path 19
In(t) envelope corresponds to this output signal S
Out(t).After the amplitude information of this input signal and the detection at the feedback loop output signal of these two amplitude demodulators 163 and 164, difference is formed and amplifies in this operational amplifier 165, that is according to the amplification control signal GS4 of this differential amplifier 165.As a result, this is supplied to this linear R F power amplifier 13 as amplitude control signal (RS) through amplifying signal via this loop filter 166 that the tool low strap leads to character.
This may command decay assembly/amplifier module the 161, the 162nd, the variable power and this PLL loop itself that are used for this linear R F power amplifier are unaffected, so this PLL loop is not influenced by the variable power of this linear R F power amplifier 13 and operates, this feedback path amplifier 19b provides in this feedback path 19.The decay of this amplifier 19b that implements with may command decay assembly, that is negative the amplification, thereby with this output signal S
Out(t) signal level is higher and bigger.
According to the present invention, thereby the amplitude information of this signal generator is by being reproduced by changing institute as the operating point of implementing this linear R F power amplifier 13 by this amplitude adjustment apparatus 16 and this feedback path 19 formed ALL loops certainly.
In addition, this output amplitude, that is at the signal S of overall transfer level output
Out(t) average power position standard is by may command decay assembly, that is by this feedback path amplifier 19b, be adjusted to preferable fixed value or preset range respectively, it can be selected such that this limiter 172 always operates safely and guarantee that the restriction of institute desire makes this phase-locked loop can not take place phase-locked with strong variable power so that defined this phase/frequency detector 173 that outputs signal to be provided, so, be maintained the increase/minimizing of the through-put power that the free space propagation channel to reach because of change of the variable power that is not subjected to this RF transmission amplifier 13 (for example because the requirement of mobile phone electronic installation) influence produces by this phase adjusting apparatus 17 and this feedback path 19 formed these PLL loops.
In addition, in preferred embodiment of the present invention shown in Figure 2, the signal level of this transmission amplifier is changed by amplifying device 161 and 162, so this PLL loop continues to be maintained impregnable and can not take place phase-locked with the variation of signal level.
The transmission feature in these two loops is set and makes their frequency range in preferred embodiment of the present invention, that is the cut-off frequency of this low pass 166 and 174 is selected such that the transmission of EDGE signal and UMTS signal can not have difficultly and carries out, this be by this frequency range for so big so that because this phase-locked loop takes place without any information loss.The useful frequency range that consideration is used for UMTS and EDGE is 2 MHz.
The amplification of this differential amplifier 165 is preferably to be set and makes this amplitude information of generation in the complete correspondence of this output signal.
For reaching this purpose, with reference to figure 5A and Fig. 5 B.Fig. 5 A is presented at the polar loop spectrum that is illustrated in Fig. 2 before the optimization, and this spectrum is to be shown in Fig. 5 A with 50a, is purpose relatively, at Fig. 5 A spectrum in addition according to this EDGE standard is shown, and represents with 50b.By Fig. 5 A as seen, near these two spectrum only close limit this central frequency " are positioned at top of each other ", yet, the not enough as yet optimizations of this polar loop, when higher offset frequency frequency, that is the frequency distance of this central frequency is used in 900 MHz certainly.Fig. 5 B is presented at the state behind the optimization, wherein is compared to the times magnification increase of this differential amplifier 165 of Fig. 2 with Fig. 5 A.The increase of comparing the amplification factor GS4 of Fig. 5 B with the optimization initial value of Fig. 5 A causes this polarity spectrum 50a to we can say " covering " in this EDGE spectrum 50b, that is the scope of restriction 100dBc.Be noted that too high GS4 value causes increasing continuously that the loop of amplitude locked loop amplifies this moment, so, know generally that as locked loop this concussion is inclined to and is continued to increase.Make this polar loop for enough optionally to satisfy desired side channel specifications so be preferably the enough height of the increase that makes this differential amplifier 165, yet, if the amplification of this differential amplifier 165 be unable can't increasing in addition, so this amplitude locked loop is operated safely and can not begin to shake because amplify in this high loop.
Hereinafter, with reference to form shown in Figure 3, its explanation is when higher or lower power P
OutRequirement when taking place indivedual amplification factors must how to change.Be noted that at the form of Fig. 3 herein and consider three kinds of situations, that is this amplitude adjustment apparatus only this amplifier 162 via GS2 change (row 300), this amplitude adjustment apparatus 16 of Fig. 2 only this amplifier 161 change (row 310) or this amplifier 162 (GS2) and this amplifier 161 (GS3) and all change (row 320).Such as in above discussion, be preferably the situation of operation instruction in row 310 because needn't relate to this actual signal 18, but only relate to nominal signal in this circuit input 21 in this situation.
If the control device 22 from Fig. 2 obtains the requirement that power output increases, at first the amplification of this feedback path amplifier 19b must be reduced, if situation 300 exists, then the amplification of this amplifier 162 also must be reduced in the case.Yet if situation 310 exists, the amplification of this amplifier 161 must be reduced, yet if situation 320 exists, GS2 must be reduced and GS3 must be increased.
Under the situation of the requirement that power output reduces, the amplification of this feedback path amplifier 19b must be increased.Under 300 the situation of being expert at, GS2 is increased, and under 310 the situation of being expert at, GS3 is reduced, and under 320 the situation of being expert at, GS2 is increased and GS3 is reduced.
So the power output according to this transmission amplifier is set controlling value GS1, for example, increase such as 5dB (by GS2 and/or GS3) along with the power output of this transmission amplifier, signal GS1 at this may command decay assembly must reduce about 5dB, this is provided at after this may command decay assembly GS1 signal and always has an equal-wattage position standard, that is keeps stabilisation and fixing.Controlling value GS2 and/or GS3 (deciding according to implementing) are responsible for this transmission amplifier variable power according to this EDGE and this UMTS standard (3GRP), by this, between this input signal and this feedback loop output signal in the differential of this operational amplifier apart from being that requirement according to the power output of this transmission amplifier changes, the controlling value of this operational amplifier is preferably this EDGE standard or this UMTS standard setting to fixing.Under the stable state situation, because of the non-linear caused gained error signal in this ALL loop of system by controlling value GS4 in this operational amplifier amplify make+/-200 kilo hertzs and+spectrum of the output signal of/-300 kilo hertzs EDGE standard respectively-54dBc or-60dBc is good, as illustrated about 5a and 5b figure.
Be noted that at this moment according to the spectrum of this amplifier output signal of UMTS standard must be whole adjacent channel-45dBc is good.
What will note in addition is to be preferably the frequency range of setting this amplitude locked loop and this phase-locked loop to make this EDGE signal reach the possibility that is transmitted as of (simultaneously) this UMTS signal according to the present invention.
Hereinafter, use Fig. 4 A and Fig. 4 B, as S in this directional coupler 19a output
Out(t) with the S that imports at this limiter 172
In(t) ratio is assumed to be V, and consistent the closing that can obtain between individual values is that Fig. 4 A is associated in the situation of Fig. 3 capable 310, and Fig. 4 B is associated in the situation of Fig. 3 capable 300.
Though showing this actual signal 18 and/or this nominal signal 20 in above-mentioned specific embodiment is to require to be changed by this amplifying device 161,162 according to the variation to this control 22, also be noted that the output signal that can alternatively change the output signal of this demodulator 163 and/or this demodulator 164 according to this power requirement is to produce amplification control signal through change in the output of this amplitude adjustment apparatus 16, as long as produce this amplifier power output of corresponding variation in the amplification control signal of these amplitude adjustment apparatus 16 outputs.Similarly, this feedback path amplifier 19b be according to through the amplification inverse ratio control of change with the actual signal of keeping this phase adjusting apparatus 17 of feed-in in preset range, as implementing, it is as far as possible little and degenerate to fixed value in fact at ideal situation that it can be made in principle, no matter the actual amplification of this amplifier 13.
Claims (17)
1. a transmitting stage is imported (10) so that input signal to be provided to the amplifier of amplifier (13), and amplifier comprises control input (12) and amplifier output (11) in addition, and this transmitting stage comprises:
A kind of signal input (21) is to receive the nominal signal (20) that will be transmitted;
A kind of may command oscillator (14) tool FREQUENCY CONTROL input (15) and oscillator output, wherein this oscillator output is operatively to be coupled to the amplifier of this amplifier (13) input (10);
A kind of feedback path (19), tool have the feedback path amplifier (19b) of variable amplification (GS1), and described feedback path (19) has a signal flow;
A kind of phase adjusting apparatus (17) is imported the frequency control signal of (15) with this FREQUENCY CONTROL that produces this may command oscillator (14), wherein this phase adjusting apparatus (17) is operatively to be coupled to this feedback path (19) to receive actual signal (18), and reaching wherein, this phase adjusting apparatus (17) is operatively to be coupled to this signal input (21) in addition to receive this nominal signal;
A kind of amplitude adjustment apparatus (16) is imported the amplitude control signal of (12) with this control that produces this amplifier (13), wherein this amplitude adjustment apparatus (16) is operatively to be coupled to this feedback path (19) to receive this actual signal (18), and reaching wherein, this amplitude adjustment apparatus (16) is to be coupled to this signal input (21) to receive this nominal signal (20); And
A kind of control device (22) is with the average power position standard of the signal of this amplifier output (11) of being controlled at this amplifier (13),
Wherein this control device (22) is implemented to control this amplitude adjustment apparatus (16) according to the requirement (23) of the accurate change in this average power position, so that this amplitude adjustment apparatus (16) uses this actual signal (18) and/or the amplification control signal of this nominal signal (20) generation through changing, this control device (22) is more operated to change the amplification (GS1) of (24) this feedback path amplifier (19b) simultaneously, make in this feedback path (19) and be arranged in this feedback path amplifier (19b) after the amplitude of signal of signal flow maintain preset range, wherein in this feedback path (19) and this signal that is arranged in the signal flow behind this feedback path amplifier (19b) be to equal this actual signal (18) or can derive from this actual signal (18), and
Wherein this control device (22) is to implement in addition to reduce the amplification (GS1) of this feedback path amplifier (19b) in the requirement (23) than high-average power position standard, and control (GS2, GS3) this amplitude adjustment apparatus (16), make this amplification control signal cause that the amplification of this amplifier (13) increases, and wherein this control device (22) is more implemented amplification (GS1) and the control (GS2 to increase this feedback path amplifier (19b) in the requirement (23) than low average power position standard, GS3) this amplitude adjustment apparatus (16) makes this amplification control signal cause that the amplification of this amplifier (13) reduces.
2. transmitting stage according to claim 1,
Wherein this amplitude adjustment apparatus comprises the changed nominal amplifier (161) of this nominal signal (20), and
Wherein implement this control device (22) to increase this average power position standard, reducing this amplification that can change feedback path amplifier (19b) (GS1) and receiving increases this amplification that can change nominal amplifier (161) (GS3) when this requires, or
Wherein implement this control device (22) to reduce this average power position standard, increase this amplification that can change feedback path amplifier (19b) (GS1) and receive and reduce this amplification that can change nominal amplifier (161) (GS3) when requiring.
3. transmitting stage according to claim 1,
Wherein this amplitude adjustment apparatus (16) comprise amplify this actual signal (18) change actual amplifier (162), and
Wherein implement this control device (22) to increase this average power position standard, reduce this amplification that can change feedback path amplifier (19b) (GS1) and receive and reduce this amplification that can change actual amplifier (162) (GS2) when this requires, or
Wherein implement this control device (22) to reduce this average power position standard, increasing the amplification (GS1) of this feedback path amplifier (19b) and receiving increases this amplification that can change actual amplifier (162) (GS2) when requiring.
4. transmitting stage according to claim 1, wherein this feedback path amplifier (19b) be embodied as a kind of change the decay assembly its for controllable to be implemented in the negative amplification of negative dB scope.
5. transmitting stage according to claim 1,
Wherein this amplitude adjustment apparatus (16) comprises a kind of differential amplifier (165) and downstream low pass filter (166), and wherein the output signal of this low pass filter (166) is the control input (12) that operatively is coupled to this amplifier (13),
Wherein this amplitude adjustment apparatus comprises the nominal amplitude demodulator (163) of the noninverting input that is coupled to this differential amplifier (165) in addition, and
Wherein this amplitude adjustment apparatus (16) comprises the actual amplitude demodulator (164) of the anti-phase input that operatively is coupled to this differential amplifier (165) in addition.
6. transmitting stage according to claim 1,
Wherein this phase adjusting apparatus (17) comprises a kind of phase/frequency detector (173) and downstream phase place low pass filter (174), wherein the output signal of this phase place low pass filter is the FREQUENCY CONTROL input (15) that operatively is coupled to this may command oscillator (14), and
Wherein this phase adjusting apparatus (17) comprises the nominal phase detector (171) of first input that is coupled to this phase/frequency detector (173) in addition, and
Wherein this phase adjusting apparatus (17) comprises the actual phase detector (172) of second input that operatively is coupled to this phase/frequency detector (173) in addition.
7. transmitting stage according to claim 6,
Wherein this actual phase detector (172) comprises a kind of predetermined input dynamic range, and wherein the preset range of the signal of the generation of the signal flow behind this feedback path amplifier (19b) is the predetermined input dynamic range that is less than or equal to this actual phase detector (172).
8. transmitting stage according to claim 7, wherein this actual phase detector is to comprise a kind of limiter circuitry.
9. transmitting stage according to claim 1,
This signal that wherein will transmit comprises first carrier frequency f 1 and comprises the second carrier frequency f2 at the signal of the amplifier output (11) of this amplifier (13) that it is this first carrier frequency to change this second carrier frequency that wherein another kind of frequency translation device (19c) provides in this feedback path (19).
10. transmitting stage according to claim 9, wherein this frequency translation device (19c) provides the signal flow after can changing feedback path amplifier (19b) at this.
11. transmitting stage according to claim 1, wherein this signal of this signal input (21) be according to the enhancing data rate standards that is used for global system for mobile communications evolution by global system for mobile communications defined or by the defined modulation scheme of Universal Mobile Telecommunications System standard by Modulation and Amplitude Modulation and phase modulated (211,212).
12. transmitting stage according to claim 1,
Wherein this control device (22) comprises a kind of control device, wherein is used for the value of magnification of this feedback path amplifier (19b) and the amplifying device (161,162) in this amplitude adjustment apparatus (16) is provided with the value of magnification that changes this amplification control signal as the variable power of input value and as will producing of output valve.
13. transmitting stage according to claim 1 is wherein implemented the requirement (23) of this control device (22) with the average power level change of the field intensity determination device that obtains cellular autofluorescence formula wireless transmission/receiving system.
14. transmitting stage according to claim 5, wherein this differential amplifier (165) comprises a kind of amplification (GS4) of setting, it is selected for the adjacent channel specification that satisfies the wireless specification that is effective to transmitting stage, wherein in this transmitting stage operation, this can be set amplification GS4 and be maintained at fixed value.
15. transmitting stage according to claim 1, wherein the cut-off frequency of this amplitude adjustment apparatus and this phase adjusting apparatus is made by sizing and takes place without any information loss by this amplitude adjustment apparatus and this phase adjusting apparatus.
16. transmitting stage according to claim 1,
Wherein implementing this control device (22) can change feedback path amplifier (19b) and make this preset range less than the dynamic range that is produced by the requirement (23) in the maximum change of the average power position standard of the signal of this amplifier output (11) of this amplifier (13) to control this.
17. one kind provides the method for input signal to the amplifier input (10) of amplifier (13), this amplifier comprises control input (12) and amplifier output (11) in addition, and this method comprises the following steps:
Import the nominal signal (20) that (21) acceptance is transmitted via signal;
Import the frequency control signal of (15) with the FREQUENCY CONTROL that produces may command oscillator (14) by phase adjusting apparatus (17), this may command oscillator (14) has more oscillator output, and wherein this oscillator output is operatively to be coupled to the amplifier of this amplifier (13) input (10);
This phase adjusting apparatus (17) is coupled to feedback path (19) to receive actual signal (18), this feedback path (19) has a signal flow and has the feedback path amplifier (19b) of variable amplification (GS1), and this phase adjusting apparatus (17) is coupled to this signal input (21) to receive this nominal signal;
Produce the amplitude control signal of this control input (12) of this amplifier (13) with amplitude adjustment apparatus (16);
Use the following step to be controlled at the average power position standard of signal of this amplifier output (11) of this amplifier (13) by control device (22):
This amplitude adjustment apparatus (16) is controlled in requirement (23) according to the accurate change in this average power position, so that this amplitude adjustment apparatus (16) uses this actual signal (18) and/or the amplification control signal of this nominal signal (20) generation through changing, and change the amplification (GS1) of (24) this feedback path amplifier (19b) simultaneously, make in feedback path (19) and be arranged in this feedback path amplifier (19b) after the amplitude of signal of signal flow maintain preset range, wherein in feedback path (19) and this signal that is arranged in the signal flow behind this feedback path amplifier (19b) be to equal this actual signal (18) or can derive from this actual signal, and wherein this controlled step comprises:
In than the requirement (23) of high-average power position standard, reduce the amplification (GS1) of this feedback path amplifier (19b), and control (GS2, GS3) this amplitude adjustment apparatus (16), make this amplification control signal cause that the amplification of this amplifier (13) increases; And
In than the requirement (23) of low average power position standard, increase the amplification (GS1) of this feedback path amplifier (19b), and control (GS2, GS3) this amplitude adjustment apparatus (16), make this amplification control signal cause that the amplification of this amplifier (13) reduces.
Applications Claiming Priority (5)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| DE10253181.1 | 2002-11-14 | ||
| DE10253181 | 2002-11-14 | ||
| DE10257435.9 | 2002-12-09 | ||
| DE10257435A DE10257435B3 (en) | 2002-11-14 | 2002-12-09 | transmitting stage |
| PCT/EP2003/012523 WO2004045093A1 (en) | 2002-11-14 | 2003-11-10 | Transmission stage comprising phases and an amplitude regulating loop |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN1711696A CN1711696A (en) | 2005-12-21 |
| CN1711696B true CN1711696B (en) | 2010-11-24 |
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN200380103176.XA Expired - Fee Related CN1711696B (en) | 2002-11-14 | 2003-11-10 | Transmitting stage |
Country Status (2)
| Country | Link |
|---|---|
| CN (1) | CN1711696B (en) |
| DE (1) | DE10257435B3 (en) |
Families Citing this family (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE102006001687A1 (en) | 2005-04-01 | 2006-10-05 | Rohde & Schwarz Gmbh & Co. Kg | Power control device |
| US7860466B2 (en) | 2006-06-04 | 2010-12-28 | Samsung Electro-Mechanics Company, Ltd. | Systems, methods, and apparatuses for linear polar transmitters |
| US7518445B2 (en) | 2006-06-04 | 2009-04-14 | Samsung Electro-Mechanics Company, Ltd. | Systems, methods, and apparatuses for linear envelope elimination and restoration transmitters |
| US7873331B2 (en) | 2006-06-04 | 2011-01-18 | Samsung Electro-Mechanics Company, Ltd. | Systems, methods, and apparatuses for multi-path orthogonal recursive predistortion |
| US8055212B2 (en) * | 2009-05-26 | 2011-11-08 | ST-Erisson SA | Transmitter phase shift determination and compensation |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2002033844A2 (en) * | 2000-10-18 | 2002-04-25 | Telefonaktiebolaget Lm Ericsson (Publ) | Communications systems |
| EP1211801B1 (en) * | 2000-11-15 | 2005-07-27 | Infineon Technologies AG | Polar Loop Transmitter |
Family Cites Families (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| GB2117589B (en) * | 1982-03-26 | 1985-10-16 | Philips Electronic Associated | Polar loop transmitter |
| GB2150378B (en) * | 1983-11-21 | 1987-06-03 | Philips Electronic Associated | Polar loop transmitter |
| FR2795280B1 (en) * | 1999-06-15 | 2001-08-10 | Sagem | MOBILE TELEPHONE COMPRISING A DEVICE FOR TRANSMITTING A MODULATED PHASE AND AMPLITUDE SIGNAL AND ITS ASSOCIATED METHOD |
| GB2368214B (en) * | 2000-10-17 | 2004-11-03 | Ericsson Telefon Ab L M | Communications systems |
| GB2369941A (en) * | 2000-12-09 | 2002-06-12 | Roke Manor Research | A polar loop amplifier arrangement with variable gain in a feedback loop |
-
2002
- 2002-12-09 DE DE10257435A patent/DE10257435B3/en not_active Expired - Fee Related
-
2003
- 2003-11-10 CN CN200380103176.XA patent/CN1711696B/en not_active Expired - Fee Related
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2002033844A2 (en) * | 2000-10-18 | 2002-04-25 | Telefonaktiebolaget Lm Ericsson (Publ) | Communications systems |
| EP1211801B1 (en) * | 2000-11-15 | 2005-07-27 | Infineon Technologies AG | Polar Loop Transmitter |
Also Published As
| Publication number | Publication date |
|---|---|
| DE10257435B3 (en) | 2004-09-09 |
| CN1711696A (en) | 2005-12-21 |
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