CN1592057A - DC-DC converter with load transient response fast reaction and method thereof - Google Patents
DC-DC converter with load transient response fast reaction and method thereof Download PDFInfo
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- CN1592057A CN1592057A CN 03156065 CN03156065A CN1592057A CN 1592057 A CN1592057 A CN 1592057A CN 03156065 CN03156065 CN 03156065 CN 03156065 A CN03156065 A CN 03156065A CN 1592057 A CN1592057 A CN 1592057A
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Abstract
This invention relates to a DC-DC converter with load transient quick response and its method including an output stage, a sensing circuit, a driver and a transient quick response circuit, in which, the output stage is connected between an input voltage and a low voltage to be controlled and switched to regulate a working period to generate an output voltage, the said sensing circuit senses the voltage to generate a feedback signal which is compared with a first reference voltage by the said conduction amplifier to generate a first current and is responded by the transient response to generate a second current, the first current is connected with a charge voltage, the driver compares the two reference signals with the voltage to generate a drive signal with the working period to the output stage, the transient response circuit compares the nodal point and second reference voltage to generate bypass signals to drive the output stage.
Description
Technical field
The present invention be relevant a kind of direct current to direct current transducer and method thereof, particularly have load transient response rapid-action direct current to direct current transducer and method thereof about a kind of.
Background technology
Direct current has been widely used in various electronic products to direct current transducer, its role is to the direct voltage of input is done the adjusting of voltage quasi position, for example boosts or step-down, and makes it to be stabilized between the voltage value that sets.In computer system, because CPU, internal memory and the employed power supply of hard disk are inequality, therefore need direct current that direct current transducer is regulated different voltages, so that being provided, uses each operating unit in the computer system.
Traditional direct current is the work period of adjusting an output stage with a drive signal to direct current transducer, and output voltage is maintained within a certain range.Traditional direct current is detected output voltage to produce a feedback signal to the direct current transducer mat, and by an error amplifier relatively this feedback signal and a reference signal to produce an error signal, again by a pulse-width modulation (PWM) comparator relatively this error signal and a sawtooth signal to produce a pwm signal, by a driver drives output stage.In this type of transducer, use a saw-toothed oscillator to produce the accurate position of a sawtooth signal as a pulse-width modulation (PWM) comparator, adjust the work period of this output stage.When the load current instantaneous variation, for example load current moment rising, cause the output voltage rapid drawdown, because with the foundation of sawtooth signal as this work period of adjustment, therefore, under the transient response of load, the reaction time that traditional direct current is adjusted this work period to direct current transducer is slow, makes that this output voltage can't the extremely due accurate position of fast lifting.Therefore, a kind of direct current of fast transient response is to be the institute Ji to direct current transducer and method thereof.
Summary of the invention
One of purpose of the present invention is to propose a kind of direct current to direct current transducer, to reach the purpose of transient response fast.
According to one embodiment of present invention, a kind of have load transient response rapid-action direct current direct current transducer comprised that an output stage is connected between an input voltage and the low pressure, and controlled switching and adjust a work period is to produce an output voltage; This output voltage of one sensing circuit senses produces a feedback signal; One conduction amplifier comparison, one first reference voltage and this feedback signal produce one first electric current, and derive one second electric current in response to a load response; One charge-discharge circuit connects this first electric current and produces a charging voltage; One driver relatively this charging voltage and first and second reference signal produces a drive signal with this work period and gives this output stage; And one transient response fast reaction circuit relatively this second electric current produce high impedance current comparison node and one second reference voltage, produce bypass signal to drive this output stage.
The method applied in the present invention comprises following steps: switch an output stage that is connected between an input voltage and the low pressure, to produce an output voltage;
This output voltage of sensing is to produce a feedback signal;
Relatively this feedback signal and one first reference voltage are to produce one first electric current and to produce one second electric current in response to a transient response;
Connect this first electric current to a charging circuit, to produce a charging voltage;
Relatively this charging voltage and first and second reference signal are given this output stage to produce a drive signal with a work period;
And relatively the high impedance current comparison node and one second reference voltage that are produced of this second electric current drives this output stage to produce a bypass signal.
Description of drawings
Fig. 1 is the circuit diagram of direct current of the present invention to direct current transducer;
Figure 2 shows that the circuit diagram of conduction amplifier among Fig. 1;
Fig. 3 is that the present invention and traditional direct current are to the output voltage waveform of direct current transducer under transient response.
The figure number explanation
100 direct currents are to direct current transducer 102 low-pressure side nmos pass transistors
104 high-pressure side nmos pass transistors, 106 inductance
108 converter output end 110SR flip-flops
112 inverters, 114 resistance
116 resistance, 118 conduction amplifier
The noninverting input of the anti-phase input of 118a 118b
120 current sources, 122 current sources
124 electric capacity, 126 comparators
The noninverting input of the anti-phase input of 126a 126b
The noninverting input of the anti-phase input of 128a 128b
130a first defeated 130b second input
134 switches, 136 current sources
The anti-phase input of 138 comparator 138a
The noninverting defeated 138c output of 138b
200PMOS transistor 204PMOS transistor
206PMOS transistor 208PMOS transistor
210NMOS transistor 212NMOS transistor
214NMOS transistor 216NMOS transistor
The output voltage waveforms of 300 the present invention under transient response
302 traditional direct currents are to the output voltage waveforms of direct current transducer under transient response
Embodiment
Fig. 1 is the circuit diagram of direct current of the present invention to direct current transducer 100, it comprises the output stage that a low-pressure side nmos pass transistor 102 and a high-pressure side nmos pass transistor 104 are formed, the source electrode of low-pressure side nmos pass transistor 102 is connected to an earth terminal GND, drain is connected to converter output end 108 via inductance 106, the source electrode of high-pressure side nmos pass transistor 104 is connected to output 108 via inductance 106, and drain is connected to an input supply voltage V
INThe gate of low-pressure side nmos pass transistor 102 and high-pressure side nmos pass transistor 104 is connected respectively to the anti-phase output Q of a SR flip-flop 110 and the output of inverter 112, switches to be controlled by drive signal LG and HG, produces output current I
OUTThe inductance 106 of flowing through, and produce output voltage V at converter output end 108
OUTOne resistance 114 and the 116 voltage divider sensing output voltage V of forming
OUT, to produce feedback signal VFB.One conduction amplifier 118 has an anti-phase input 118a connection feedback signal VFB and is connected a reference voltage V with a noninverting input 118
REF, conduction amplifier 118 is feedback signal VFB and reference voltage V relatively
REFAnd produce an electric current I at output 118c
GM1Reach at output 118d and produce an electric current I
GM2The charge-discharge circuit that current source 120,122 and an electric capacity 124 are formed is by electric current I
GM1Provide a charging current I with current source 120 and 122
C, to produce a charging voltage V
C, current source 120 has an electric current I
1, current source 122 has an electric current I
2, therefore, charging current I
CAnd electric current I
GM1And equal electric current I
1And I
2And, promptly
I
C+ I
GM1=I
1+ I
2(EQ-1) according to mathematical expression EQ-1, can be by Control current I
1, I
2And electric current I
GM1Change charging current I
CSize makes charging voltage V
CRate of change with charging current I
CChange.The work period of the driver control high and low pressure side nmos pass transistor 104,102 that comparator 126,128 and SR flip-flop 110 are formed, comparator 126 has an anti-phase input 126a and connects a reference voltage V
REF1, a noninverting input 126b connects charging voltage V
C, comparator 126 comparison reference voltage V
REF1And charging voltage V
C, 126c produces one first comparison signal in output, and it is a high or low accurate position voltage.Comparator 128 has an anti-phase input 128a and connects charging voltage V
C, a noninverting input 128b connects reference voltage V
REF2, comparator 128 comparison reference voltage V
REF2And charging voltage V
C, 128c produces one second comparison signal in output, and it is a high or low accurate position voltage.SR flip-flop 110 has two input S, R and complementary output end Q and Q, input S and R connect first and second comparison signal respectively, when first or second comparison signal is high levle, output Q produces high levle voltage and output Q produces low level voltage, via NOR gate 130 and inverter 112 outputs, to open high-pressure side nmos pass transistor 104; When the first or second comparison signal low level, output Q produces low level voltage and output Q produces high levle voltage, to open low-pressure side nmos pass transistor 102.Output high-low pressure that Q produced accurate position controllable switch 132 and 134 unlatching or close make electric current I
1Or I
2The electric current I that is produced with conduction amplifier 118
GMCharging current I is provided
CFlow to or flow out electric capacity 122 to change charging voltage V
CRate of change.The transient response fast reaction circuit that one current source 136, a comparator 138, NOR gate 130 and inverter 112 are formed is in response to load transient response or reference voltage V
REFDuring much larger than feedback signal VFB, conduction amplifier 118 produces electric current I
GM2, current source 136 connects output 118d, and produces certain electric current I
3, comparator 138 has an anti-phase input 138a and a noninverting input 138b, and anti-phase input 138a connects a reference voltage V
REF3, noninverting input 138b connects output 118d, by electric current I
GM2Reach and decide electric current I
3Connection has high impedance current comparison node 138a, through comparator 138 and reference voltage V
REF3Relatively, and produce a bypass signal at the output 138c of comparator 138, and NOR gate 130 has an input 130a and 130b connects output Q and output 138c respectively, and the output 130c of NOR gate 130 connects the input of inverter 112, when transient response, comparator 138 comparison reference voltage V
REF3Produce bypass signal with high impedance current comparison node 138a, for directly controlling high-pressure side nmos pass transistor 104 as drive signal HG.
Direct current has three kinds of operator schemes to direct current transducer 100, and it is to be set by conduction amplifier 118.Under the Delta-sigma pattern, electric current I
GM1Be to flow into amplifier 118, promptly have suction electric current (sinking) ability, when the load current instantaneous variation, by feedback signal VFB and reference voltage V
REFDifference adjust work period of high and low pressure side nmos pass transistor 104 and 102.Under the magnetic hysteresis pattern, electric current I
GM1Can flow into amplifier 118 or, promptly have the electric current of suction and output current (sourcing) ability simultaneously, make output voltage V from amplifier 118 outflows
OUTBe adjusted in the scope.Under the peak valley pattern, electric current I
GM1Be to flow out, promptly have the output current ability, make output voltage V from amplifier 118
OUTMaintain on the accurate position of a low pressure.
According to mathematical expression EQ-1, under three kinds of operator schemes, electric current I
GM1Size, influence charging current I
CSize.Under the Delta-sigma pattern, amplifier 118 has suction current capacity, electric current I
GM1Flow to amplifier 118, make electric current I
1Charging current I need be provided
C, electric current I
2And electric current I
GM1, therefore, mathematical expression EQ-1 is revised as under the Delta-sigma pattern
I
C+ I
2+ I
GM1=I
1(EQ-2) under the magnetic hysteresis pattern, amplifier 118 has the electric current of suction and output current ability simultaneously, so electric current I among the mathematical expression EQ-1
GM1Change charging current I according to sucking electric current or output current
CAnd under the peak valley pattern, amplifier 118 has the output current ability, electric current I
GM1Flow out electric current I from amplifier 118
GM1And electric current I
1Charging current I is provided
CAnd electric current I
2, therefore, according to mathematical expression EQ-1 control charging current I
C
Direct current is to current source 120 and 122 electric current I that provide of direct current transducer 100
1And I
2With input and output voltage V
1NAnd V
OUTProportion relation.
In any case, conduction amplifier 118 is adjusted electric current I
GM1Make the charging voltage V of electric capacity 124
CAlong with electric current I
GM1Change, with the work period of control high and low pressure side nmos pass transistor 104,102, and when transient response took place, conduction amplifier 118 produced electric current I in response to transient response
GM2, and see through comparator 138 generation bypass signal fast, with the work period of control high-pressure side nmos pass transistor 104, make when load transient response, but direct current is to direct current transducer 100 fast reactions.
Figure 2 shows that the circuit diagram of conduction amplifier 118 among Fig. 1, it comprises PMOS transistor 200,202,204,206,208 and nmos pass transistor 210,212,214,216,218 and current source 220, the source electrode of PMOS transistor 200 connects the source electrode of PMOS transistor 208, the drain of PMOS transistor 200 connects the drain and the gate of nmos pass transistor 216, the drain of PMOS transistor 208 connects the drain and the gate of nmos pass transistor 218, the source electrode of PMOS transistor 202 connects the source electrode of PMOS transistor 204 and 206, the gate of PMOS transistor 202 is connected the gate of PMOS transistor 204 and 206 with drain, the drain of PMOS transistor 202 connects the drain of nmos pass transistor 210, the drain of PMOS transistor 204 connects the drain of nmos pass transistor 212, the drain of PMOS transistor 206 connects the drain of nmos pass transistor 214, the gate of nmos pass transistor 210 connects the gate of nmos pass transistor 216, the gate of nmos pass transistor 214 connects the gate of nmos pass transistor 212 and 218, nmos pass transistor 210,212,214,216 and 218 source electrode connects earth terminal, current source 220 is between the source electrode of the source electrode of PMOS transistor 202 and PMOS transistor 200, the gate of PMOS transistor 200 connects feedback signal VFB, and the gate of PMOS transistor 208 connects reference voltage V
REF, the drain of PMOS transistor 206 and nmos pass transistor 214 connects electric capacity 124, and the drain of PMOS transistor 204 and nmos pass transistor 212 connects the anti-phase input 138a of comparator 138.Direct current has three kinds of operator schemes to direct current transducer 100, and it is Delta-sigma pattern, magnetic hysteresis pattern and peak valley pattern, and these three kinds of operator schemes are 118 decisions of design conduction amplifier.Shown in Figure 2 is the conduction amplifier 118 that direct current uses in the magnetic hysteresis pattern direct current transducer 100, as reference voltage V
REFGreater than feedback signal VFB, 206 conductings of PMOS transistor also produce electric current I
GM1Flow to electric capacity 124, otherwise, as reference voltage V
REFLess than feedback signal VFB, nmos pass transistor 214 conductings also produce electric current I
GM1Flow to conduction amplifier 118.Therefore, the present invention is under the magnetic hysteresis pattern, and conduction amplifier 118 has output current and sucks the ability of electric current.Under the Delta-sigma pattern, conduction amplifier 118 does not have PMOS transistor 206, so 118 of conduction amplifier have the ability that sucks electric current.Under the peak valley pattern, conduction amplifier 118 does not have nmos pass transistor 214, so 118 abilities with output current of conduction amplifier.
Along with reference voltage V
REFBigger with the difference of feedback signal VFB, make that the work period of high-pressure side nmos pass transistor 14 is bigger, otherwise, reference voltage V
REFLittler with the difference of feedback signal VFB, then the work period of high-pressure side nmos pass transistor 14 littler, therefore, under the Delta-sigma pattern, the work period of high and low pressure side nmos pass transistor 14,12 is in response to reference voltage V
REFAdjust with the difference of feedback signal VFB, in order to do output voltage is maintained in the scope.
As shown in Figure 2, as reference voltage V
REFGreater than feedback signal VFB, i.e. when transient response takes place, the drain output current I of PMOS transistor 204 and nmos pass transistor 212
GM2, make comparator 138 produce bypass signal and directly drive high-pressure side nmos pass transistor 104, reach direct current to direct current transducer 100 load transient response rapid-action purposes.
Fig. 3 is that the present invention and traditional direct current are to the output voltage V of direct current transducer under transient response
OUTOscillogram, the present invention in the output voltage waveforms under the transient response 300 and traditional direct current to the output voltage waveforms 302 of direct current transducer under transient response, at output current I
OUTMoment is when rising, because transient response fast reaction circuit of the present invention fast reaction, make comparator 138 produce high levle output, thereby directly adjust work period of high-pressure side nmos pass transistor 104, therefore, by the present invention in the contrast of the output voltage waveforms under the transient response 300 and traditional direct current to the output voltage waveforms 302 of direct current transducer under transient response, when time T 1, output voltage V of the present invention
OUTBy the work period of transient response fast reaction circuit control high-pressure side nmos pass transistor 104, make output voltage V
OUTRise, and traditional output voltage V
OUT' must drop to minimum voltage V
MINAfter just reaction make output voltage V
OUT' rise, when time T 2, output voltage V of the present invention
OUTReached set point, and traditional output voltage V
OUT' still need one period reaction time, in other words, the direct current that the present invention is more traditional has the ability of load transient response fast reaction to direct current transducer.
More than the narration done for the present invention's preferred embodiment be purpose for illustrating, accurately be disclosed form and be not intended to limit the present invention, based on above instruction or to make an amendment or change from embodiments of the invention study be possible, embodiment has the knack of this operator and utilizes the present invention to select in practical application with various embodiment and narrate for explaining orally principle of the present invention and allowing, and technological thought attempt of the present invention is decided by following claim and equalization thereof.
Claims (14)
1. one kind has load transient response rapid-action direct current to direct current transducer, it is characterized in that, comprising:
One output stage is connected between an input voltage and the low pressure, and controlled switching and adjust a work period is to produce an output voltage;
One sensing circuit produces a feedback signal with this output voltage of sensing;
One conduction amplifier produces one first electric current to compare one first reference voltage and this feedback signal, and answers a load response to derive one second electric current;
One charge-discharge circuit connects this first electric current and produces a charging voltage;
One driver is so that relatively this charging voltage and first and second reference signal generation one have the drive signal of this work period to this output stage;
And a transient response fast reaction circuit, produced high impedance current comparison node and one second reference voltage with this second electric current relatively, produce bypass signal to drive this output stage.
2. transducer as claimed in claim 1 is characterized in that, this charge-discharge circuit comprises:
One first current source between a high pressure and a node is controlled by this drive signal;
One second current source between this node and a low pressure is controlled by this drive signal;
One electric capacity connects this node, to produce this charging voltage.
3. transducer as claimed in claim 1 is characterized in that, this driver comprises:
One first comparator is so that relatively this first reference signal and this charging voltage produce one first comparison signal;
One second comparator is so that relatively this second reference signal and this charging voltage produce one second comparison signal;
And a flip-flop, producing this drive signal by first and second comparison signal.
4. transducer as claimed in claim 1 is characterized in that, this transient response fast reaction circuit comprises:
One comparator, has first and second input, this first input end connects a bias current and this conduction amplifier to introduce this generation high impedance current comparison node, and this second input connects this second reference voltage, produces a transient response reaction signal according to this;
One NOR gate connects this driver and transient response reaction signal, produces an output when this transient response;
And an inverter, the output that connects this NOR gate is to produce this bypass signal.
5. transducer as claimed in claim 1 is characterized in that, this first electric current can flow to this conduction amplifier under the Delta-sigma pattern.
6. transducer as claimed in claim 1 is characterized in that, this electric current residual quantity flows to this conduction amplifier or flows out from this conduction amplifier under the magnetic hysteresis pattern.
7. transducer as claimed in claim 1 is characterized in that, this first electric current flows out from this conduction amplifier under 0 pattern.
8. transducer as claimed in claim 2 is characterized in that the ratio of this first and second current source is proportional to the ratio of this input and output voltage.
9. transducer as claimed in claim 3 is characterized in that, this flip-flop comprises a SR flip-flop.
10. one kind has load transient response rapid-action direct current to DC voltage transforming method, it is characterized in that, comprises the following steps:
Switch an output stage that is connected between an input voltage and the low pressure, to produce an output voltage;
This output voltage of sensing is to produce a feedback signal;
Relatively this feedback signal and one first reference voltage are to produce one first electric current and to produce one second electric current in response to a transient response;
Connect this first electric current to a charging circuit, to produce a charging voltage;
Relatively this charging voltage and first and second reference signal are given this output stage to produce a drive signal with a work period;
And relatively the high impedance current comparison node and one second reference voltage that are produced of this second electric current drives this output stage to produce a bypass signal.
11. method as claimed in claim 10 is characterized in that, the step that produces this charging voltage comprises the following steps:
This first electric current charges to an electric capacity;
This drive signal is switched one the 3rd electric current and is connected to this electric capacity;
This drive signal is switched and is drawn one the 4th electric current from this electric capacity.
12. method as claimed in claim 10 is characterized in that, relatively the step of this charging voltage and this first and second reference signal comprises the following steps:
Relatively this first reference signal and this charging voltage are to produce one first comparison signal;
Relatively this second reference signal and this charging voltage are to produce one second comparison signal;
Produce this drive signal in response to this first and second comparison signal.
13. a method of improving direct current to the load transient response reaction of direct current transducer is characterized in that, comprises the following steps:
Transient response in response to the output voltage of this transducer produces a bypass signal;
Drive the output stage of this transducer by this bypass signal.
14. method as claimed in claim 13 is characterized in that, the step that produces this bypass signal comprises the following steps:
The output voltage of this transducer of sensing is to produce a feedback signal;
Relatively this feedback signal and one first reference voltage are to produce an electric current;
And relatively this electric current produces high impedance current comparison node and one second reference voltage to produce this bypass signal.
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNB031560652A CN100337390C (en) | 2003-08-29 | 2003-08-29 | DC-DC converter with load transient response fast reaction and method thereof |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNB031560652A CN100337390C (en) | 2003-08-29 | 2003-08-29 | DC-DC converter with load transient response fast reaction and method thereof |
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| Publication Number | Publication Date |
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| CN1592057A true CN1592057A (en) | 2005-03-09 |
| CN100337390C CN100337390C (en) | 2007-09-12 |
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