CN118054677A - Current stress modulation method of two-level DAB and storage medium - Google Patents
Current stress modulation method of two-level DAB and storage medium Download PDFInfo
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Abstract
The invention discloses a two-level DAB inductive current stress modulation method and a storage medium, and relates to the technical field of converter optimal control. The method comprises the following steps: dividing a current operation mode of the two-level DAB, and determining an inductance current and transmission power in the operation mode; the circuit includes eight modes; calculating the ZVS range and the stress of the inductive current of each mode, namely the inductive current peak value, and carrying out numerical discrete optimization on the current stress in the corresponding transmission power range and the ZVS range to obtain an off-line optimal control table; and carrying out inductive current stress modulation on the two-level DAB by utilizing the optimized control table. The invention applies the modulation method combining the pulse width modulation strategy and the blocking capacitor to the converter, can control the converter based on the off-line optimal control table, reduces the current stress of the converter and improves the overall operation efficiency.
Description
Technical Field
The invention relates to the technical field of converter control, in particular to a current stress modulation method of two-level DAB and a storage medium.
Background
The most traditional control strategy of the two-level double active bridge converter (DAB) is single phase shift control (SINGLE PHASE SHIFT, SPS), which changes the direction and the size of transmission power by controlling the inter-bridge phase shift angle of the primary side and the secondary side, but the two-level double active bridge converter has only one control degree of freedom, and the phase shift control is carried out under the condition that the traditional control strategy is a fixed half-period duty ratio, so that the phase shift control of the variable duty ratio cannot be realized, and the transformer cannot work normally because of magnetic bias. When the voltage at two sides of the converter is not matched, namely k is not equal to 1, the full-range zero voltage switching on is difficult to realize under the working condition, but the full-power-range zero voltage switching on can be realized when the input voltage and the output voltage are matched, and the defects of high current stress, low converter efficiency and the like exist. At this time, a plurality of control degrees of freedom are needed, and because of the coupling relation between different control degrees of freedom, the more the control quantity is, the more complicated the control is, and the more difficult the optimization of the current stress is by the traditional mathematical method.
Disclosure of Invention
The invention aims to provide a current modulation method of two-level DAB and a storage medium, which can control a converter based on a control boundary and an off-line optimal control table, increase the control freedom of the converter and improve the overall operation efficiency.
In order to achieve the above object, the present invention provides the following solutions:
A current modulation method of two-level DAB and a storage medium, comprising:
dividing a current operation mode of the two-level DAB, and determining an inductance current and transmission power in the current operation mode; the current operation modes include eight modes;
Calculating peak values of the transmission power and the inductance current under each mode, namely current stress, and carrying out numerical discrete optimization on the current stress in a corresponding transmission power range and a zero voltage opening range (Zero Voltage Switching, ZVS) to obtain an off-line optimal control table;
And carrying out current modulation on the two-level DAB by utilizing the actual control boundary and the optimized control table.
Optionally, the dividing the current operation mode of the two-level DAB to determine the inductor current and the transmission power in the current operation mode specifically includes:
Dividing eight working modes according to the phase relation of the rising edges of the primary side output voltage and the secondary side output voltage of the two-level DAB; the working modes of the two-level DAB comprise a mode A, a mode B, a mode C, a mode D, a mode E, a mode F, a mode G and a mode H;
based on the divided working modes of the two-level DAB, respectively solving the inductive current and the transmission power under eight modes according to an equivalent circuit model and a typical voltage waveform.
Optionally, the equivalent circuit model is composed of a primary full bridge, a secondary full bridge, a leakage inductance equivalent inductance, a high-frequency isolation transformer, a blocking capacitor and 4 bypass capacitors; the primary full bridge consists of 4 switching tubes and 4 antiparallel diodes; the secondary full bridge consists of 4 switching tubes and 4 anti-parallel diodes; the leakage inductance equivalent circuit is the sum of a high-frequency inductor and a transformer leakage inductance; the blocking capacitor is connected in series with the primary side and the secondary side of the high-frequency isolation transformer.
Optionally, calculating the peak value of the inductance current, namely current stress, under each mode, and performing numerical discrete optimization on the stress in a corresponding transmission power range to obtain an offline optimal control table, which specifically includes:
Calculating instantaneous values of the transmission power and the inductive current in each mode, comparing to obtain inductive current peak values, namely current stress, taking the current stress of the inductive current as an optimization target, carrying out discrete numerical optimization on the inductive current stress in a full power range by taking the transmission power and a ZVS range as limiting conditions, and establishing an offline optimal control table.
Optionally, the current modulation is performed on the two-level DAB by using the optimized control table, which specifically includes:
and using the optimized control table to enable the two-level DAB to generate corresponding direct-current bias voltages under the corresponding working mode so as to meet different input-output voltage ratios and finish current modulation.
The invention also provides a memory electronic device, which comprises a memory and a processor, wherein the memory is used for storing a controller execution program, and the processor runs the controller execution program to enable the memory electronic device to execute the current modulation method of the two-level DAB.
The present invention also provides a computer-readable storage medium storing a computer-executable program which, when executed by a processor, implements the current modulation method of two-level DAB as described above.
According to the specific embodiment provided by the invention, the invention discloses the following technical effects:
The invention discloses a two-level DAB inductive current stress modulation method and a storage medium, wherein the method comprises the steps of dividing a current operation mode of the two-level DAB, and determining inductive current and transmission power in the current operation mode; the current operation modes include eight operation modes; dividing a ZVS range, calculating the stress of the inductive current of each mode, namely an inductive current peak value, carrying out numerical discrete optimization on the current stress in the corresponding transmission power range and the ZVS range to obtain an off-line optimal control table, and carrying out current modulation on the two-level DAB. The invention applies the modulation method combining the pulse width modulation strategy and the blocking capacitor to the converter, and can enable the converter to generate corresponding direct-current bias voltage under the corresponding working mode so as to adapt to different input-output voltage ratios, thereby realizing ZVS of the full-switching tube and reducing the switching loss of the converter; meanwhile, the converter is controlled based on the off-line optimal control table, so that the control degree of freedom of the converter is increased, the current stress of the converter is reduced, the on-state loss is reduced, and the overall operation efficiency is improved on the premise of ensuring safe operation.
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In order to more clearly illustrate the embodiments of the present invention or the technical solutions of the prior art, the drawings that are needed in the embodiments will be briefly described below, it being obvious that the drawings in the following description are only some embodiments of the present invention, and that other drawings may be obtained according to these drawings without inventive effort for a person skilled in the art.
FIG. 1 is a flow chart of a current modulation method of two-level DAB according to the present invention;
FIG. 2 is a schematic diagram of a two-level DAB topology based on a blocking capacitor in the present embodiment;
FIG. 3 is a diagram of an inductor current stress control framework based on the structure of FIG. 2 in this embodiment;
FIG. 4 is a schematic diagram of the main waveforms of operation of each mode in the present embodiment; wherein (a) is a waveform diagram of a mode A, (B) is a waveform diagram of a mode B, (C) is a waveform diagram of a mode C, (D) is a waveform diagram of a mode D, (E) is a waveform diagram of a mode E, (F) is a waveform diagram of a mode F, (G) is a waveform diagram of a mode G, and (H) is a waveform diagram of a mode H;
FIG. 5 is a flow chart of an offline optimization algorithm;
FIG. 6 is a schematic diagram of a control flow of the controller in the present embodiment;
FIG. 7 is an efficiency curve for three different control strategies.
Detailed Description
The following description of the embodiments of the present invention will be made clearly and completely with reference to the accompanying drawings, in which it is apparent that the embodiments described are only some embodiments of the present invention, but not all embodiments. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
The invention aims to provide a current modulation method of two-level DAB and a storage medium, which can control a converter based on an actual control boundary and an off-line optimal control table, increase the control freedom of the converter and improve the overall operation efficiency.
In order that the above-recited objects, features and advantages of the present invention will become more readily apparent, a more particular description of the invention will be rendered by reference to the appended drawings and appended detailed description.
As shown in fig. 1, the present invention provides a current modulation method of two-level DAB, comprising:
Step 1: dividing a current operation mode of the two-level DAB, and determining an inductance current and transmission power in the current operation mode; the current operation modes include eight modes; the method specifically comprises the following steps:
Dividing eight working modes according to the phase relation of the rising edges of the primary side output voltage and the secondary side output voltage of the two-level DAB; the working modes of the two-level DAB comprise a mode A, a mode B, a mode C, a mode D, a mode E, a mode F, a mode G and a mode H; based on the divided working modes of the two-level DAB, respectively solving the inductive current and the transmission power of each mode according to an equivalent circuit model and a typical voltage waveform.
The equivalent circuit model consists of a primary full bridge, a secondary full bridge, a leakage inductance equivalent inductor, a high-frequency isolation transformer, a blocking capacitor and 4 bypass capacitors; the primary full bridge consists of 4 switching tubes and 4 antiparallel diodes; the secondary full bridge consists of 4 switching tubes and 4 anti-parallel diodes; the leakage inductance equivalent circuit is the sum of a high-frequency inductor and a transformer leakage inductance; the blocking capacitors are connected in series at two ends of the high-frequency isolation transformer.
Step 2: calculating peak values of the transmission power and the inductance current, namely current stress, under each mode, specifically including:
And calculating the peak value of the inductor current in each mode, and obtaining the transmission power of each mode by using the inductor current.
Step 3: performing numerical discrete optimization on the current stress in a corresponding transmission power range and a ZVS range to obtain an offline optimal control table; the method specifically comprises the following steps:
And taking the inductor current stress as an optimization target, carrying out discrete numerical optimization on the inductor current stress in a full power range by taking transmission power and a ZVS range as limiting conditions, and establishing an offline optimal control table.
Step 4: and carrying out current modulation on the two-level DAB by utilizing the actual control boundary and the optimized control table. The method specifically comprises the following steps:
And using the mode switching boundary and the optimization control table to enable the two-level DAB to generate corresponding direct-current bias voltages under the working mode of the corresponding mode so as to meet different input-output voltage ratios and finish current modulation.
On the basis of the technical scheme, the following embodiments are provided.
When input and output voltages are not matched based on the two-level DAB under the traditional phase-shifting control, particularly under the light load condition, the inductance current stress and the reflux power of the traditional phase-shifting control are larger, the on-state loss is increased, and the efficiency of the converter is seriously reduced.
The present embodiment is thus ready to solve the following problems: 1. the problem that the inductance current stress is larger when the two-level DAB is under light load under the traditional phase shift control; 2. the problem of large current stress under low voltage transformation ratio; 3. the traditional phase shift control has lower flexibility.
The embodiment discloses a modulation method for reducing inductance current of a two-level double-active-bridge converter. The topological structure of the transformer consists of a primary full bridge, a secondary full bridge, a leakage inductance equivalent inductor, a high-frequency isolation transformer, a blocking capacitor and 2 bypass capacitors; the primary full bridge consists of 4 switching tubes and 4 antiparallel diodes; the secondary full bridge consists of 4 switching tubes and 4 anti-parallel diodes; such a topology has device symmetry, simplifying the analysis of the transducer.
In general, an SPS modulation is commonly used as a control method of the converter, but when the input and output voltages are not matched with each other, the modulation has the problems of difficulty in realizing soft switching, overlarge current stress and the like, which seriously increases loss and reduces the efficiency of the converter. To improve this, the present embodiment employs a current modulation method combining pulse width modulation with phase shifting (Pulse Width Modulation WITH PHASE SHIFT, PWMPS). Compared with the traditional modulation methods such as SPS, PWMPS modulation in the embodiment adopts an asymmetric PWM control signal in the primary side two-level full bridge and adopts a symmetric PWM control signal in the secondary side full bridge. The blocking capacitor at the primary side and the secondary side are matched with the PWM signals, so that the problem of magnetic bias of the asymmetric PWM time-varying transformer is solved. Fig. 4 is a typical voltage operating waveform of two-level DAB with dc blocking capacitance in each mode under PWMPS control, where V 1 is the primary side input voltage, V 2 is the secondary side output voltage,For the phase difference between the primary and secondary bridges, D is the duty cycle of the primary switching tube, V AB is the primary side port voltage, V CD is the secondary side port voltage, and V cps and V cbs are the dc bias voltages on the blocking capacitors C ps and C bs.
In the scheme of the embodiment, C s does not generate direct current bias to the secondary side port voltage, and the direct current bias is considered to be 0 at the moment, and the secondary side port voltage has two voltage levels of positive and negative output bus voltage; c p generates direct current bias to the primary side port voltage, and the direct current bias is considered to be DV 1 at the moment, and the primary side port voltage has two voltage classes of positive and negative half output direct current bus voltage.
Firstly, dividing working areas of all modes; then analyzing the induction current stress and the transmission power under different modes, and performing discrete numerical optimization on the obtained induction current stress; and finally, the switch control of the two-level double-active bridge is completed through optimizing the control table.
In the scheme, the converter is controlled, and the converter can generate corresponding direct-current bias voltage to adapt to different input-output voltage ratios k under the corresponding working mode, so that ZVS of the full-switching tube is realized, and the switching loss of the converter can be greatly reduced; meanwhile, the converter is controlled based on the optimal control table, so that the current stress of the converter is reduced, the on-state loss is reduced, and the overall operation efficiency is improved on the premise of ensuring safe operation.
Thus, the above algorithm uses PWM modulation and inter-bridge phase shift angle to control the magnitude and direction of energy transfer. According to the power transmission requirement, an optimal working point is selected in an optimal working table, and when the inductance current stress is reduced, the transmission efficiency of the converter is improved. Meanwhile, the running cost of the converter is reduced, and the flexibility of the converter is improved.
Further, as the inverter control flow shown in fig. 1, the steps are respectively:
S1: dividing a two-level double-active-bridge converter into eight working modes through control signals, and solving inductance current and transmission power in each mode according to converter topology and switching signals;
s2: obtaining induction current stress and transmission power according to the induction current solved in the step S1;
s3: performing numerical optimization on stress in a full power range and a ZVS range to obtain an offline optimization control table;
S4: and the converter is controlled by optimizing the control table.
The control method provided by the embodiment increases the control degree of freedom of the duty ratio on the basis of the conventional phase shift control method. Under the premise, the scheme changes the duty ratio of the primary side switching tube of the converter to solve the problems that when the input and output voltage transformation ratios are not matched, the current stress is larger and soft switching is difficult to realize; performing numerical discrete optimization on the inductance current stress under different modes, and establishing an offline optimal control table; and finally, completing the control of the two-level double active bridge through an off-line optimal control table.
In the example, the control method based on PWM modulation can realize soft switching characteristics in a full power range when the input/output voltage transformation ratio is not matched with the ultra-light load; and the degree of freedom of control is increased, the flexibility of the converter is improved, the current stress is reduced, and the efficiency of the converter is improved. In addition, in the implementation patent, the DC bias can be generated through the DC blocking capacitor of the primary side and the secondary side of the transformer based on the control of the transformer, so that the situation that the transformer generates magnetic bias and cannot work normally when the duty ratio is not half-period is improved; and the converter is controlled based on the off-line optimal control table, so that the converter has good steady-state performance, and the overall efficiency is improved on the premise of ensuring the safe operation of the converter.
It should be noted that the two-level double active bridge converter topology is composed of a primary full bridge composed of 4 switching tubes (S 1-S8) and 4 antiparallel diodes (SD 1-SD4), a secondary full bridge composed of 4 switching tubes (Q 1-Q4) and 4 antiparallel diodes (QD 1-QD4), two bypass capacitors (C 1 and C 2), a leakage inductance equivalent inductance L, a high-frequency isolation transformer T, and blocking capacitors C p and C s connected in series with the former two-level double active bridge converter topology as shown in fig. 2. The input side direct current voltage source is V 1, the output side direct current voltage source is V 2, the transformer transformation ratio is n1, and the capacitance value of C 1 is the same as that of C 2.
In this embodiment, C s does not generate a voltage bias to the secondary side port voltage, and it is considered that the dc bias is 0 at this time; c p produces a voltage bias for the secondary side port voltage, which is considered dc offset DV 1 at this time.
The two-level double-active-bridge converter inductance current stress optimization control framework is shown in fig. 3, and specifically comprises the following steps:
The first step is to solve the instantaneous value of the inductance current and the transmission power of the two-level double-active-bridge converter based on the equivalent circuit model of the converter in the divided mode and the control signal waveform.
Further, the dividing mode refers to eight circuit working modes, specifically:
Dividing eight working modes according to the phase relation of the rising edges of the primary side output voltage and the secondary side output voltage of the two-level DAB; the operation modes of the two-level DAB include mode A, mode B, mode C, mode D, mode E, mode F, mode G and mode H.
The control method in this example is pulse width modulation in combination with inter-bridge phase shifting. The duty ratio of the primary side switching tube is D, and the phase shift angle between the bridges isThe variable control range of the eight modes is as follows,/>For pattern A,/>For pattern B,/>For pattern C,/>For pattern D,/>For pattern E,/>For pattern F,/>For pattern G,/>And the mode is H, and eight working modes are adopted.
The control quantity range is the whole operation range under the corresponding working mode, and is the natural operation range before optimization. Fig. 4 is a typical voltage waveform diagram of the corresponding mode under the control of the pulse width modulation method. The instantaneous value of the inductor current and the transmission power can be obtained in combination with fig. 4 and an equivalent circuit model, as shown in table 1.
Table 1 transmission power and inductor current for mode
And step two, according to the instantaneous value of the inductance current obtained in the step one, solving the inductance current stress and the transmission work of the converter by combining the current stress definition, and then solving the ZVS range.
It should be noted that the inductor current stress i * of the different mode is obtained on the basis of the equivalent circuit model of the corresponding mode, so that their expressions are as follows:
Mode a:
Mode B:
Mode C:
mode D:
mode E:
mode F:
mode G:
mode H:
in the above expression, the parameter k represents the input-output voltage transformation ratio, k=v 1/nV2, where n is the transformer transformation ratio.
It should be noted that, when the ZVS is implemented, current needs to flow through the anti-parallel diode before the switch tube is turned on, and the zero voltage conduction ranges of different modes are different, and when the mode a is analyzed as an example, at the time t 0, S 1 and S 4 are turned on, S 2 and S 3 are turned off, and the current on the equivalent inductor is less than or equal to zero at the time. At time t 1, Q 1 and Q 4 are on, Q 2 and Q 3 are off, and the current on the equivalent inductance is zero or more at this time to achieve ZVS. At time t 2, S 2 and S 3 are on, S 1 and S 4 are off, and ZVS is achieved when the current on the equivalent inductor is greater than or equal to zero. At time t 3, Q 2 and Q 3 are on, Q 1 and Q 4 are off, and the current on the equivalent inductance is less than or equal to zero at the time to realize ZVS. The soft switching boundary conditions for each mode were analyzed in the same manner and are shown in Table 2.
Table 2 soft switch boundary conditions for modes
And thirdly, taking the inductive current stress as an optimization target, taking the transmission power as a limiting condition, carrying out discrete numerical optimization on the inductive current stress in a full power range and a ZVS range, and establishing an offline optimization control table.
It should be noted that, the basic idea of discrete value optimization is to find an optimal operating point in the discretized operating region. The whole operation area is divided into grids by setting the control value measuring step length, so that the problem of solving the analysis solution of the optimal operation point by non-convex optimization is converted into a problem of numerical calculation comparison. The operating points are converted into a limited number through discretization, so that the transmission power and the current stress of each operating point in the operating area are solved, and the optimal operating point is obtained through comparison. FIG. 5 is a flowchart of an offline optimization algorithm.
And step four, determining an operation table according to k and P, determining the duty ratio of the converter by inquiring an off-line optimal control table, and adjusting the inter-bridge phase shift angle by a PI regulator to realize steady-state control of the converter. Fig. 6 is a control flow diagram of the controller performing the above method.
Finally, the program for realizing the control method is stored in the upper computer, and when the upper computer executes the program, the two-level double-active-bridge inductance current stress control method is realized.
It should be noted that, through this step, the system robustness and the dynamic response speed can be ensured while the system steady-state control requirement is achieved.
In order to further explain the technical scheme of the invention, the technical effect is highlighted, a two-level double-active-bridge converter experimental platform based on a pulse width modulation method and a phase shift modulation method is built, and parameters of the experimental platform are shown in table 3:
Table 3 two level double active bridge converter experiment platform parameters
| Input voltage V 1 | 200V |
| Output voltage V 2 | 100V |
| Transformer transformation ratio n | 0.5 |
| Equivalent leakage inductance L | 269μH |
| Switching frequency f s | 10kHz |
| Maximum transmission power P base | 915.36W |
| Dc blocking capacitor C p、Cs | 1600μF |
By giving the same transmission power P and input-output voltage modulation ratio k, the method provided by the invention is ensured to be consistent with the testing working conditions of two traditional modulation methods, namely SPS and DPS, and the induction current stress of the three methods is measured.
Table 4 experimental comparison of the present modulation method with the conventional modulation method
The experimental result shows that the modulation method implemented in this example can make all the switching tubes realize zero-voltage conduction. According to the experimental results of table 4, it can be seen that compared with the single phase shift control and the double phase shift control, the modulation method of the embodiment can effectively reduce the inductance current stress and the current stress when the converter works in the light load state, thereby greatly reducing the conduction loss. Fig. 7 is an efficiency curve under three control strategies.
As can be seen from fig. 7, the modulation method of the present embodiment can effectively improve the efficiency of the converter compared to the SPS and DPS control methods.
In addition, the invention also provides a memory electronic device, which comprises a memory and a processor, wherein the memory is used for storing a controller execution program, and the processor is used for executing the controller execution program to enable the memory electronic device to execute the current modulation method of the two-level DAB.
Furthermore, the present invention provides a computer-readable storage medium storing a computer-executable program which, when executed by a processor, implements the current modulation method of two-level DAB as described above.
In the present specification, each embodiment is described in a progressive manner, and each embodiment is mainly described in a different point from other embodiments, and identical and similar parts between the embodiments are all enough to refer to each other.
The principles and embodiments of the present invention have been described herein with reference to specific examples, the description of which is intended only to assist in understanding the core concept of the invention; also, it is within the scope of the present invention to be modified by those of ordinary skill in the art in light of the present teachings. In view of the foregoing, this description should not be construed as limiting the invention.
Claims (8)
1. A method of current modulation of two-level DAB comprising:
dividing a current operation mode of two-level DAB with a blocking capacitor, and determining an inductance current and a transmission power in the current operation mode; the current operation modes include all eight modes;
Calculating the peak value of the inductive current, namely the inductive current stress, in each mode, and carrying out numerical discrete optimization on the current stress in a corresponding transmission power range and a zero voltage opening range to obtain an off-line optimal control table;
and carrying out current modulation on the two-level DAB by utilizing the optimized control table.
2. The method for modulating the current of the two-level DAB according to claim 1, wherein the dividing the current operation mode of the two-level DAB to determine the inductor current and the transmission power in the current operation mode comprises the following steps:
Dividing eight working modes according to the phase relation of the rising edges of the primary side output voltage and the secondary side output voltage of the two-level DAB; the working modes of the two-level DAB comprise a mode A, a mode B, a mode C, a mode D, a mode E, a mode F, a mode G and a mode H;
Based on the divided working modes of the two-level DAB, respectively solving the inductive current and the transmission power under each mode according to an equivalent circuit model and a typical voltage waveform.
3. The method for modulating the current of the two-level DAB according to claim 2, wherein the equivalent circuit model is composed of a primary full bridge, a secondary full bridge, a leakage inductance equivalent inductance, a high-frequency isolation transformer, a blocking capacitor and 2 bypass capacitors; the primary full bridge consists of 4 switching tubes and 4 antiparallel diodes; the secondary full bridge consists of 4 switching tubes and 4 anti-parallel diodes; the leakage inductance equivalent circuit is the sum of a high-frequency inductor and a transformer leakage inductance; the blocking capacitors are connected in series at two ends of the high-frequency isolation transformer.
4. The method of two-level DAB current modulation according to claim 1, wherein calculating the peak values of the transmission power and inductor current, i.e., the current stress, in each mode comprises:
And calculating the instantaneous values of the transmission power and the inductive current under each mode, comparing to obtain an inductive current peak value, namely current stress, and obtaining the transmission power of each mode by utilizing the inductive current.
5. The method for modulating the current of the two-level DAB according to claim 1, wherein the performing numerical discrete optimization on the current stress in the corresponding transmission power range and zero voltage on range to obtain an off-line optimal control table specifically comprises:
and taking the current stress of the inductive current as an optimization target, carrying out discrete numerical optimization on the inductive current stress in a full power range and a zero voltage opening range by taking transmission power as a limiting condition, and establishing an offline optimal control table.
6. The method for current modulation of two-level DAB according to claim 1, characterized in that said two-level DAB is current modulated by means of said optimal control table, comprising in particular:
And using the optimized control table to enable the two-level DAB to generate corresponding direct-current bias voltage under a corresponding working mode so as to adapt to different duty ratios and finish current modulation.
7. A memory electronic device comprising a memory for storing a controller-executable program and a processor that runs the controller-executable program to cause the memory electronic device to perform the two-level DAB current modulation method as recited in claims 1-6.
8. A computer-readable storage medium, characterized in that it stores a computer-executable program which, when executed by a processor, implements the two-level DAB current modulation method as claimed in claims 1-6.
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