CN117543174A - Broadband frequency division duplexer - Google Patents
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Abstract
The invention discloses a broadband frequency division duplexer, which comprises: the LC series resonance grounding network is respectively connected in parallel with the combination port and the low-pass port or the high-pass port, the transformer T and the resistor R are connected in a bridging manner between serial nodes of the LC series resonance grounding network, the serial nodes of the transformer T and the resistor R are connected with the grounding reactance element, and the reactance element is connected in a bridging manner between the combination port and the low-pass port or the high-pass port. The broadband frequency division duplexer provided by the invention consists of 4 basic passive elements including a resistor, a capacitor, an inductor and a transformer, and has the characteristics of full-frequency band matching of three port impedances and excellent isolation performance between two shunt ports.
Description
Technical Field
The invention relates to the field of radio frequency electronic components, in particular to a broadband frequency division duplexer.
Background
In order to simplify the design of the radio communication device, a scheme that the transceiving links share one antenna is commonly adopted. In order to realize real-time two-way communication, the receiving and transmitting links are selected from different frequency channels, isolation between the receiving and transmitting links is realized through a frequency division duplexer, and the receiving and transmitting links are coupled to the same pair of antennas. Modern mobile communication devices, such as mobile phones, typically support multiple communication standards operating on different frequency channels, and therefore require frequency division or combining for multiple transmit and receive links, which requires the use of multiple frequency division duplexers.
The core function of the frequency division duplex is to split or combine the receiving and transmitting links of two different frequency channels and to provide isolation for the two channels so as to prevent the mutual influence between the circuits.
Most of the existing frequency division duplex devices adopt two filters with non-overlapping pass bands to be connected together through a T-shaped interface circuit, so as to construct a three-port network: in the shunt port, the port frequency domain characteristics are consistent with the port frequency domain characteristics of the connected filter, so that the passband is internally matched and the passband is externally mismatched; in the combining port, the port frequency domain characteristics of the combining port are shown as being matched in the pass bands of the two filters, and other frequency ranges are mismatched; the isolation between the split ports is related to the decoupling performance of the T-interface circuit and the rejection capability of each filter out-of-band to another channel.
The frequency division duplex constructed by the dual band-pass filter can be regarded as a narrow-band duplex, is strongly constrained by the bandwidth of the band-pass filter, has no reconfigurability or reusability, and can only meet the branching or combining of two specific channel signals. When a frequency division multiplexer needs to be built, a plurality of bandpass filters are required, and the design of a plurality of filter decoupling circuits is very complex.
From the perspective of electromagnetic compatibility, it is advantageous for the receiving channel to integrate the filter with the frequency division diplexer, but for the transmitting channel the filter should be placed close to the transmitting source, and when the transmitting source and the frequency division diplexer cannot be closely laid out, a filter must be added closely to suppress out-of-band emissions from the transmitting source, thereby increasing the complexity of the system design. Therefore, a narrowband frequency division duplexer constructed with a band pass filter objectively reduces flexibility in system design.
The frequency division diplexer built up from a combination of high and low pass filters has a wideband characteristic, both filters having the same 3dB cut-off frequency f c The frequency is the frequency division point. The single-tone signal injected into the combining port reaches the two split ports at the dividing point with equal power, that is, at the dividing point f c The wideband frequency division diplexer is equivalently a 3dB power divider.
This wideband frequency division duplex can be realized with a low-order butterworth-type filter. For example, in the book "RF Design Guide-Systems, circuits and Equations" published by ARTECH HOUSE, science and technology book Press in 1995, the authors, wittz Muller, have given a wideband frequency division diplexer Design with a division point of 100MHz, the circuit configuration and component parameters of which are shown in FIG. 1.
Modeling and simulating the circuit design, we can intuitively see the electrical performance of the wideband frequency division duplex, as shown in fig. 2A and 2B.
In fig. 2A, S21 is a transmission coefficient between the combining port and the low-pass port, S31 is a transmission coefficient between the combining port and the high-pass port, and S32 is a transmission coefficient between the low-pass port and the high-pass port. m1 is a reading mark, and as can be seen from the reading of m1, the 3dB cut-off frequency of the two frequency division filters is 100.8MHz, and the isolation between the two branch ports is equal to the superposition of the insertion loss of the two filters at the same frequency.
S11, S22, and S33 in fig. 2B are reflection coefficients of the combining port, the low-pass port, and the high-pass port, respectively. Obviously, the combined port shows good matching characteristics in the full frequency band, and the split port has good matching performance in the passband region with small insertion loss, but the reflection coefficient gradually worsens along with the increase of the insertion loss when the passband is transited to the stopband. At the frequency division point of 100.8MHz, the return loss of both branch ports is about-6 dB.
The broadband frequency division duplex can provide wide matching bandwidth in the pass bands of three ports, and the split ports can increase isolation among the ports by cascading corresponding band-pass filters. Obviously, the design of separating the duplexer from the filter improves the flexibility of the system design and also reduces the requirement on the out-of-band rejection performance of the cascade filter.
At the same time, however, the isolation and reflection coefficient of the shunt port are seriously deteriorated near the division point of the wideband frequency division duplex, resulting in difficulty in utilization of this frequency band.
At the frequency division point f c The wideband frequency division duplexer is equivalent to a 3dB power divider, and according to the law of conservation of energy, the matching performance of the shunt ports near the frequency division point cannot be improved by increasing the overlapping area of the two filters, so that the isolation between the two shunt ports is deteriorated.
Steepening the transition band by increasing the order of the two filters can compress the unusable bandwidth around the division point at the cost of increasing the design complexity of the diplexer and the number of circuit elements and cannot fundamentally solve the problem.
Substitution of chebyshev or elliptic function filters with steep transition band characteristics for butterworth filters also enables to compress the unavailable bandwidth around the division point, but in fact, chebyshev or elliptic function filters of the same order are all more complex than butterworth filters and as such do not fundamentally solve the problem.
Up to now, no prior art has been found that can fundamentally solve the problem of unavailable frequency bands near the division point of a wideband frequency division duplex. Under the condition that the radio frequency band spectrum resources in the radio communication field are abnormally tense, the existing broadband frequency division duplex is difficult to meet the application requirement of narrow channel interval, or the application of the existing broadband frequency division duplex has the serious problem of spectrum resource waste.
Disclosure of Invention
The invention discloses a broadband frequency division duplex aiming at the problems of poor multiplexing property of the band-pass duplex and serious spectrum resource waste of the existing broadband frequency division duplex.
The technical scheme of the broadband frequency division duplex device comprises a combining port, a low-pass port and a high-pass port; the combining port is connected in parallel with a first LC series resonance grounding network; the low-pass port is connected in parallel with a second LC series resonance grounding network; the transformer T and the resistor R are connected across the series nodes of the first LC series resonance grounding network and the second LC series resonance grounding network; a series node of the transformer T and the resistor R is connected with a grounding reactance element; a reactance element is connected between the combining port and the low-pass port.
Further, the combined port and the low-pass port have the same impedance, and the impedance value of the combined port is equal to the value of the resistor R.
Further, the inductance and capacitance of the first LC series resonance grounding network connected in parallel with the combining port and the second LC series resonance grounding network connected in parallel with the low-pass port are the same, so that the series resonance angular frequency omega of the two LC series resonance grounding networks is achieved 0 The same; the capacitor ends of the two LC series resonance grounding networks are respectively connected with a combining port and a low-pass port, and the inductor ends of the two LC series resonance grounding networks are grounded; the value of the inductor in the two LC series resonant ground networks is l=r +.ω 0 The capacitor has a value of c=1/(r·ω) 0 )。
Further, one end of the secondary coil of the transformer T is connected with a series node of the first LC series resonance grounding network; one end of the resistor R is connected with a series node of the second LC series resonance grounding network; the other end of the secondary coil of the transformer T is connected with the other end of the resistor R in series; the primary winding of the transformer T is connected to the high-pass port.
Further, the grounding reactance element connected to the series node of the transformer T and the resistor R is at least one capacitor, and the value of the capacitor is 2 times that of the capacitor in the first LC series resonant ground network or the second LC series resonant ground network.
Further, the reactance element connected across the combining port and the low-pass port is at least one inductor, and the value of the inductor is 2 times that of the inductor in the first LC series resonant ground network or the second LC series resonant ground network.
The technical scheme of the invention provides another broadband frequency division duplexer which comprises a combining port, a low-pass port and a high-pass port; the combining port is connected in parallel with a first LC series resonance grounding network; the high-pass port is connected in parallel with a second LC series resonance grounding network; the transformer T and the resistor R are connected across the series nodes of the first LC series resonance grounding network and the second LC series resonance grounding network; a series node of the transformer T and the resistor R is connected with a grounding reactance element; a reactance element is bridged between the combining port and the high-pass port.
Further, the combined port and the high-pass port have the same impedance, and the impedance value of the combined port is equal to the value of the resistor R.
Further, the inductance and capacitance of the first and second LC series resonance grounding networks are the same, so that the series resonance angular frequency omega of the two LC series resonance grounding networks 0 The same; the inductor ends of the two LC series resonance grounding networks are respectively connected with a combining port and a high-pass port, and the capacitor ends of the two LC series resonance grounding networks are grounded; the value of the inductor in the two LC series resonant ground networks is l=r/ω 0 The capacitor has a value of c=1/(r·ω) 0 )。
Further, one end of the secondary coil of the transformer T is connected with a series node of the first LC series resonance grounding network; one end of the resistor R is connected with a series node of the second LC series resonance grounding network; the other end of the secondary coil of the transformer T is connected with the other end of the resistor R in series; the primary winding of the transformer T is connected to the low-pass port.
Further, the grounding reactance element connected to the series node of the transformer T and the resistor R is at least one inductor, and the value of the inductor is 2 times that of the inductor in the first LC series resonant ground network or the second LC series resonant ground network.
Furthermore, the reactance element connected across the combining port and the low-pass port is at least one capacitor, and the value of the capacitor is 2 times that of the capacitor in the first LC series resonance grounding network or the second LC series resonance grounding network.
Compared with the prior duplexer technical scheme, the beneficial effect of the scheme is that:
first is the operating frequency bandwidth. The three ports are all broadband matching, and the phenomenon of deterioration of reflection coefficient and isolation degree does not exist near the frequency division point, so that the defect of the existing frequency division duplexer is overcome.
Secondly, the application is simple and convenient, and the reconfigurability or reusability is strong; the isolation between the branch ports is high, and the isolation can be improved without integrating or cascading band-pass filters; meanwhile, the cascade structure multiplexer is very convenient, and the design is obviously simplified and the cost is reduced.
Thirdly, the port integrated transformer has strong applicability. The two configurations adopt transformers as interface elements at the low-pass port and the high-pass port respectively, so that single-ended/differential signal interconnection, impedance transformation, phase inversion and the like are realized conveniently.
And fourthly, the integrated circuit consists of 4 basic passive elements, namely a resistor, a capacitor, an inductor and a transformer, and is suitable for monolithic integration manufacture.
Drawings
FIG. 1 is a prior art 100MHz division point wideband frequency division duplexer;
FIGS. 2A and 2B are diagrams illustrating the electrical performance of a prior art 100MHz division point broadband frequency division duplexer;
fig. 3A is a circuit diagram of a wideband frequency division duplexer of a configuration disclosed in the present invention;
fig. 3B is a circuit diagram of a B-configuration wideband frequency division duplexer of the present disclosure;
FIGS. 4A and 4B show the electrical performance of a 100MHz band division point broadband frequency division duplexer in accordance with the configuration design of the present invention;
FIGS. 5A and 5B are diagrams illustrating the electrical performance of a wideband frequency division diplexer with a 100MHz cut point designed in the configuration of the present invention;
fig. 6A-6E are schematic diagrams of a quad-multiplexer constructed using the diplexer cascade of the present invention.
Detailed Description
It should be understood that the detailed description and specific examples are intended for purposes of illustration only and are not intended to limit the scope of the invention.
The wideband frequency division diplexer disclosed in the present invention is divided into two basic configurations, as shown in fig. 3A and 3B, respectively representing a configuration and B configuration. Both configurations are composed of at least 6 reactance elements, 1 resistance element and 1 transformer, Z0 and Z1 are characteristic impedances of the ports, and n is the primary to secondary coil turns ratio of the transformer.
In the a configuration, the inductor L31a is connected across the junction port and the low-pass port; the combining port is connected in parallel with a first series resonance grounding network formed by C31a and L32a, and the low-pass port is connected in parallel with a second series resonance grounding network formed by C32a and L33 a; one end of a secondary coil of the transformer T31a is connected to a series node of a first LC series resonance grounding network of the combining port, one end of a resistor R31a is connected to a series node of a second LC series resonance grounding network of the low-pass port, and the other end of the secondary coil of the transformer T31a is connected with the other end of the resistor R31a and is grounded through a capacitor C33 a; the primary side of the transformer T31a is a high-pass port.
The parameter values of the elements in the a configuration are constrained as follows:
R31a＝R
C31a＝G32a＝C
C33a＝2C
L31a＝2L
L32a＝L33a＝L
wherein the method comprises the steps of
L＝R/ω 0
C＝1/(R·ω 0 )
Wherein omega is 0 The value of the series resonance angular frequency is LC and the value of the series resonance angular frequency is frequency division point angular frequency omega c ＝(2π·f c ) 1.5 times of (2).
At this time, for any angular frequency ω, the input impedances of the a-configuration combining port and the low-pass port are
Z0(ω)＝R
a-configuration high-pass port input impedance is
Z1(ω)＝n 2 ·R
The difference between configuration b and configuration a is that the inductor and capacitor in the circuit are interchanged, while the shunt port is also interchanged.
In the b configuration, the capacitor C31b is connected across the junction port and the high-pass port; the combining port is connected in parallel and forms a first series resonance grounding network by L31b and C32b, and the high-pass port is connected in parallel and forms a second series resonance grounding network by L32b and C33 b; one end of a secondary coil of the transformer T31b is connected to a series node of a first LC series resonance grounding network of the combining port, one end of a resistor R31b is connected to a series node of a second LC series resonance grounding network of the high-pass port, and the other end of the secondary coil of the transformer T31b is connected with the other end of the resistor R31b and is grounded through an inductor L33 b; the primary side of the transformer T31b is a low-pass port.
The parameter values of the elements in the b configuration are constrained as follows:
R31b＝R
C31b＝2C
C32b＝C33b＝C
L31b＝L32b＝L
L33b＝2L
wherein the method comprises the steps of
L＝R/ω 0
C＝1/(R·ω 0 )
Wherein omega is 0 The LC series resonance angular frequency is the frequency division point angular frequency omega c ＝(2π·f c ) 2/3 times that of (C).
At this time, for any angular frequency omega, the input impedance of the b-configuration combining port and the high-pass port is
Z0(ω)＝R
b-configuration low-pass port input impedance is
Z1(ω)＝n 2 ·R
On the premise of meeting the conditions, when the value of the resistor R is equal to the characteristic impedance Z0 of the application network, the three ports of the a and b configuration broadband frequency division duplex can realize broadband matching. This means that there is no phenomenon that the reflection coefficient is deteriorated in all three ports in the vicinity of the division point.
The wideband frequency division duplexer disclosed by the invention is composed of 4 basic passive elements, namely a resistor, a capacitor, an inductor and a transformer, the representation of the 4 passive elements in fig. 3A and 3B adopts a schematic diagram symbol form, the representation is not limited to be realized in a lumped element form, and any equivalent circuit form can be used for realizing the wideband frequency division duplexer, such as lumped, distributed or mixed parameter element forms in the manufacturing process of LTCC (low temperature cofired ceramic), MEMS (micro-electromechanical system), thick film printed circuit or MMIC (microwave integrated circuit).
The features and advantages of the invention are further illustrated by the following 3 specific examples.
Example 1:
as shown in fig. 3A, a 50 Ω characteristic impedance wideband frequency division duplexer with a division point of 100MHz designed in the a configuration is provided.
According to the foregoing, the LC series resonant frequency should be 150MHz, and the inductance L and the capacitance C are calculated respectively, and the inductance L is 53nH and the capacitance C is 21pF. Through modeling simulation, the electrical performance of the 100MHz frequency division point broadband frequency division duplex designed by the configuration a of the invention is shown in fig. 4A and 4B.
In fig. 4A, S21 is a transmission coefficient between the combined port and the low-pass port, S31 is a transmission coefficient between the combined port and the high-pass port, and S32 is a transmission coefficient between the low-pass port and the high-pass port. As can be seen from comparison of FIG. 2A, the out-of-band rejection capability of the branching ports is not as strong as that of the broadband frequency division duplex device in the existing design form, but the isolation between the branching ports is obviously much higher, the isolation is worst at the frequency division point, but is also over 50dB, the attenuation is obviously lower than the stop band attenuation of the filter, and the engineering application is completely satisfied, so that the isolation is not improved by cascading the filter, and the system design can be simplified.
In fig. 4B, S11, S22, and S33 are reflection coefficients of the combining port, the low-pass port, and the high-pass port, respectively. The reflection coefficient curves of the three ports can be completely overlapped, and the reflection coefficient curves are below-45 dB, which indicates that all the ports are matched in full frequency range, and the matching performance is excellent.
The isolation between the shunt ports does not reach an infinite high, and the reflection coefficient of each port does not reach an infinite low ideal matching state, because the capacitance and inductance obtained by calculation are rounded in the design process, and thus deviate from the optimal theoretical value.
The configuration a of the invention solves the problems of poor isolation and deteriorated reflection coefficient near the frequency division point of the broadband frequency division duplex device in the prior form by comparing the isolation performance among the branch ports with the matching performance of each port.
Example 2:
as shown in fig. 3B, a frequency division point designed in the B configuration is also a 50 Ω characteristic impedance wideband frequency division diplexer of 100 MHz.
According to the foregoing, the LC series resonant frequency was about 67MHz, and the inductance L and the capacitance C were calculated, respectively, and rounded to obtain an inductance L of 119nh and a C of 48pF. Through modeling simulation, the electrical performance of the 100MHz frequency division point broadband frequency division duplex designed by the configuration B of the invention is shown in fig. 5A and 5B.
In fig. 5A, S21 is a transmission coefficient between the combining port and the high-pass port, S31 is a transmission coefficient between the combining port and the low-pass port, and S32 is a transmission coefficient between the low-pass port and the high-pass port. Similar to the electrical performance of the a-configuration design, the out-of-band rejection capability of the b-configuration design shunt port is not as strong as that of the existing design mode frequency division duplexer, but the isolation between the shunt ports is obviously much higher, the isolation is worst at the frequency division point, and is also over 50dB, which is obviously lower than the stop band attenuation of the filter, and the engineering application requirement is completely satisfied.
In fig. 5B, S11, S22, and S33 are reflection coefficients of the combining port, the low-pass port, and the high-pass port, respectively. The reflection coefficient curves of the three ports can be completely overlapped, and the full frequency band matching of each port is illustrated below-45 dB, and the matching performance is excellent, so that the problems of poor isolation and deteriorated reflection coefficient near the frequency division point of the broadband frequency division duplex in the prior form are fundamentally solved, and the cascade filter is not needed to improve the isolation.
Example 3:
a quad-multiplexer is constructed using the wideband frequency division diplexer of the present invention.
The duplexer is used for constructing a quadruplex, at least three duplexers with different frequency division points are needed, the frequency division points of the three broadband frequency division duplexers are respectively f1, f2 and f3, wherein f1 is smaller than f2 and smaller than f3, and because the three ports of the duplexer are all broadband matched, the impedance characteristics of front-stage and rear-stage circuits are not affected by direct cascading.
According to the frequency relation of the frequency division points, the frequency division point of the rear-stage duplexer is required to be positioned in the passband of one of the branch ports of the front-stage duplexer, and the combining ports of the rear-stage duplexer can be directly cascaded corresponding to the branch port of the front-stage duplexer. According to this rule, the quadplexer may have a variety of cascaded construction schemes, as shown in FIGS. 6A-6E.
In the figure, CH1, CH2, CH3 and CH4 are 4 channels to be split or combined by the quad, and as long as the operating frequencies defined by the 4 channels meet the following conditions, the quad can be used to meet the splitting or combining application:
CH1 defines an operating frequency range less than f1;
CH2 defines an operating frequency range greater than f1 and less than f2;
CH3 defines an operating frequency range greater than f2 and less than f3;
CH4 defines an operating frequency range greater than f3.
The embodiment shows that the broadband frequency division duplex disclosed by the invention has very flexible reconfigurable characteristics, and is very convenient for designers to optimize circuit layout in actual work. If the multiplexer is used for combining the radio frequency signals of multiple different channels, the radio frequency signals are transmitted through one broadband cable (such as a radio frequency coaxial cable) and then are split by the multiplexer, so that the number of radio frequency interconnection cables between the whole radio frequency signals or the radio frequency interconnection cables between the radio frequency communication systems can be obviously reduced, the cost is reduced, and the maintenance convenience is improved.
The foregoing description of the preferred embodiments of the invention is not intended to be limiting, but rather is intended to cover all modifications, equivalents, and alternatives falling within the spirit and principles of the invention.
Claims (13)
1. A wideband frequency division duplexer, comprising: a combiner port, a low pass port and a high pass port.
2. The combining port is connected with a first LC series resonance grounding network in parallel;
the low-pass port is connected with a second LC series resonance grounding network in parallel;
the transformer T and the resistor R are connected between the series nodes of the first LC series resonance grounding network and the second LC series resonance grounding network in a bridging way;
a grounding reactance element is connected to a series node of the transformer T and the resistor R;
and a reactance element is connected between the combining port and the low-pass port.
3. The wideband frequency division duplex according to claim 1, wherein said combining port and said low-pass port have the same impedance, and the impedance value is equal to the value of said resistor R.
4. The wideband frequency division duplex according to claim 1, wherein inductance and capacitance of said first LC series resonant ground network connected in parallel to said combining port and said second LC series resonant ground network connected in parallel to said low pass port are the same, thereby making the series resonant angular frequency ω of both said LC series resonant ground networks equal 0 The same; the two LC series resonance grounding networksThe capacitor end is respectively connected with the combining port and the low-pass port, and the inductor ends of the two LC series resonance grounding networks are grounded; the value of the inductor in the two LC series resonance grounding networks is L=R/omega 0 The capacitor has a value of c=1/(r·ω) 0 )。
5. A wideband frequency division duplex according to claim 1, wherein one end of the secondary winding of the transformer T is connected to a series node of the first LC series resonant ground network; one end of the resistor R is connected with a series node of the second LC series resonance grounding network; the other end of the secondary coil of the transformer T is connected with the other end of the resistor R in series; the primary coil of the transformer T is connected with the high-pass port.
6. The wideband frequency division duplex according to claim 1, wherein said grounding reactance element connected at a series node of said transformer T and said resistor R is at least one capacitor, said capacitor having a value of 2 times the value of a capacitor in said any LC series resonant ground network.
7. The wideband frequency division duplex according to claim 1, wherein said reactance element connected across said combining port and said low pass port is at least one inductor, said inductor having a value of 2 times the value of an inductor in said any LC series resonant ground network.
8. A wideband frequency division duplexer, comprising: a combining port, a low-pass port and a high-pass port;
the combining port is connected with a first LC series resonance grounding network in parallel;
the high-pass port is connected in parallel with a second LC series resonance grounding network;
the transformer T and the resistor R are connected between the series nodes of the first LC series resonance grounding network and the second LC series resonance grounding network in a bridging way;
a grounding reactance element is connected to the series node of the transformer T and the resistor R;
and a reactance element is bridged between the combining port and the high-pass port.
9. The wideband frequency division duplex according to claim 7, wherein said combining port and said high-pass port have the same impedance, and the impedance value is equal to the value of said resistor R.
10. The wideband frequency division duplex according to claim 7, wherein inductance and capacitance of said first LC series resonant ground network and said second LC series resonant ground network are the same, thereby providing a series resonant angular frequency ω of both said LC series resonant ground networks 0 The same; the inductor ends of the two LC series resonance grounding networks are respectively connected with the combining port and the high-pass port, and the capacitor ends of the two LC series resonance grounding networks are grounded; the value of the inductor in the two LC series resonance grounding networks is L=R/omega 0 The capacitor has a value of c=1/(r·ω) 0 )。
11. The wideband frequency division duplex according to claim 7, wherein one end of the secondary winding of the transformer T is connected to a series node of the first LC series resonant ground network; one end of the resistor R is connected with a series node of the second LC series resonance grounding network; the other end of the secondary coil of the transformer T is connected with the other end of the resistor R in series; the primary coil of the transformer T is connected with the low-pass port.
12. The wideband frequency division duplex according to claim 7, wherein said grounding reactance element connected at a series node of said transformer T and said resistor R is at least one inductor, said inductor having a value of 2 times the value of an inductor in said any LC series resonant ground network.
13. The wideband frequency division duplex according to claim 7, wherein said reactance element connected across said combining port and said low pass port is at least one capacitor, said capacitor having a value that is 2 times the value of a capacitor in said any LC series resonant ground network.
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2005073199A (en) * | 2003-08-28 | 2005-03-17 | Hitachi Kokusai Electric Inc | High-speed tuner antenna multiplexer |
| CN1620754A (en) * | 2002-01-22 | 2005-05-25 | M/A-Com公司 | Improved quadrature hybrid and improved vector modulator in a chip scale package using same |
| US20060229035A1 (en) * | 2005-04-07 | 2006-10-12 | Hitachi Metals, Ltd. | High-frequency circuit and communications apparatus comprising same |
| CN1901437A (en) * | 2006-07-26 | 2007-01-24 | 上海华为技术有限公司 | Communication system duplexer and multiplexer and duplexer and multiplexer method |
| CN101297479A (en) * | 2005-11-03 | 2008-10-29 | 诺基亚公司 | Method and arrangement for performing analog signal processing and measuring between a signal source and a load |
| US20120256702A1 (en) * | 2011-04-05 | 2012-10-11 | Rf Micro Devices, Inc. | Tunable duplexer method using hybrid transformer with dual antenna |
| US20140204806A1 (en) * | 2013-01-18 | 2014-07-24 | Siliconware Precision Industries Co., Ltd. | Duplexer, circuit structure thereof and rf transceiver apparatus comprising the duplexer |
| CN106664070A (en) * | 2015-03-25 | 2017-05-10 | 株式会社村田制作所 | Phase shifter, impedance matching circuit, multiplexer/demultiplexer and communication terminal device |
| CN111200419A (en) * | 2020-01-16 | 2020-05-26 | 诺思(天津)微系统有限责任公司 | Filter, duplexer, high-frequency front-end circuit and communication device |
| CN111756386A (en) * | 2019-03-28 | 2020-10-09 | 株式会社村田制作所 | Front-end circuit and communication device |
| CN113475002A (en) * | 2019-02-14 | 2021-10-01 | 瑞典爱立信有限公司 | Differential combination circuit |
| US20230036705A1 (en) * | 2020-01-31 | 2023-02-02 | The Texas A&M University System | An Ultra-Wide Bandwidth Ultra-Isolation DC-100 Gigahertz Front-End Module with Integrated Duplexer, Low Noise Amplifier, and Power Amplifier for Wireless Communication Applications |
-
2023
- 2023-12-25 CN CN202311797350.0A patent/CN117543174B/en active Active
Patent Citations (12)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1620754A (en) * | 2002-01-22 | 2005-05-25 | M/A-Com公司 | Improved quadrature hybrid and improved vector modulator in a chip scale package using same |
| JP2005073199A (en) * | 2003-08-28 | 2005-03-17 | Hitachi Kokusai Electric Inc | High-speed tuner antenna multiplexer |
| US20060229035A1 (en) * | 2005-04-07 | 2006-10-12 | Hitachi Metals, Ltd. | High-frequency circuit and communications apparatus comprising same |
| CN101297479A (en) * | 2005-11-03 | 2008-10-29 | 诺基亚公司 | Method and arrangement for performing analog signal processing and measuring between a signal source and a load |
| CN1901437A (en) * | 2006-07-26 | 2007-01-24 | 上海华为技术有限公司 | Communication system duplexer and multiplexer and duplexer and multiplexer method |
| US20120256702A1 (en) * | 2011-04-05 | 2012-10-11 | Rf Micro Devices, Inc. | Tunable duplexer method using hybrid transformer with dual antenna |
| US20140204806A1 (en) * | 2013-01-18 | 2014-07-24 | Siliconware Precision Industries Co., Ltd. | Duplexer, circuit structure thereof and rf transceiver apparatus comprising the duplexer |
| CN106664070A (en) * | 2015-03-25 | 2017-05-10 | 株式会社村田制作所 | Phase shifter, impedance matching circuit, multiplexer/demultiplexer and communication terminal device |
| CN113475002A (en) * | 2019-02-14 | 2021-10-01 | 瑞典爱立信有限公司 | Differential combination circuit |
| CN111756386A (en) * | 2019-03-28 | 2020-10-09 | 株式会社村田制作所 | Front-end circuit and communication device |
| CN111200419A (en) * | 2020-01-16 | 2020-05-26 | 诺思(天津)微系统有限责任公司 | Filter, duplexer, high-frequency front-end circuit and communication device |
| US20230036705A1 (en) * | 2020-01-31 | 2023-02-02 | The Texas A&M University System | An Ultra-Wide Bandwidth Ultra-Isolation DC-100 Gigahertz Front-End Module with Integrated Duplexer, Low Noise Amplifier, and Power Amplifier for Wireless Communication Applications |
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| CN117543174B (en) | 2024-06-21 |
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