CN117254252A - Magneto-electric dipole antenna and antenna array - Google Patents

Abstract

The present disclosure provides a magneto-electric dipole antenna and an antenna array, which belong to the technical field of communication. The magneto-electric dipole antenna comprises a substrate, a floor, a first patch, a second patch, a shorting strap, a first conductive member and a second conductive member. The floor is located the first surface of base plate, and first paster and second paster are located the second surface of base plate, and the interval is arranged. The both ends of short-circuit area are connected with first paster and second paster respectively, and separate the gap between first paster and the second paster into first gap and second gap. The first conductive part penetrates through the substrate and is connected with the first patch and the floor, and the second conductive part penetrates through the substrate and is connected with the second patch and the floor. The magnetic electric dipole antenna provided by the disclosure has the electric dipole and the magnetic dipole which are orthogonally placed, so that wide beams can be formed on the H plane and the E plane simultaneously, and the short circuit band is connected with two patches, so that the current distribution on the patches is disturbed, and the impedance bandwidth of the magnetic electric dipole antenna is widened.

Description

Magneto-electric dipole antenna and antenna array

Technical Field

The present disclosure relates to the field of communications technologies, and in particular, to a magneto-electric dipole antenna and an antenna array.

Background

The beam width of an antenna refers to the angle between two points at which the radiation intensity decreases by 3dB on both sides of the maximum radiation beam of the antenna. The beam width of the antenna can be divided into a beam width in the E plane and a beam width in the H plane, wherein the E plane and the H plane are perpendicular to each other.

In many applications such as wireless communication, under the condition of maintaining good directional radiation characteristics and a certain gain of an antenna, the antenna is generally required to realize a wide beam on the E plane and the H plane at the same time, so that the antenna can radiate and receive wireless communication signals in a larger spatial range.

Therefore, how to make the antenna realize a wide beam on the E plane and the H plane simultaneously is a technical problem worthy of research.

Disclosure of Invention

The present disclosure provides a magneto-electric dipole antenna and an antenna array, and the magneto-electric dipole antenna provided by the present disclosure has orthogonally placed electric dipoles and magnetic dipoles, so that a wide beam can be formed simultaneously on an H plane and an E plane, and a short-circuit band connects a first patch and a second patch, which perturbs current distribution on the patches, and widens impedance bandwidth of the magneto-electric dipole antenna. The technical schemes of the magneto-electric dipole antenna and the antenna array are as follows:

in a first aspect, the present disclosure provides a magneto-electric dipole antenna comprising a substrate, a floor, a first patch, a second patch, a shorting strap, a first conductive member, and a second conductive member. The floor is located the first surface of base plate, first paster with the second paster is located the second surface of base plate, and the interval is arranged, wherein, first surface with the second surface is opposite. The two ends of the short circuit belt are respectively connected with the first patch and the second patch, and the short circuit belt divides a gap between the first patch and the second patch into a first gap and a second gap. The first conductive component and the second conductive component penetrate through the substrate, the first conductive component is connected with the first patch and the floor respectively, and the second conductive component is connected with the second patch and the floor respectively.

The magneto-electric dipole antenna can be used alone or as a unit antenna of an antenna array, and the antenna array applied by the magneto-electric dipole antenna can be a phased array, a constant-amplitude in-phase feed antenna array and the like.

The substrate is used to carry the rest of the magneto-electric dipole antenna. The floor is a metal floor for grounding. The first patch and the second patch are metal patches. The short-circuit strip is connected with the first patch and the second patch, current distribution on the first patch and the second patch can be disturbed, and feed signals can be transmitted between the first patch and the second patch through the short-circuit strip.

According to the technical scheme provided by the disclosure, the first patch and the second patch form an electric dipole, the electric dipole is in an O shape on the direction diagram of the H surface, and the direction diagram of the E surface is in an 8 shape. The first conductive component, the second conductive component, the floor, the first gap and the second gap form a magnetic dipole, the magnetic dipole has an 8-shaped directional diagram on the H surface and an O-shaped directional diagram on the E surface. The E-plane and the H-plane of the electric dipole and the magnetic dipole overlap each other.

Thus, for the E plane, the directional diagram of the electric dipole is in an 8 shape, and the directional diagram of the magnetic dipole is in an O shape, and after the two directional diagrams are overlapped, the magnetic dipole antenna can form a wide wave beam on the E plane. For the H surface, the directional diagram of the electric dipole is in an O shape, the directional diagram of the magnetic dipole is in an 8 shape, and after the two directional diagrams are overlapped, the magnetic dipole antenna can form a wide wave beam on the H surface. That is, the present disclosure provides a magneto-electric dipole antenna capable of realizing a wide beam simultaneously in the H-plane and the E-plane.

And the first patch and the second patch are short-circuited by arranging the short-circuit band, so that the current distribution on the first patch and the second patch is disturbed, and the impedance bandwidth of the magnetic electric dipole antenna is expanded. Through experimental simulation, the impedance bandwidth covers 150GHz-170GHz by arranging the short-circuit band, so that the impedance matching performance of the magnetic electric dipole antenna is good at least within 150GHz-170GHz.

In addition, by providing a shorting strip, two new return loss minima points (or resonance points) are created. The frequencies of the two resonance points can be independently adjusted, thereby facilitating the adjustment of the specific frequency band of the impedance bandwidth.

In one possible implementation, the physical lengths of the first and second slots are the same. That is, the shorting strap is located at an intermediate position of the sides of the first patch and the second patch.

In one possible implementation, the electrical lengths of the first slot and the second slot are equal to λ/4, where λ is a wavelength corresponding to an operating frequency of the magneto-electric dipole antenna.

Where λ may be a wavelength corresponding to a center frequency of the magneto-electric dipole antenna.

According to the technical scheme, the effect of the first gap and the second gap with the electric length equal to lambda/4 is the same as that of the gap with the electric length equal to lambda/2.

In one possible implementation, the spacing between the first patch and the second patch is greater than or equal to 0.075m m.

According to the technical scheme provided by the disclosure, experimental simulation shows that in the slot antenna, the longer the slot is, the smaller the required width of the slot is, therefore, the longer slot formed by arranging the first patch and the second patch at intervals is divided into the shorter first slot and the shorter second slot, the distance between the first patch and the second patch can be increased, and the magneto-electric dipole antenna can meet the low-temperature co-fired ceramic (low temperature cofired ceramic, LTCC) process requirements.

In one possible implementation, the side of the first patch remote from the second patch has a first protrusion, and the side of the second patch remote from the first patch has a second protrusion.

According to the technical scheme, the beam width of the magneto-electric dipole antenna on the E plane and the H plane can be adjusted by adjusting the lengths of the first protrusion and the second protrusion. Thus, by arranging the first protrusion and the second protrusion with different protrusion lengths, the magneto-electric dipole antenna with different beam widths on the E face and the H face can be obtained so as to meet different application requirements.

In one possible implementation, the first and second projection projections have a length greater than or equal to 0.02m m and less than or equal to 0.06mm.

In one possible implementation, the first protrusion is located at an intermediate position of a side of the first patch remote from the second patch, and the second protrusion is located at an intermediate position of a side of the second patch remote from the first patch.

In one possible implementation manner, the working frequency band of the magneto-electric dipole antenna is 150GHz-170GHz.

In one possible implementation, the substrate is made of LTCC.

In one possible implementation, the magneto-electric dipole antenna is made using LTCC technology.

In a second aspect, the present disclosure provides an antenna array comprising a feed element for feeding a plurality of the magneto-electric dipole antennas as described in any one of the first aspects and a plurality of magneto-electric dipole antennas.

In one possible implementation, the antenna array is a phased array.

According to the technical scheme, the unit antenna adopted by the phased array is the magneto-electric dipole antenna, and the magneto-electric dipole antenna can form wide beams on the E plane and the H plane simultaneously, so that the phased array can realize two-dimensional wide beam scanning in a large angle range.

In one possible implementation, the antenna array is a constant amplitude in-phase feed antenna array.

Drawings

FIG. 1 is a schematic diagram of a magneto-electric dipole antenna provided by embodiments of the present disclosure;

FIG. 2 is an exploded view of a magneto-electric dipole antenna provided by embodiments of the present disclosure;

FIG. 3 is a schematic diagram of the internal structure of a magneto-electric dipole antenna according to an embodiment of the present disclosure;

FIG. 4 is a schematic diagram of a pattern superposition of electric and magnetic dipoles provided by an embodiment of the present disclosure;

FIG. 5 is a schematic diagram of return loss contrast of a magneto-electric dipole antenna with a shorting strip and a magneto-electric dipole antenna without a shorting strip provided by embodiments of the present disclosure;

FIG. 6 is a front view of a magneto-electric dipole antenna provided by an embodiment of the present disclosure;

FIG. 7 is a schematic diagram of a beam width in the E-plane of a magneto-electric dipole antenna having first and second protrusions with different protrusion lengths provided by an embodiment of the present disclosure;

FIG. 8 is a schematic diagram of beam width in the H-plane of a magneto-electric dipole antenna having first and second protrusions with different protrusion lengths provided by an embodiment of the present disclosure;

fig. 9 is a schematic diagram of an antenna array provided by an embodiment of the present disclosure;

FIG. 10 is a schematic diagram of an array of magneto-electric dipole antennas provided in accordance with an embodiment of the present disclosure;

FIG. 11 is a schematic diagram of an array of magneto-electric dipole antennas provided in accordance with embodiments of the present disclosure;

fig. 12 is an exploded view of an antenna array provided by an embodiment of the present disclosure;

FIG. 13 is a schematic view of a first substrate provided by an embodiment of the present disclosure;

FIG. 14 is a partial schematic view of a first substrate provided by an embodiment of the present disclosure;

FIG. 15 is a schematic view of a first flooring and conversion structure patch provided by an embodiment of the present disclosure;

FIG. 16 is a schematic illustration of a second floor provided by an embodiment of the disclosure;

FIG. 17 is a schematic view of a second substrate provided by an embodiment of the present disclosure;

FIG. 18 is a schematic view of a floor provided by an embodiment of the disclosure;

FIG. 19 is a schematic view of a second surface of a substrate provided by an embodiment of the present disclosure;

FIG. 20 is a schematic diagram of another power feed component provided by an embodiment of the present disclosure;

fig. 21 is a schematic diagram of return loss of an antenna array in an operating frequency band according to an embodiment of the present disclosure;

fig. 22 is a schematic diagram of maximum gain of an antenna array in an operating frequency band according to an embodiment of the present disclosure.

Description of the drawings

01. The device comprises a feed component 010, an amplitude-phase regulation and control unit 011, a first substrate, 0111, a waveguide-to-dielectric integrated waveguide conversion cavity, 0112, a one-to-eight dielectric integrated waveguide power divider 012, a first floor, 0121, a dielectric integrated waveguide coupling groove 013, a conversion structure patch 014, a second floor, 0141, a binary cavity coupling groove 015, a second substrate, 0151 and a binary dielectric integrated cavity;

02. a magneto-electric dipole antenna;

1. a substrate 1a, a first surface 1b, a second surface;

2. a floor, 21, antenna feed slot;

3. a first patch 31, a first protrusion;

4. a second patch 41, a second protrusion;

5. a shorting strap;

6. a first conductive member 61, a first conductive member;

7. a second conductive member 71, a second conductive member;

8. an isolation chamber;

9. an isolation gate;

a. first gap, b, second gap.

Detailed Description

In order to better understand the technical solutions provided by the embodiments of the present disclosure, some terms related to the technical solutions provided by the embodiments of the present disclosure are explained below.

Beam width: refers to the angle between the two points at which the radiation intensity decreases by 3dB on both sides of the maximum radiation beam of the antenna. The beam width of the antenna can be divided into a beam width in the E plane and a beam width in the H plane.

E face: a plane containing the direction of maximum antenna gain and parallel to the electric field vector.

H face: a plane containing the direction of maximum antenna gain and perpendicular to the E-plane.

An electric dipole: the direction diagram on the E surface is 8-shaped, and the direction diagram on the H surface is O-shaped.

Magnetic dipole: the direction diagram on the E surface is in an O shape, and the direction diagram on the H surface is in an 8 shape.

Gain: the ratio of the power densities of the signals generated by the actual antenna and the ideal radiating element at the same point in space, with equal input power. It quantitatively describes the extent to which an antenna radiates concentrated input power, and is used to measure the ability of the antenna to transmit and receive signals in a particular direction.

Phased array: the phased array comprises a feed component and a plurality of unit antennas which are arranged in an array mode, wherein the feed component is used for feeding the plurality of unit antennas, and the phase and the amplitude of feed signals of the plurality of unit antennas can be independently adjusted so as to realize beam scanning.

Beam scanning: after the beams radiated by a plurality of unit antennas forming the phased array are overlapped, the maximum radiation beam of the phased array is formed. By adjusting the phase and amplitude of the feed signals of the multiple element antennas, the position of the beam overlap can be adjusted, thereby changing the pointing direction of the maximum radiation beam of the phased array so that the maximum radiation beam can be scanned over a range of angles. Since the maximum radiation beam of the phased array is formed by the superposition of beams of a plurality of unit antennas constituting the phased array, the angle range of beam scanning is approximately the same as the beam width of the unit antennas. Therefore, in order to realize a beam scanning at a large angle, it is necessary for the element antenna to have a sufficiently wide beam width.

Return loss S11 (dB): refers to the ratio of the power reflected from the rf input signal to the power of the input signal, often expressed in dB, is a negative number. In an ideal case, the impedance of the antenna and the radio frequency circuit are completely matched, and no reflected power is generated at all, so that the return loss is infinitely small. However, it is not possible for the impedance to match exactly in engineering, so reflected power is necessarily present. The worst case is when the input power is totally reflected, with a return loss of 0dB. Thus, for this technical parameter of return loss, a lower value indicates better antenna performance.

Impedance bandwidth: so that the return loss S11 (dB) of the antenna is smaller than the bandwidth of the target value, i.e., when the antenna operates at the impedance bandwidth, the return loss S11 (dB) of the antenna is smaller than the target value. A target value of-10 dB is generally required. The impedance bandwidth may also be referred to as the radiation bandwidth.

With the increasing popularity of wireless devices, data traffic has exploded. Meanwhile, the wireless system has higher and higher requirements on the data transmission rate, and the frequency spectrum resources are more and less. Terahertz (THz) frequency band has rich frequency spectrum resources and wider bandwidth, and can meet the requirement of high transmission rate. In addition, the antenna corresponding to the terahertz frequency band is small in size and convenient to integrate with a radio frequency circuit. Terahertz antenna technology is one of the important technologies for the next generation of mobile communication. Among them, a frequency band of 0.1THz-10THz is generally referred to as a terahertz frequency band, for example, a 150GHz-170GHz frequency band.

However, the terahertz frequency band has high frequency, the path attenuation is serious, and the acting distance of the antenna is short. Therefore, in order to perform efficient wireless communication in the terahertz frequency band, a high-gain antenna is required.

The phased array can scan the wave beam by adjusting and controlling the amplitude and phase of the feed signal while guaranteeing the high gain of the antenna, and further expands the action range of the antenna. As the scan angle of the phased array increases, the gain of the main beam (the maximum radiation beam) of the phased array is continuously reduced, and in order to ensure that the phased array maintains a certain gain during scanning at a large angle, it is generally required that the unit antennas forming the phased array have a relatively wide beam width, and in particular, that the unit antennas can simultaneously realize a wide beam in the H-plane and the E-plane in the target frequency band.

In view of the above technical problems, the presently disclosed embodiments provide a magneto-electric dipole antenna, as shown in fig. 1-3, which includes a substrate 1, a floor 2, a first patch 3, a second patch 4, a shorting strap 5, a first conductive member 6, and a second conductive member 7. The floor 2 is located on the first surface 1a of the base plate 1. The first patch 3 and the second patch 4 are located on the second surface 1b of the substrate 1 and are arranged at intervals, and the first surface 1a and the second surface 1b are opposite. The two ends of the short-circuit strip 5 are respectively connected with the first patch 3 and the second patch 4, and the short-circuit strip 5 separates the gap between the first patch 3 and the second patch 4 into a first gap a and a second gap b. The first conductive member 6 and the second conductive member 7 penetrate the substrate 1, the first conductive member 6 is connected to the first patch 3 and the floor 2, respectively, and the second conductive member 7 is connected to the second patch 4 and the floor 2, respectively.

The working frequency band of the magnetic electric dipole antenna is not limited, and in some examples, the working frequency band of the magnetic electric dipole antenna is located in a terahertz frequency band, for example, the working frequency band is 150GHz-170GHz, but is not limited thereto. The magneto-electric dipole antenna provided by the embodiment of the disclosure can be used alone or as a unit antenna of an antenna array, wherein the antenna array applied by the magneto-electric dipole antenna can be a phased array, a constant amplitude in-phase feed antenna array and the like.

The substrate 1 is used to carry the rest of the magneto-electric dipole antenna. In some examples, the substrate 1 is made of low temperature co-fired ceramic (low temperature cofired ceramic, LTCC). The floor 2 is a metal floor for grounding. The first patch 3 and the second patch 4 are metal patches. The short-circuit strip 5 is connected with the first patch 3 and the second patch 4, so that the current distribution on the first patch 3 and the second patch 4 can be disturbed, and a feed signal can be transmitted between the first patch 3 and the second patch 4 through the short-circuit strip 5. In some examples, the direction of current flow on the first patch 3, the second patch 4, and the shorting strip 5 is parallel to the X-axis in fig. 1.

According to the technical scheme provided by the embodiment of the disclosure, as shown in fig. 1 and 4, the first patch 3 and the second patch 4 form an electric dipole, the electric dipole is placed along the X-axis direction in fig. 1 and 4, the H plane of the electric dipole is a YOZ plane, and the E plane is an XOZ plane. The electric dipole has an O-shaped directional diagram on the H plane and an 8-shaped directional diagram on the E plane.

As shown in fig. 3 and 4, the first conductive member 6, the second conductive member 7, the floor 2, the first slit a, and the second slit b form a magnetic dipole placed in the Y-axis direction in fig. 3 and 4, the H-plane of the magnetic dipole being YOZ-plane, and the E-plane being XOZ-plane. The magnetic dipole has an 8-shaped directional diagram on the H surface and an O-shaped directional diagram on the E surface.

As shown in fig. 4, for the E plane (XOZ plane), the electric dipole pattern is "8" shaped, and the magnetic dipole pattern is "O" shaped, and after the two patterns are superimposed, the E plane pattern shown in the upper right corner of fig. 4 is formed. For the H plane (YOZ plane), the pattern of the electric dipole is "O" shaped, and the pattern of the magnetic dipole is "8" shaped, and the two are superimposed to form the H plane pattern shown in the lower right corner of fig. 4. As can be seen from fig. 4, the magneto-electric dipole antenna provided by the embodiment of the present disclosure can realize a wide beam (the wide beam points to the positive direction of the Z axis) on both the H plane and the E plane.

And, through setting up short-circuit area 5 and shorting out first paster 3 and second paster 4, the electric current distribution on first paster 3 and the second paster 4 has disturbed, has expanded the impedance bandwidth of magneto-electric dipole antenna.

Through experimental simulation, as shown in fig. 5, a schematic diagram of comparison of return loss of the magneto-electric dipole antenna with the short-circuit band 5 and the magneto-electric dipole antenna without the short-circuit band 5 is shown, in fig. 5, the horizontal axis represents the working frequency (unit is GHz) of the magneto-electric dipole antenna, and the vertical axis represents the return loss, and as can be seen from fig. 5, by setting the short-circuit band 5, the impedance bandwidth of the magneto-electric dipole antenna is expanded, so that the impedance bandwidth covers 150GHz-170GHz, and the impedance matching performance of the magneto-electric dipole antenna is better at least within 150GHz-170GHz.

In addition, as can be seen from fig. 5, by providing the shorting strip 5, two new return loss minimum points (or referred to as resonance points, points a and B in fig. 5) are created. The positions of the point A and the point B can be independently adjusted (along the transverse axis), so that the specific frequency band of the impedance bandwidth is convenient to adjust.

In adjusting the position of the point a, this can be achieved by adjusting the width W0 of the first patch 3 and the second patch 4 along the X-axis, as shown in fig. 6. Wherein the width W0 of the first patch 3 and the second patch 4 along the X-axis determines the electrical length of the formed electric dipole, and 2 times the electrical length of the electric dipole is equal to the wavelength corresponding to the center frequency of the electric dipole. Therefore, the width W0 of the first patch 3 and the second patch 4 along the X-axis determines the center frequency of the electric dipole, which is the frequency corresponding to the point a in fig. 5. Therefore, the position of the point a can be adjusted by adjusting the width W0 of the first patch 3 and the second patch 4 along the X axis.

In adjusting the position of the B-point, this can be achieved by adjusting the structure of the feeding means for feeding the magneto-electric dipole antenna.

Moreover, the existence of the short-circuit strip 5 separates the gaps formed by the interval arrangement of the first patch 3 and the second patch 4 into the shorter first gap a and the shorter second gap b, so that the interval W1 between the first patch 3 and the second patch 4 can be larger, the manufacturing precision requirement on the magneto dipole antenna is lower, and the magneto dipole antenna is easier to realize.

In the slot antenna, it was found through experimental simulation that the longer the slot, the smaller the required width of the slot, and therefore, by dividing the long slot formed by arranging the first patch 3 and the second patch 4 at intervals into the first slot a and the second slot b which are shorter, the interval between the first patch 3 and the second patch 4 can be increased.

In some examples, when the working frequency band of the magnetic dipole antenna is a terahertz frequency band, the size of the magnetic dipole antenna is smaller, and higher manufacturing precision is required, and then the LTCC process can be used for manufacturing the magnetic dipole antenna. For the LTCC process, the minimum metal line width and the line spacing are required to be greater than 0.075mm, and the gap between the first patch 3 and the second patch 4 is separated into the first gap a and the second gap b by the arrangement of the shorting tape 5, so that the spacing W1 between the first patch 3 and the second patch 4 is greater than or equal to 0.075mm, thereby meeting the LTCC process requirement.

The embodiment of the present disclosure does not limit the specific position of the shorting strap 5, and in some examples, as shown in fig. 6, the physical lengths of the first slit a and the second slit b are the same (two L1 in fig. 6 are the same). That is, the short-circuit strap 5 is located at an intermediate position of the side portions of the first patch 3 and the second patch 4.

In some examples, the electrical lengths of the first slot a and the second slot b are each equal to λ/4, where λ is a wavelength corresponding to an operating frequency of the magnetic electric dipole antenna. Where λ may be a center frequency of an operating frequency band of the magneto-electric dipole antenna.

According to the technical scheme provided by the embodiment of the disclosure, the same effect as that of a gap with the electric length equal to lambda/2 can be achieved by arranging two gaps with the electric length equal to lambda/4. And after the length of the gap is shortened, the distance between the first patch 3 and the second patch 4 can be larger, and the LTCC process requirement can be met.

In some examples, as shown in fig. 1-3 and 6, the side of the first patch 3 remote from the second patch 4 has a first protrusion 31 and the side of the second patch 4 remote from the first patch 3 has a second protrusion 41.

According to the technical scheme provided by the embodiment of the disclosure, the beam width of the magneto-electric dipole antenna on the E plane and the H plane can be adjusted by adjusting the protruding lengths (the protruding lengths along the X axis, W2 in FIG. 6) of the first protrusion 31 and the second protrusion 41.

Thus, by providing the first protrusion 31 and the second protrusion 41 having different protrusion lengths, a magneto-electric dipole antenna having different beam widths on the E-plane and the H-plane can be obtained to satisfy different application requirements.

Through experimental simulation, as shown in fig. 7, a schematic diagram of beam width of the magneto-electric dipole antenna in the E plane within the operating frequency band (150 GHz-170 GHz) is shown in the case that lengths W2 of the first protrusion 31 and the second protrusion 41 are 0.02mm, 0.04mm, and 0.06mm, respectively. As can be seen from fig. 7, the beam width of the magnetodipole antenna at the E plane is at least greater than 87.5 ° under the three protruding lengths, and it can be seen that the magnetodipole antenna provided by the embodiments of the present disclosure can realize a wide beam at the E plane. Also, the beam width of the magneto-electric dipole antenna in the E plane is different in the three projection lengths, and therefore, by adjusting the lengths of the first projection 31 and the second projection 41, the beam width of the magneto-electric dipole antenna in the E plane can be adjusted.

As shown in fig. 8, a schematic diagram of the beam width of the magneto-electric dipole antenna in the H plane within the operating frequency band (150 GHz-170 GHz) is shown with the lengths W2 of the projections of the first projection 31 and the second projection 41 being 0.02mm, 0.04mm and 0.06mm, respectively. As can be seen from fig. 8, the beam width of the magnetic electric dipole antenna on the H plane is at least greater than 90 ° under the three protruding lengths, and it can be seen that the magnetic electric dipole antenna provided by the embodiment of the present disclosure can realize a wide beam on the H plane. Also, the beam width of the magneto-electric dipole antenna in the H plane is different in the three projection lengths, and therefore, by adjusting the lengths of the first projection 31 and the second projection 41, the beam width of the magneto-electric dipole antenna in the H plane can be adjusted.

The specific positions of the first protrusion 31 and the second protrusion 41 are not limited in the embodiments of the present disclosure, and in some examples, as shown in fig. 6, the first protrusion 31 is located at an intermediate position on a side of the first patch 3 away from the second patch 4, and the second protrusion 41 is located at an intermediate position on a side of the second patch 4 away from the first patch 3.

The form of the first conductive member 6 and the second conductive member 7 is not limited in the embodiment of the present disclosure, and in some examples, as shown in fig. 3, the first conductive member 6 includes a plurality of first conductive members 61, the plurality of first conductive members 61 are arranged at intervals, and both ends of each first conductive member 61 are connected to the first patch 3 and the floor 2, respectively. The second conductive member 7 includes a plurality of second conductive members 71, the plurality of second conductive members 71 are arranged at intervals, and both ends of each second conductive member 71 are connected to the second patch 4 and the floor 2, respectively.

The first conductive member 61 and the second conductive member 71 may be any devices capable of electrically connecting the first patch 3, the second patch 4, and the floor 2. In some examples, the first conductive element 61 and the second conductive element 71 are metallized vias, and in other examples, the first conductive element 61 and the second conductive element 71 are metal posts.

The number of the first conductive members 61 and the second conductive members 71 is not limited in the embodiment of the present disclosure, and in some examples, as shown in fig. 3, the first conductive members 61 and the second conductive members 71 are three, but not limited thereto.

The feeding manner of the magneto-electric dipole antenna according to the embodiment of the present disclosure is not limited, and in some examples, as shown in fig. 3, the floor 2 has an antenna feeding slot 21, and the antenna feeding slot 21 is opposite to the region between the first conductive member 6 and the second conductive member 7.

In feeding, the feeding member can feed the first conductive member 6, the second conductive member 7, the first patch 3, the second patch 4, and the short-circuit strip 5 through the antenna feeding slot 21, and the feeding signal can be transmitted toward the first patch 3, the second patch 4, and the short-circuit strip 5 via the first conductive member 6, the second conductive member 7, and the space between the first conductive member 6 and the second conductive member 7.

The manufacturing process of the magneto-electric dipole antenna is not limited in the embodiment of the disclosure, and the magneto-electric dipole antenna can be manufactured and formed by adopting a printed circuit board (printed circuit board, PCB) process or an LTCC process.

In some examples, for the case that the working frequency band of the magnetic electric dipole antenna is located in the terahertz frequency band, the size of the magnetic electric dipole antenna is relatively smaller, and higher processing precision is required, so that the LTCC process can be used for manufacturing and shaping.

The embodiment of the present disclosure further provides an antenna array, as shown in fig. 9, where the antenna array includes a feeding unit 01 and a plurality of the above-mentioned magneto-electric dipole antennas 02, and the feeding unit 01 is configured to feed the plurality of magneto-electric dipole antennas 02.

The embodiments of the present disclosure are not limited to the type of antenna array, and in some examples, the antenna array is a phased array with beam scanning. In addition, since the unit antenna used by the phased array is the magneto-electric dipole antenna, the phased array can realize two-dimensional wide beam scanning within a large angle range.

Of course, in other examples, the antenna array may be a constant-amplitude in-phase feed antenna array, etc., where the amplitude and the phase of the feed signals transmitted from the feed unit 01 of the constant-amplitude in-phase feed antenna to the plurality of magneto-dipole antennas 02 are the same, and the constant-amplitude in-phase feed antenna array does not have a beam scanning function.

The number of the magnetic dipole antennas 02 included in the antenna array is not limited in the embodiments of the present disclosure, and in some examples, the plurality of magnetic dipole antennas 02 are arranged in an M-row N-column array.

Illustratively, as shown in fig. 9, the number of the magnetic electric dipole antennas 02 is 16, and the 16 magnetic electric dipole antennas 02 are arranged in 4 rows and 4 columns.

In some examples, as shown in fig. 9, a plurality of magneto-electric dipole antennas 02 are equally spaced along the X-axis and the Y-axis.

In some examples, as shown in fig. 9, the antenna array includes a plurality of magneto-electric dipole antennas 02 that share the same substrate 1 and the same floor 2. Of course, it is also understood that the substrates 1 of the plurality of magneto-electric dipole antennas 02 are integrally connected, and the floors 2 of the plurality of magneto-electric dipole antennas 02 are integrally connected.

In some examples, as shown in fig. 10 and 11, the antenna array further comprises an isolation cavity 8 and an isolation grating 9 located at the first surface 1a of the substrate 1. Wherein the isolation cavity 8 is surrounded by a metallized via or metal post penetrating the substrate 1.

According to the technical scheme provided by the embodiment of the disclosure, the isolation cavity 8, the isolation grating 9 and the floor 2 jointly act to separate different magnetic dipole antennas 02, so that high-frequency surface waves of the magnetic dipole antennas 02 on the first surface 1a are effectively restrained, energy leakage of electromagnetic waves in a non-target direction (the target direction is a direction perpendicular to the first surface 1 a) is reduced, and the gain of an antenna array is improved.

Next, the feeding section 01 will be described in more detail as an example:

as shown in fig. 12, the power feeding section 01 includes a first substrate 011, a first floor 012, a conversion structure patch 013, a second floor 014, and a second substrate 015.

As shown in fig. 13, the first substrate 011 has a waveguide-to-dielectric integrated waveguide conversion cavity 0111 and an eight-division dielectric integrated waveguide power divider 0112, each of which is formed by surrounding a metallized via or metal pillar extending through the first substrate 011. When the magneto-electric dipole antenna 02 is 2N, the one-to-eight dielectric integrated waveguide power divider 0112 is replaced by a one-to-N dielectric integrated waveguide power divider.

As shown by the arrow direction in fig. 13, the feed signal is introduced by the waveguide-to-dielectric integrated waveguide conversion cavity 0111 and then input into eight (N) subchambers 01121 of the one-to-eight dielectric integrated waveguide power divider 0112 via one-to-eight power division of the one-to-eight dielectric integrated waveguide power divider 0112.

In some examples, as shown in fig. 14, in the first one-to-two structure (which may be referred to as a T-section) of the one-to-eight dielectric integrated waveguide power divider 0112, when the feed signal is transmitted to the one-to-two structure, a part of the feed signal is reflected by a reflecting surface formed by the metallized through hole or the metal pillar, and the reflected feed signal affects the matching performance of the input end.

To improve the matching performance of the input, in some examples, partially metallized vias or metal posts in the backbone portion of the one-to-two structure are recessed inward as shown in fig. 14. The distance between the concave metalized through hole or the metal column and the reflecting surface of the one-to-two structure is about lambda/4, so that the feed signal reflected by the reflecting surface is reflected by the concave metalized through hole or the metal column, and the phase difference of the two feed signals is 180 degrees, therefore, the two feed signals can cancel each other, and the reflection coefficient of the input end is greatly improved.

As shown in fig. 15, the first floor 012 is located on one surface of the first substrate 011, and the dielectric integrated waveguide coupling groove 0121 on the first floor 012 is opposite to the dielectric integrated waveguide conversion cavity 0111 on the first substrate 011, and a conversion structure patch 013 is provided in the dielectric integrated waveguide coupling groove 0121, the conversion structure patch 013 being attached to the first substrate 011. A power supply may be connected to the dielectric integrated waveguide coupling slot 0121, and the power supply may be capable of feeding a power supply signal to the waveguide-to-dielectric integrated waveguide conversion cavity 0111 through the dielectric integrated waveguide coupling slot 0121 and the conversion structure patch 013.

As shown in fig. 16, the second floor 014 is located on the other surface of the first base plate 011, and the second floor 014 has eight binary cavity coupling grooves 0141, which are respectively opposite to eight sub-cavities 01121 of the one-to-eight-medium integrated waveguide power divider 0112 of the first base plate 011. Thus, the feeding signals transmitted to the eight sub-cavities 01121 can be fed to the second substrate 015 via the eight binary cavity coupling grooves 0141, respectively. When the one-to-eight-medium integrated waveguide power divider 0112 is replaced by one-to-N-medium integrated waveguide power divider, the number of binary cavity coupling grooves 0141 is N.

In some examples, as shown in fig. 17, the second substrate 015 has eight (N) dielectric integrated cavities 0151, the dielectric integrated cavities 0151 being formed by surrounding metallized vias or metal posts through the second substrate 015. The second floor 014 is sandwiched between the first and second substrates 011 and 015, and the feeding signals outputted from the eight binary cavity coupling grooves 0141 of the second floor 014 are transmitted to the eight dielectric integrated cavities 0151, respectively. Further, as shown in fig. 17, it is found through experimental tests that the position of the point B in fig. 6 can be adjusted individually by adjusting the length L2 of the medium integration chamber 0151.

The second substrate 015 is attached to the floor 2 of the magneto-electric dipole antenna 02, and as shown in fig. 18, of the 16 antenna feed slots 21 of the floor 2, each two antenna feed slots 21 are opposed to one dielectric integrated cavity 0151, and each dielectric integrated cavity 0151 is fed through two antenna feed slots 21.

As shown in fig. 18 and 19, each antenna feed slot 21 of the floor board 2 is opposed to the region between the first conductive member 6 and the second conductive member 7, and then each antenna feed slot 21 feeds one of the magnetic electric dipole antennas 02.

The feeding section 01 provided above can be applied to a constant amplitude in-phase feeding antenna array. In other examples, the disclosed embodiments also provide a feed element 01 that can be applied to a phased array.

Illustratively, as shown in fig. 20, the feeding member 01 has a plurality of amplitude-phase control units 010, and each of the amplitude-phase control units 010 is capable of independently adjusting the amplitude and phase of the feeding signal and transmitting the feeding signal to the corresponding magneto-electric dipole antenna 02.

In some examples, the amplitude phase control unit 010 is 16.

The return loss and gain of the antenna array provided by the embodiments of the present disclosure are described below:

as shown in fig. 21, a schematic diagram of return loss of the antenna array provided by the embodiment of the disclosure in an operating frequency band is shown, and as can be seen from fig. 21, return loss S11 (dB) of the antenna array provided by the embodiment of the disclosure in a range of 150GHz-170GHz is below-10 dB. That is, the antenna array provided by the embodiment of the present disclosure has good impedance matching performance in the working frequency band, and the impedance bandwidth of the antenna array covers 150GHz-170GHz.

As shown in fig. 22, a schematic diagram of maximum gain of an antenna array provided by an embodiment of the present disclosure in an operating frequency band is shown, and as can be seen from fig. 22, the maximum gain of the antenna array provided by the embodiment of the present disclosure in a range of 150GHz-170GHz is above 16.3dBi, and the fluctuation of the gain in a range of 150GHz-170GHz is less than 1.2dBi. That is, the antenna array for the embodiment of the present disclosure has a larger gain and a larger working distance.

The terminology used in the description of the embodiments of the disclosure is for the purpose of describing the embodiments of the disclosure only and is not intended to be limiting of the disclosure. Unless defined otherwise, technical or scientific terms used in the embodiments of the present disclosure should be given the ordinary meaning as understood by one of ordinary skill in the art to which the present disclosure belongs. The terms "first," "second," and the like in the description and in the claims, are not used for any order, quantity, or importance, but are used for distinguishing between different elements. Likewise, the terms "a" or "an" and the like do not denote a limitation of quantity, but rather denote the presence of at least one. The word "comprising" or "comprises", and the like, is intended to mean that elements or items that are present in front of "comprising" or "comprising" are included in the word "comprising" or "comprising", and equivalents thereof, without excluding other elements or items. "upper", "lower", "left", "right", etc. are used merely to denote relative positional relationships, which may also change accordingly when the absolute position of the object to be described changes. "plurality" means two or more, unless expressly defined otherwise.

The foregoing description of the preferred embodiments of the present disclosure is provided for the purpose of illustration only, and is not intended to limit the disclosure to the particular embodiments disclosed, but on the contrary, the intention is to cover all modifications, equivalents, alternatives, and alternatives falling within the spirit and scope of the disclosure.

Claims (10)

1. A magneto-electric dipole antenna, characterized by comprising a substrate (1), a floor (2), a first patch (3), a second patch (4), a short-circuit strip (5), a first conductive member (6) and a second conductive member (7);

the floor (2) is located on a first surface (1 a) of the substrate (1);

the first patch (3) and the second patch (4) are positioned on the second surface (1 b) of the substrate (1) and are arranged at intervals, wherein the first surface (1 a) and the second surface (1 b) are opposite;

two ends of the short-circuit belt (5) are respectively connected with the first patch (3) and the second patch (4), and the short-circuit belt (5) divides a gap between the first patch (3) and the second patch (4) into a first gap (a) and a second gap (b);

the first conductive component (6) and the second conductive component (7) penetrate through the substrate (1), the first conductive component (6) is respectively connected with the first patch (3) and the floor (2), and the second conductive component (7) is respectively connected with the second patch (4) and the floor (2).

2. The magneto-electric dipole antenna of claim 1, wherein the physical lengths of the first slot (a) and the second slot (b) are the same.

3. The magneto-electric dipole antenna according to claim 1 or 2, wherein the electrical lengths of said first slot (a) and said second slot (b) are each equal to λ/4, where λ is the wavelength corresponding to the operating frequency of said magneto-electric dipole antenna.

4. A magneto-electric dipole antenna according to any of claims 1-3, wherein the spacing between said first patch (3) and said second patch (4) is greater than or equal to 0.075mm.

5. A magneto-electric dipole antenna according to any one of claims 1-4, wherein the side of the first patch (3) remote from the second patch (4) has a first bulge (31);

the side of the second patch (4) remote from the first patch (3) has a second projection (41).

6. A magneto-electric dipole antenna according to claim 5, wherein said first protrusion (31) is located in an intermediate position of a side of said first patch (3) remote from said second patch (4);

the second protrusion (41) is located at an intermediate position of a side of the second patch (4) remote from the first patch (3).

7. The magneto-electric dipole antenna of any one of claims 1-6, wherein the operating frequency band of the magneto-electric dipole antenna is 150GHz-170GHz.

8. A magneto-electric dipole antenna according to any of claims 1-7, characterized in that the material of the substrate (1) is a low temperature co-fired ceramic LTCC.

9. An antenna array, characterized in that it comprises a feeding member (01) and a plurality of magneto-electric dipole antennas (02) according to any of claims 1-9, said feeding member (01) being arranged to feed a plurality of said magneto-electric dipole antennas (02).

10. The antenna array of claim 9, wherein the antenna array is a phased array.