CN116937136A

CN116937136A - Electronic equipment

Info

Publication number: CN116937136A
Application number: CN202210849062.4A
Authority: CN
Inventors: 薛亮; 王汉阳; 侯猛; 叶茂; 孙思宁
Original assignee: Huawei Technologies Co Ltd
Current assignee: Huawei Technologies Co Ltd
Priority date: 2022-04-01
Filing date: 2022-07-19
Publication date: 2023-10-24

Abstract

The embodiment of the application provides electronic equipment, which comprises a radiator, a floor, a first inductor and a second inductor. The radiator includes first end and second end, and is located ground point, first tie point and the second tie point between first end and the second end, and the ground point sets up in the central region of radiator. The inductance values of the first inductor and the second inductor are smaller than or equal to a first threshold value. The length of the radiator is greater than three-quarters of the first wavelength, where the first wavelength is the medium wavelength of the first resonance produced by the radiator. The first inductor is electrically connected between the first connection point and the floor, and the second inductor is electrically connected between the second connection point and the floor. The distance between the first connection point and the first end is less than a quarter of the first wavelength, and the second connection point is located between the first connection point and the second end. The radiation caliber of the antenna structure can be expanded by utilizing the inductance electrically connected between the radiator and the floor, and the conductor loss is reduced, so that the radiation efficiency of the antenna structure is effectively improved.

Description

Electronic equipment

The present application claims priority from the chinese patent office, application number 202210348011.3, application name "an electronic device" filed on 1 month 2022, which is incorporated herein by reference in its entirety.

Technical Field

The present application relates to the field of wireless communications, and in particular, to an electronic device.

Background

With the rapid development of wireless communication technology, the second generation (second generation, 2G) mobile communication system mainly supports a call function in the past, and electronic devices are only tools for people to send and receive short messages and communicate with voice, and wireless internet function is very slow due to the fact that data transmission utilizes voice channels for transmission. Nowadays, the electronic device is used for on-line listening to music, watching network movies, real-time video, etc. besides being used for talking, sending short messages, photographing, and the like, and covers various applications such as talking, video entertainment, electronic commerce, etc. in life, various functional applications all need to upload and download data through a wireless network, so that high-speed transmission of data is very important.

As the demand for high-speed data transmission increases, the trend in the industrial design (industrial design, ID) of electronic devices is a large screen ratio, multiple cameras. This results in a substantial reduction of antenna headroom and an increasing limitation of layout space. Many new communication specifications are presented at the same time, and more antennas need to be laid out in the mobile phone. The problems of multi-antenna coexistence design and single antenna performance improvement have been studied by antenna designers. For antenna design in electronic devices, there is a trend of miniaturization of the antenna, but this requirement contradicts the characteristics of the antenna itself as an open system, which restricts the performance of the antenna.

Disclosure of Invention

The embodiment of the application provides electronic equipment, which comprises a radiator, a floor, a first inductor and a second inductor. The radiation caliber of the antenna structure can be expanded by utilizing the inductance arranged between the radiator and the floor, and the conductor loss is reduced, so that the radiation efficiency of the antenna structure is effectively improved.

In a first aspect, an electronic device is provided, including: the radiator comprises a first end, a second end, a grounding point, a first connecting point and a second connecting point, wherein the grounding point, the first connecting point and the second connecting point are positioned between the first end and the second end, the grounding point is arranged in the central area of the radiator, and the first end and the second end are both open ends; a floor through which the radiator is grounded at the grounding point; the first inductor and the second inductor have inductance values smaller than or equal to a first threshold value; wherein the length of the radiator from the first end to the second end is greater than three-quarters of a first wavelength, the portion of the radiator from the first end to the second end being for generating a first resonance, wherein the first wavelength is a medium wavelength of the first resonance; the first inductor is electrically connected between the first connection point and the floor, and the second inductor is electrically connected between the second connection point and the floor; the distance between the first connection point and the first end is less than a quarter of the first wavelength, and the second connection point is located between the first connection point and the second end.

According to the embodiment of the application, the inductance arranged between the radiator and the floor can be utilized, so that when the feeding point feeds an electric signal, the current on the radiator is reversed in the area near the first connecting point and the second connecting point because the radiator is respectively and electrically connected with the first inductance and the second inductance between the first connecting point and the second connecting point and the floor. Correspondingly, the current on the floor can be reversed in the area near the connection of the first inductor and the second inductor on the floor. The current density on the radiator can be dispersed (the intensity of a single current strong point is reduced, so that the current is more uniformly distributed), thereby reducing the loss caused by the radiator and the conductors arranged around the radiator, and further improving the efficiency of the antenna structure.

With reference to the first aspect, in certain implementations of the first aspect, when a frequency of the first resonance is less than or equal to 1GHz, the first threshold is 6nH; when the frequency of the first resonance is greater than 1GHz and less than or equal to 2.2GHz, the first threshold is 4nH; when the frequency of the first resonance is greater than 2.2GHz and less than or equal to 3GHz, the first threshold is 3nH; when the frequency of the first resonance is greater than 3GHz, the first threshold is 2nH.

According to the embodiment of the application, the inductance values of the first inductor and the second inductor are designed according to the working frequency bands of different antenna structures, so that the current distribution on the radiator is more uniform in the working frequency bands, the conductor loss is reduced, and the efficiency of the antenna structure is improved.

With reference to the first aspect, in certain implementations of the first aspect, the first connection point is located between the first end and the ground point, and the second connection point is located between the second end and the ground point; the distance between the second connection point and the second end is less than a quarter of the first wavelength.

According to the embodiment of the application, the distance between the first connecting point and the first end is smaller than one fourth of the first wavelength, so that the efficiency of the antenna structure can be further improved.

With reference to the first aspect, in certain implementation manners of the first aspect, the electronic device further includes: the third inductor is electrically connected between a third connection point and the ground plate, and the third connection point is positioned between the grounding point and the first connection point; and/or a fourth inductor electrically connected between a fourth connection point and the ground plate, wherein the fourth connection point is positioned between the ground point and the second connection point.

According to the embodiment of the application, the number of the inductors electrically connected with the radiator and the floor is increased, so that the current density distribution on the radiator is more uniform, and the loss caused by the radiator and the conductors arranged around the radiator is reduced. Meanwhile, the position of each radiator connected with the inductor comprises a current reversing area, so that the electric field cannot reach zero, the electric field generated by the radiator is continuous, the reverse direction (not comprising the electric field reversing area) does not occur, the radiation caliber of the antenna structure is increased, the conductor loss is reduced, and the efficiency of the antenna structure is improved.

With reference to the first aspect, in certain implementation manners of the first aspect, the radiator is provided with one or more insulation slits, and a width of each slit is greater than or equal to 0.1mm and less than or equal to 2mm.

According to the embodiment of the application, two ends of a gap formed on the radiator can be connected with a capacitor (for example, a lumped capacitor) in series to form a metamaterial structure of the series capacitor.

With reference to the first aspect, in certain implementation manners of the first aspect, the electronic device further includes a conductive frame, the frame has a first position and a second position, the frame between the first position and the second position is used as the radiator, a central area of the radiator is an area within 5mm from a center of the radiator, and insulating slits are respectively provided on the first position and the second position of the frame.

According to the embodiment of the application, the first position and the second position may be located on the same side of the frame, the radiator may be linear, or the first position and the second position may be located on two adjacent sides of the frame, and the radiator may be a polygonal line, for example, an L-shape.

In a second aspect, there is provided an electronic device comprising: a radiator including a first end and a second end, and a first connection point and a second connection point between the first end and the second end; a floor through which the radiator is grounded at the first and second ends; the first inductor and the second inductor have inductance values smaller than a first threshold value; wherein the length of the radiator is greater than three-quarters of a first wavelength, the portion of the radiator from the first end to the second end being configured to produce a first resonance, wherein the first wavelength is a medium wavelength of the first resonance; the first inductor is electrically connected between the first connection point and the floor, and the second inductor is electrically connected between the second connection point and the floor; the first connection point is located between the center of the radiator and the first end and is less than one eighth of the first wavelength from the center of the radiator, and the second connection point is located between the first connection point and the second end.

With reference to the second aspect, in certain implementations of the second aspect, the first end and the second end are separated by a distance equal to a length of the radiator; when the frequency of the first resonance is less than or equal to 1GHz, the first threshold is 6nH; when the frequency of the first resonance is greater than 1GHz and less than or equal to 2.2GHz, the first threshold is 4nH; when the frequency of the first resonance is greater than 2.2GHz and less than or equal to 3GHz, the first threshold is 3nH; when the frequency of the first resonance is greater than 3GHz, the first threshold is 2nH. In one embodiment, the first end and the second end are spaced apart a distance equal to the length of the radiator

With reference to the second aspect, in certain implementations of the second aspect, the second connection point is located between the second end and a center of the radiator; the distance between the second connection point and the center of the radiator is less than one eighth of the first wavelength.

With reference to the second aspect, in certain implementations of the second aspect, the first end and the second end are separated by a distance less than a length of the radiator; when the frequency of the first resonance is less than or equal to 1GHz, the first threshold is 20nH; when the frequency of the first resonance is greater than 1GHz and less than or equal to 2.2GHz, the first threshold is 16nH; when the frequency of the first resonance is greater than 2.2GHz and less than or equal to 3GHz, the first threshold is 12nH; when the frequency of the first resonance is greater than 3GHz, the first threshold is 10nH.

With reference to the second aspect, in certain implementations of the second aspect, the electronic device further includes: a third inductor electrically connected between a corresponding at least one third connection point and a ground plane, the third connection point being located between the center of the radiator and the first connection point; and/or a fourth inductor electrically connected between the respective at least one fourth connection point and the ground plane, the fourth connection point being located between the center of the radiator and the second connection point.

With reference to the second aspect, in certain implementations of the second aspect, the radiator is provided with one or more insulating slits, and each slit has a width greater than or equal to 0.1mm and less than or equal to 2mm.

With reference to the second aspect, in some implementations of the second aspect, the electronic device further includes a conductive bezel, where the bezel has a first position and a second position, and the bezel between the first position and the second position acts as the radiator, and where the bezel is continuous with a rest of the bezel.

In a third aspect, an electronic device is provided, comprising: a radiator comprising a first portion, the first portion of the radiator comprising a first end and a second end, and a first connection point and a feed point between the first end and the second end, wherein the second end is an open end; a floor through which the radiator is grounded at the first end; a first inductor, the inductance value of which is smaller than a first threshold value; wherein the length of the first portion is greater than three-eighths of a first wavelength, the first portion being for generating a first resonance, the first wavelength being a medium wavelength of the first resonance; the first inductor is electrically connected between the first connection point and the floor, and the first connection point is arranged between the feed point and the first end; the first connection point is less than a quarter of the first wavelength from the second end.

With reference to the third aspect, in certain implementations of the third aspect, the radiator further includes a second connection point located between the first connection point and the first end; the electronic device further includes a second inductor electrically connected between the first connection point and the floor.

With reference to the third aspect, in certain implementations of the third aspect, the radiator further includes a second portion including a third end and a fourth end, and a third connection point between the third end and the fourth end, the first end of the first portion being connected with the third end of the second portion to form a continuous radiator, wherein the fourth end is an open end; a third inductor electrically connected between the third connection point and the floor, wherein an inductance value of the third inductor is smaller than the second threshold value; the length of the first portion is different from the length of the second portion; the second portion having a length greater than three-eighths of a second wavelength, the second portion being configured to produce a second resonance, the second wavelength being a medium wavelength of the second resonance; the third connection point is less than a quarter of the second wavelength from the fourth end.

With reference to the third aspect, in certain implementations of the third aspect, when a frequency of the first resonance is less than or equal to 1GHz, the first threshold is 6nH; when the frequency of the first resonance is greater than 1GHz and less than or equal to 2.2GHz, the first threshold is 4nH; when the frequency of the first resonance is greater than 2.2GHz and less than or equal to 3GHz, the first threshold is 3nH; when the frequency of the first resonance is greater than 3GHz, the first threshold is 2nH.

With reference to the third aspect, in certain implementations of the third aspect, when a frequency of the second resonance is less than or equal to 1GHz, the second threshold is 6nH; when the frequency of the second resonance is greater than 1GHz and less than or equal to 2.2GHz, the second threshold is 4nH; when the frequency of the second resonance is greater than 2.2GHz and less than or equal to 3GHz, the second threshold is 3nH; when the frequency of the second resonance is greater than 3GHz, the second threshold is 2nH.

With reference to the third aspect, in certain implementations of the third aspect, the electronic device further includes: a fourth inductor electrically connected between a corresponding at least one fourth connection point and the ground, the fourth connection point being located between the first end and the first connection point; and/or a fifth inductor electrically connected between a respective at least one fifth connection point and the ground plane, the fifth connection point being located between the fourth end and the third connection point.

In a fourth aspect, there is provided an electronic device comprising: a radiator including a first end and a second end, and a first connection point and a second connection point between the first end and the second end; a floor through which the radiator is grounded; the first inductor is electrically connected between the first connecting point and the floor, and the inductance value of the first inductor is smaller than or equal to a first threshold value; the second inductor is electrically connected between the second connection point and the floor, and the inductance value of the second inductor is smaller than or equal to the first threshold value; the portion of the radiator from the first end to the second end is used for generating first resonance, the current of the radiator in a first area and/or the current of the floor in a second area comprise a current reversing area, the first area comprises the first connection point and the second connection point, and the second area comprises the first inductor and the floor connection point and the second inductor and the floor connection point; and/or when the radiator generates the first resonance, a magnetic field generated by the radiator between the first area and the floor is in the same direction.

With reference to the fourth aspect, in some implementations of the fourth aspect, no switch is included between the first inductor and either the radiator or the floor, and no switch is included between the second inductor and either the radiator or the floor.

With reference to the fourth aspect, in certain implementations of the fourth aspect, when the frequency of the first resonance is less than or equal to 1GHz, the first threshold is 6nH; when the frequency of the first resonance is greater than 1GHz and less than or equal to 2.2GHz, the first threshold is 4nH; when the frequency of the first resonance is greater than 2.2GHz and less than or equal to 3GHz, the first threshold is 3nH; when the frequency of the first resonance is greater than 3GHz, the first threshold is 2nH.

With reference to the fourth aspect, in some implementations of the fourth aspect, the radiator is provided with an insulation slit; when the radiator generates the first resonance, the current of the radiator in a fifth area does not comprise a current reversing area, and the fifth area comprises the insulation gap; and/or the magnetic field of the radiator in the fifth region comprises a magnetic field reversal region when the radiator generates the first resonance.

Drawings

Fig. 1 is a schematic diagram of an electronic device according to an embodiment of the present application.

Fig. 2 is a schematic diagram of a common mode structure of a line antenna and corresponding current and electric field distribution.

Fig. 3 is a schematic diagram of a differential mode structure of a line antenna and corresponding current and electric field distribution.

Fig. 4 is a graph showing the structure of the common mode of the slot antenna and the corresponding current, electric field and magnetic current distribution.

Fig. 5 is a diagram showing the structure of the differential mode of the slot antenna and the corresponding current, electric field and magnetic current distribution.

Fig. 6 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 7 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 8 is a diagram of simulation results of the antenna structure shown in fig. 6.

Fig. 9 is a diagram of simulation results of the antenna structure shown in fig. 7 (a).

Fig. 10 is a schematic diagram of an antenna structure 100 according to an embodiment of the present application.

Fig. 11 is a schematic diagram of an electronic device according to an embodiment of the present application.

Fig. 12 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 13 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 14 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 15 is an S-parameter diagram of the antenna structure shown in fig. 12 to 14 according to an embodiment of the present application.

Fig. 16 is a diagram of simulation results of system efficiency and radiation efficiency of the antenna structures shown in fig. 12 to 14 according to an embodiment of the present application.

Fig. 17 is a schematic diagram of the current and electric field of the antenna structure of fig. 12.

Fig. 18 is a schematic diagram of the current and electric field of the antenna structure of fig. 13.

Fig. 19 is a schematic diagram of the current and electric field of the antenna structure of fig. 14.

Fig. 20 is a schematic diagram of another antenna structure according to an embodiment of the present application.

Fig. 21 is an S-parameter diagram of the antenna structure shown in fig. 12, fig. 14 and fig. 20 according to an embodiment of the present application.

Fig. 22 is a schematic diagram of the antenna structure of fig. 12, 14 and 20 according to an embodiment of the present application, wherein the radiator has a conductivity of 10 ⁵ Simulation results for system efficiency and radiation efficiency of magnitude.

Fig. 23 is a schematic diagram of the antenna structure of fig. 12, 14 and 20 according to an embodiment of the present application, in which the radiator has a conductivity of 10 ⁶ Simulation results for system efficiency and radiation efficiency of magnitude.

Fig. 24 is a schematic diagram of the current distribution of the antenna structure of fig. 12.

Fig. 25 is a schematic diagram of the current distribution of the antenna structure shown in fig. 14.

Fig. 26 is a current distribution diagram of the antenna structure shown in fig. 20.

Fig. 27 is a schematic diagram of another antenna structure according to an embodiment of the present application.

Fig. 28 is a current distribution diagram of the antenna structure shown in fig. 27.

Fig. 29 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 30 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 31 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 32 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 33 is an S-parameter diagram of the antenna structure shown in fig. 29 to 32 according to an embodiment of the present application.

Fig. 34 is a diagram of simulation results of system efficiency and radiation efficiency of the antenna structure shown in fig. 29 to 32 according to an embodiment of the present application.

Fig. 35 is a schematic diagram of an antenna structure 200 according to an embodiment of the present application.

Fig. 36 is a schematic diagram of another antenna structure 200 according to an embodiment of the present application.

Fig. 37 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 38 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 39 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 40 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 41 is an S-parameter diagram of the antenna structure shown in fig. 37 to 40 according to an embodiment of the present application.

Fig. 42 is a diagram showing simulation results of system efficiency and radiation efficiency of the antenna structures shown in fig. 37 to 40 according to an embodiment of the present application.

Fig. 43 is a schematic diagram of the distribution of current and electric field for the antenna structure of fig. 38.

Fig. 44 is a schematic diagram of the current and electric field distribution of the antenna structure of fig. 39.

Fig. 45 is a schematic diagram of the distribution of current and electric field for the antenna structure of fig. 40.

Fig. 46 is a schematic diagram of another antenna structure according to an embodiment of the present application.

Fig. 47 is a schematic diagram of another antenna structure according to an embodiment of the present application.

Fig. 48 is an S-parameter diagram of the antenna structure shown in fig. 37, fig. 39, fig. 46 and fig. 47 provided in an embodiment of the present application.

Fig. 49 is a graph of simulation results of system efficiency and radiation efficiency of the antenna structures of fig. 37, 39, 46 and 47 provided by an embodiment of the present application.

Fig. 50 is a schematic diagram of the current distribution of the antenna structure of fig. 37.

Fig. 51 is a schematic diagram of the current distribution of the antenna structure of fig. 39.

Fig. 52 is a schematic diagram of the current distribution of the antenna structure of fig. 46.

Fig. 53 is a current distribution diagram of the antenna structure shown in fig. 47.

Fig. 54 is a schematic diagram of an antenna structure 300 according to an embodiment of the present application.

Fig. 55 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 56 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 57 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 58 is an S-parameter diagram of the antenna structure shown in fig. 55 to 57 according to an embodiment of the present application.

Fig. 59 is a diagram showing simulation results of system efficiency and radiation efficiency of the antenna structure shown in fig. 55 to 57 according to an embodiment of the present application.

Fig. 60 is a schematic diagram of the current and electric field of the antenna structure of fig. 55.

Fig. 61 is a schematic diagram of the current and electric field of the antenna structure of fig. 56.

Fig. 62 is a schematic diagram of the current and electric field of the antenna structure of fig. 57.

Fig. 63 is a schematic diagram of another antenna structure according to an embodiment of the present application.

Fig. 64 is an S-parameter diagram of the antenna structure shown in fig. 55, 57 and 63 according to an embodiment of the present application.

Fig. 65 shows the antenna structure of fig. 55, 57 and 63 with a radiator conductivity of 10 according to an embodiment of the present application ⁵ Simulation results for system efficiency and radiation efficiency of magnitude.

Fig. 66 shows the antenna structure of fig. 55, 57 and 63 with a radiator conductivity of 10 according to an embodiment of the present application ⁶ Simulation results for system efficiency and radiation efficiency of magnitude.

Fig. 67 is a current distribution diagram of the antenna structure of fig. 55.

Fig. 68 is a current distribution diagram of the antenna structure of fig. 57.

Fig. 69 is a schematic diagram of a current distribution corresponding to the antenna structure shown in fig. 63 when the inductance value is large.

Fig. 70 is a schematic diagram of a current distribution corresponding to the antenna structure shown in fig. 63 when the inductance value is small.

Fig. 71 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 72 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 73 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 74 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 75 is an S-parameter diagram of the antenna structure shown in fig. 71 to 74 according to an embodiment of the present application.

Fig. 76 is a diagram of simulation results of system efficiency and radiation efficiency of the antenna structures shown in fig. 71-74 provided by an embodiment of the present application.

Fig. 77 is a schematic diagram of an antenna structure 400 according to an embodiment of the present application.

Fig. 78 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 79 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 80 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 81 is a schematic diagram of an antenna structure according to an embodiment of the present application.

Fig. 82 is an S-parameter diagram of the antenna structure shown in fig. 78 to 81 in CM mode according to an embodiment of the present application.

Fig. 83 is a diagram of simulation results of system efficiency and radiation efficiency in CM mode for the antenna structures shown in fig. 78 to 81 according to an embodiment of the present application.

Fig. 84 is an S-parameter diagram of the antenna structure shown in fig. 78 to 81 in the DM mode according to an embodiment of the present application.

Fig. 85 is a diagram of simulation results of system efficiency and radiation efficiency of the antenna structure shown in fig. 78 to 81 in the DM mode according to an embodiment of the present application.

Fig. 86 is an S-parameter diagram of the antenna structure shown in fig. 78 to 81 according to an embodiment of the present application.

Fig. 87 is a diagram showing simulation results of system efficiency and radiation efficiency of the antenna structures shown in fig. 78 to 81 according to an embodiment of the present application.

Detailed Description

Hereinafter, terms that may appear in the embodiments of the present application will be explained.

Coupling: it is to be understood that a direct coupling and/or an indirect coupling, and that "coupled connection" is to be understood as a direct coupling connection and/or an indirect coupling connection. Direct coupling may also be referred to as "electrical connection," meaning that the components are in physical contact and electrically conductive; the circuit structure can also be understood as a form of connecting different components through solid circuits which can transmit electric signals, such as copper foils or wires of a printed circuit board (printed circuit board, PCB) and the like; an "indirect coupling" is understood to mean that the two conductors are electrically conductive by means of a space/no contact. In one embodiment, the indirect coupling may also be referred to as capacitive coupling, such as by coupling between a gap between two conductive elements to form an equivalent capacitance to effect signal transmission.

Connection/association: may refer to a mechanical or physical connection, for example, a and B connection or a and B connection may refer to the presence of a fastening member (e.g., screw, bolt, rivet, etc.) between a and B, or a and B in contact with each other and a and B are difficult to separate.

Switching on: the above electrical connection or indirect coupling means may be used to conduct or connect two or more components to perform signal/energy transmission, which may be called on.

Capacitance: which may be understood as lumped capacitance and/or distributed capacitance. Lumped capacitance refers to components that are capacitive, such as capacitive elements; the distributed capacitance (or distributed capacitance) refers to an equivalent capacitance formed by two conductive members with a certain gap therebetween.

Resonance/resonant frequency: the resonance frequency is also called resonance frequency. The resonant frequency may refer to a frequency at which the imaginary part of the input impedance of the antenna is zero. The resonance frequency may have a frequency range, i.e. a frequency range in which resonance occurs. The frequency corresponding to the strongest resonance point is the center frequency point frequency. The return loss characteristic of the center frequency may be less than-20 dB. It should be understood that, unless otherwise specified, reference to "resonance of an antenna/radiator" in the present application shall refer to either the fundamental mode resonance of the antenna/radiator or the lowest frequency resonance of the antenna/radiator.

Resonance frequency band/communication frequency band/operating frequency band: whatever the type of antenna, it always operates in a certain frequency range (frequency band width). For example, an antenna supporting the B40 band has an operating band including frequencies in the range of 2300MHz to 2400MHz, or stated otherwise, the operating band of the antenna includes the B40 band. The frequency range meeting the index requirements can be regarded as the operating frequency band of the antenna.

Electrical length: may refer to the ratio of the physical length (i.e., mechanical length or geometric length) to the wavelength of the transmitted electromagnetic wave, the electrical length may satisfy the following equation:

where L is the physical length and λ is the wavelength of the electromagnetic wave.

In some embodiments of the application, the physical length of the radiator may be understood as being within + -25%, such as within + -10%, of the electrical length of the radiator.

Wavelength: or the operating wavelength may be a wavelength corresponding to the center frequency of the resonant frequency or the center frequency of the operating frequency band supported by the antenna. For example, assuming that the center frequency of the B1 upstream band (resonance frequency of 1920MHz to 1980 MHz) is 1955MHz, the operating wavelength may be a wavelength calculated using the frequency of 1955 MHz. The "operating wavelength" may also refer to, without limitation to the center frequency, a wavelength corresponding to a resonance frequency or a non-center frequency of an operating frequency band.

It should be understood that the wavelength (operating wavelength) may be understood as the wavelength of electromagnetic waves in a medium, for example, the wavelength of electromagnetic waves generated by a radiator transmitted in a medium and the wavelength transmitted in vacuum satisfy the following equation:

wherein lambda is _ε Lambda is the wavelength of electromagnetic waves in a medium _c For the wavelength of electromagnetic waves in vacuum, ε _r Is the relative dielectric constant of the medium in the dielectric layer. The wavelength in the embodiment of the present application is generally referred to as a dielectric wavelength, which may be a dielectric wavelength corresponding to a center frequency of a resonant frequency, or a dielectric wavelength corresponding to a center frequency of an operating frequency band supported by an antenna. For example, assuming that the center frequency of the B1 upstream band (resonance frequency of 1920MHz to 1980 MHz) is 1955MHz, that wavelength may be a medium wavelength calculated using this frequency of 1955 MHz. The "dielectric wavelength" may also refer to, without limitation to the center frequency, a dielectric wavelength corresponding to a resonance frequency or a non-center frequency of the operating frequency band. For ease of understanding, the medium wavelengths mentioned in the embodiments of the present application may be calculated simply by the relative dielectric constants of the medium filled in one or more sides of the radiator.

The definition of the position, the distance, and the like, such as the middle or the middle position, in the embodiment of the application is all the definition of the current technology, not the absolute strict definition in the mathematical sense. For example, the middle (position) of a conductor may refer to a section of conductor on the conductor that includes a midpoint, e.g., the middle (position) of a conductor may refer to a section of conductor on the conductor that is less than a predetermined threshold (e.g., 1mm,2mm, or 2.5 mm) from the midpoint.

Antenna system efficiency (total efficiency): refers to the ratio of the input power to the output power at the port of the antenna.

Antenna radiation efficiency (radiation efficiency): refers to the ratio of the power radiated out of the antenna to space (i.e., the power that effectively converts the electromagnetic wave portion) to the active power input to the antenna. Wherein active power input to the antenna = input power of the antenna-loss power; the loss power mainly includes return loss power and ohmic loss power and/or dielectric loss power of metal. The radiation efficiency is a value for measuring the radiation capacity of the antenna, and the metal loss and the dielectric loss are both influencing factors of the radiation efficiency.

Those skilled in the art will appreciate that the efficiency is generally expressed in terms of a percentage, which has a corresponding scaling relationship with dB, the closer the efficiency is to 0dB, the better the efficiency characterizing the antenna.

Antenna return loss: it is understood that the ratio of the signal power reflected back through the antenna circuit to the antenna port transmit power. The smaller the reflected signal, the larger the signal radiated into space through the antenna, the greater the radiation efficiency of the antenna. The larger the reflected signal, the smaller the signal radiated into space through the antenna, and the smaller the radiation efficiency of the antenna.

The antenna return loss can be represented by an S11 parameter, S11 belonging to one of the S parameters. S11 represents a reflection coefficient, which can characterize the quality of the antenna transmission efficiency. The S11 parameter is usually a negative number, and the smaller the S11 parameter, the smaller the return loss of the antenna, and the smaller the energy reflected by the antenna, that is, the more energy actually enters the antenna, the higher the system efficiency of the antenna; the larger the S11 parameter, the larger the antenna return loss, and the lower the system efficiency of the antenna.

It should be noted that, engineering generally uses an S11 value of-6 dB as a standard, and when the S11 value of the antenna is smaller than-6 dB, the antenna can be considered to work normally, or the transmission efficiency of the antenna can be considered to be better.

Electromagnetic wave absorption ratio (specific absorption rate, SAR): is a unit of representation of how much radio frequency radiant energy is actually absorbed by the body, called the specific absorption ratio, expressed in watts per kilogram (W/kg) or milliwatts per gram (mW/g). The exact definition of SAR is: the unit energy (dw) absorbed per unit substance (dm) per unit volume (dv) at a given substance density (ρ—human tissue density) is derivative with respect to time.

There are two international standards, one being the European standard 2w/kg and one being the US standard 1.6w/kg, the specific meaning of which is that the electromagnetic radiation energy absorbed per kilogram of human tissue must not exceed 2 watts, measured in 6 minutes.

Floor, or floor: may refer broadly to at least a portion of any ground layer, or ground plate, or ground metal layer, etc., or at least a portion of any combination of any of the above, or ground plates, or ground components, etc., within an electronic device (such as a cell phone), and "ground" may be used for grounding of components within the electronic device. In one embodiment, the "ground" may be a ground layer of a circuit board of the electronic device, or may be a ground plate formed by a middle frame of the electronic device or a ground metal layer formed by a metal film under a screen. In one embodiment, the circuit board may be a printed circuit board (printed circuit board, PCB), such as an 8-, 10-, 13-or 12-to 14-ply board having 8, 10, 12, 13 or 14 layers of conductive material, or elements separated and electrically insulated by dielectric or insulating layers such as fiberglass, polymers, or the like. In one embodiment, the circuit board includes a dielectric substrate, a ground layer, and a trace layer, the trace layer and the ground layer being electrically connected by vias.

Any of the above ground layers, or ground plates, or ground metal layers are made of conductive materials. In one embodiment, the conductive material may be any of the following materials: copper, aluminum, stainless steel, brass, and alloys thereof, copper foil on an insulating substrate, aluminum foil on an insulating substrate, gold foil on an insulating substrate, silver plated copper foil on an insulating substrate, silver foil and tin plated copper on an insulating substrate, cloth impregnated with graphite powder, graphite coated substrate, copper plated substrate, brass plated substrate, and aluminized substrate. Those skilled in the art will appreciate that the ground layer/plate/metal layer may be made of other conductive materials.

The technical scheme of the embodiment of the application will be described below with reference to the accompanying drawings.

As shown in fig. 1, the electronic device 10 may include: a cover (cover) 13, a display/module (display) 15, a printed circuit board (printed circuit board, PCB) 17, a middle frame (middle frame) 19 and a rear cover (rear cover) 21. It should be appreciated that in some embodiments, the cover 13 may be a glass cover (cover glass) or may be replaced with a cover of other materials, such as an ultra thin glass material cover, a PET (Polyethylene terephthalate ) material cover, or the like.

The cover plate 13 may be tightly attached to the display module 15, and may be mainly used for protecting and preventing dust of the display module 15.

In one embodiment, the display module 15 may include a liquid crystal display panel (liquid crystal display, LCD), a light emitting diode (light emitting diode, LED) display panel, or an organic light-emitting diode (OLED) display panel, which is not limited in this embodiment of the present application.

The middle frame 19 mainly plays a role in supporting the whole machine. While the PCB17 is shown in fig. 1 as being disposed between the middle frame 19 and the rear cover 21, it should be understood that in one embodiment, the PCB17 may also be disposed between the middle frame 19 and the display module 15, and the embodiment of the application is not limited thereto. The printed circuit board PCB17 may be a flame retardant material (FR-4) dielectric board, a Rogers (Rogers) dielectric board, a hybrid dielectric board of Rogers and FR-4, or the like. Here, FR-4 is a code of a flame resistant material grade, and the Rogers dielectric board is a high frequency board. The PCB17 carries electronic components, such as radio frequency chips and the like. In one embodiment, a metal layer may be provided on the printed circuit board PCB 17. The metal layer may be used for grounding of electronic components carried on the printed circuit board PCB17, but also for grounding of other components, such as bracket antennas, frame antennas, etc., and may be referred to as a ground plate, or ground layer. In one embodiment, the metal layer may be formed by etching metal at the surface of any one of the dielectric plates in the PCB 17. In one embodiment, the metal layer for grounding may be provided on the printed circuit board PCB17 on a side near the center frame 19. In one embodiment, the edge of the printed circuit board PCB17 may be considered the edge of its ground plane. In one embodiment, the metal center 19 may also be used for grounding of the above elements. The electronic device 10 may also have other floors/ground plates/layers, as previously described, which are not described here.

The electronic device 10 may also include a battery (not shown). The battery may be disposed between the middle frame 19 and the rear cover 21, or may be disposed between the middle frame 19 and the display module 15, which is not limited in the embodiment of the present application. In some embodiments, the PCB17 is divided into a main board and a sub-board, and the battery may be disposed between the main board and the sub-board, wherein the main board may be disposed between the middle frame 19 and an upper edge of the battery, and the sub-board may be disposed between the middle frame 19 and a lower edge of the battery.

The electronic device 10 may further include a bezel 11, and the bezel 11 may be formed of a conductive material such as metal. The bezel 11 may be disposed between the display module 15 and the rear cover 21 and extend circumferentially around the periphery of the electronic device 10. The bezel 11 may have four sides surrounding the display module 15 to help secure the display module 15. In one implementation, the bezel 11 made of metal material may be used directly as a metal bezel of the electronic device 10, creating the appearance of a metal bezel suitable for use in metal industry design (industrial design, ID). In another implementation, the outer surface of the bezel 11 may also be a non-metallic material, such as a plastic bezel, forming the appearance of a non-metallic bezel, suitable for non-metallic ID.

The middle frame 19 may include the frame 11, and the middle frame 19 including the frame 11 is used as an integral piece, and may support the electronic device in the whole machine. The cover 13 and the rear cover 21 are respectively covered along the upper and lower edges of the frame to form a housing or case (housing) of the electronic device. In one embodiment, cover 13, back cover 21, bezel 11, and/or center 19 may be collectively referred to as a shell or housing of electronic device 10. It should be understood that "housing or shell" may be used to refer to a portion or all of any one of the lid 13, back cover 21, bezel 11, or center frame 19, or to a portion or all of any combination of the lid 13, back cover 21, bezel 11, or center frame 19.

The frame 11 on the middle frame 19 can be at least partially used as an antenna radiator to receive/transmit frequency signals, and a gap can exist between the part of the frame serving as the radiator and other parts of the middle frame 19, so that the antenna radiator is ensured to have a good radiation environment. In one embodiment, the middle frame 19 may be provided with an aperture at the portion of the rim that acts as a radiator to facilitate radiation by the antenna.

Alternatively, the bezel 11 may not be considered as part of the middle frame 19. In one embodiment, the rim 11 may be integrally formed with the middle frame 19. In another embodiment, the rim 11 may include inwardly extending protrusions to connect with the middle frame 19, for example, by means of clips, screws, welding, etc. The protruding member of the frame 11 may also be used for feeding the electrical signal such that at least a portion of the frame 11 acts as a radiator of the antenna for receiving/transmitting the frequency signal. A gap 42 may exist between the part of the frame serving as the radiator and the middle frame 30, so as to ensure that the antenna radiator has a good radiation environment, and thus the antenna has a good signal transmission function.

Wherein the rear cover 21 may be a rear cover made of a metal material; the rear cover can also be made of non-conductive materials, such as a glass rear cover, a plastic rear cover and other non-metal rear covers; it may also be a back cover made of both conductive and non-conductive materials. In one embodiment, the rear cover 21 comprising conductive material can replace the middle frame 19, and is integrated with the frame 11 to support the electronic devices in the whole machine; it should be understood that references to "center" of the present application shall include a center disposed within the housing for supporting the device as well as including conductive portions as part of the housing and for use in the back cover 21 for supporting the device.

In one embodiment, the conductive portions in the middle frame 19, and/or the back cover 21 may serve as a reference ground for the electronic device 10, wherein the bezel, PCB, etc. of the electronic device may be grounded through electrical connections to the middle frame.

The antenna of the electronic device 10 may also be arranged within the frame 11. When the bezel 11 of the electronic device 10 is a non-conductive material, the antenna radiator may be located within the electronic device 10 and disposed along the bezel 11. For example, the antenna radiator is disposed against the frame 11, so as to reduce the volume occupied by the antenna radiator as much as possible, and be closer to the outside of the electronic device 10, so as to achieve a better signal transmission effect. The antenna radiator being disposed close to the frame 11 means that the antenna radiator may be disposed close to the frame 11, or may be disposed close to the frame 11, for example, a certain small gap may be formed between the antenna radiator and the frame 11.

The antenna of the electronic device 10 may also be disposed within a housing, such as a bracket antenna, millimeter wave antenna, or the like (not shown in fig. 1). The clearance of the antenna arranged in the shell can be obtained by the middle frame, and/or the back cover, and/or the slotting/opening on any one of the display screens, or by the non-conductive slots/apertures formed between any two, and the clearance of the antenna can ensure the radiation performance of the antenna. It should be appreciated that the headroom of the antenna may be a non-conductive area formed by any conductive element within the electronic device 10 through which the antenna radiates signals to the external space. In one embodiment, the antenna 40 may be in the form of a flexible motherboard (flexible printed circuit, FPC) based antenna, a laser-direct-structuring (LDS) based antenna, or a microstrip antenna (microstrip disk antenna, MDA) or the like. In one embodiment, the antenna may also be a transparent structure embedded inside the screen of the electronic device 10, such that the antenna is a transparent antenna unit embedded inside the screen of the electronic device 10.

Fig. 1 only schematically illustrates some of the components included in the electronic device 10, and the actual shape, actual size, and actual configuration of these components are not limited by fig. 1.

It should be understood that in the embodiment of the present application, the surface where the display screen of the electronic device is located may be considered as the front surface, the surface where the rear cover is located is the back surface, and the surface where the bezel is located is the side surface.

It should be appreciated that in embodiments of the present application, the electronic device is considered to be held by a user (typically held vertically and facing the screen) in an orientation having a top, a bottom, a left side, and a right side. It should be appreciated that in embodiments of the present application, the electronic device is considered to be held by a user (typically held vertically and facing the screen) in an orientation having a top, a bottom, a left side, and a right side.

First, the present application will be described with reference to fig. 2 to 5, which will relate to four antenna modes. Fig. 2 is a schematic diagram of a common mode structure of a line antenna and corresponding current and electric field distribution. Fig. 3 is a schematic diagram of a differential mode structure of another line antenna and corresponding current and electric field distribution. Fig. 4 is a schematic diagram of a common mode structure of a slot antenna and corresponding current, electric field, and magnetic current distribution. Fig. 5 is a schematic diagram of a differential mode structure of another slot antenna and corresponding current, electric field, and magnetic current distribution.

1. Common Mode (CM) mode of a line antenna

Fig. 2 (a) shows that the radiator of the line antenna 40 is connected to ground (e.g., a floor, which may be a PCB) by a feeder 42. The line antenna 40 is connected to a feeding unit (not shown) at an intermediate position 41 and adopts symmetrical feeding (symmetrical feed). The feed unit may be connected to the intermediate position 41 of the line antenna 40 by a feed line 42. It should be understood that symmetrical feeding is understood to mean that the feeding unit is connected to the radiator at one end and to ground at the other end, wherein the feeding unit and the radiator connection point (feeding point) are located in the center of the radiator, which may be, for example, the midpoint of the aggregate structure or the midpoint of the electrical length (or a region within a certain range around the midpoint).

The intermediate position 41 of the line antenna 40, for example the intermediate position 41, may be the geometric centre of the line antenna, or the midpoint of the electrical length of the radiator, for example where the feed line 42 connects with the line antenna 40, covers the intermediate position 41.

Fig. 2 (b) shows the current and electric field distribution of the line antenna 40. As shown in fig. 2 (b), the current exhibits a symmetrical distribution, e.g. a reverse distribution, on both sides of the intermediate position 41; the electric field is equidirectional on both sides of the intermediate position 41. As shown in fig. 2 (b), the current at the feeder 42 exhibits a homodromous distribution. Such feeding shown in fig. 2 (a) may be referred to as CM feeding of the line antenna based on the current sharing at the feeder 42. Such a line antenna pattern shown in fig. 2 (b) may be referred to as a CM pattern of the line antenna (also simply referred to as a CM pattern, for example, for the line antenna, the CM pattern refers to a CM pattern of the line antenna) based on that the currents are symmetrically distributed on both sides where the radiator and the feeder 42 are connected. The current and the electric field shown in (b) of fig. 2 may be referred to as a CM mode current and an electric field of the line antenna, respectively.

The CM mode current, electric field of the line antenna is generated by two branches (e.g., two horizontal branches) of the line antenna 40 on either side of the intermediate position 41 as an antenna operating in the quarter wavelength mode. The current is strong at the middle position 41 of the line antenna 40 and weak at both ends of the line antenna 40. The electric field is weak at the middle position 41 of the line antenna 40 and strong at both ends of the line antenna 40.

2. Differential mode (differential mode, DM) mode of a line antenna

The two radiators of the line antenna 50 are shown connected to ground (e.g., a floor, which may be a PCB) by a feed line 52 as shown in fig. 3 (a). The line antenna 50 is connected to a feeding unit at an intermediate position 51 between the two radiators and adopts an antisymmetric feed (anti-symmetric feed). One end of the feeding unit is connected to one of the radiators through a feeding line 52, and the other end of the feeding unit is connected to the other radiator through the feeding line 52. The intermediate position 51 may be the geometric center of the line antenna or a gap formed between the radiators.

It should be understood that the reference to "central antisymmetric feed" in the present application is to be understood as meaning that the positive and negative poles of the feed unit are connected to two connection points near the above-mentioned midpoint of the radiator, respectively. The positive and negative electrodes of the feed unit output signals with the same amplitude and opposite phases, for example 180 DEG + -10 DEG phase difference.

Fig. 3 (b) shows the current and electric field distribution of the line antenna 50. As shown in fig. 3 (b), the current exhibits an asymmetric distribution, e.g., a homodromous distribution, across the middle position 51 of the line antenna 50; the electric field is inversely distributed on both sides of the intermediate position 51. As shown in (b) in fig. 3, the current at the feeder 52 exhibits an inverse distribution. Such feeding shown in fig. 3 (a) may be referred to as wire antenna DM feeding based on the current reverse distribution at the feeder 52. Such a line antenna pattern shown in fig. 3 (b) may be referred to as a DM pattern of a line antenna (may also be simply referred to as a DM pattern, for example, for a line antenna, the DM pattern refers to a DM pattern of a line antenna) based on that the currents exhibit an asymmetric distribution (e.g., a homodromous distribution) on both sides where the radiator and the power feed line 52 are connected. The current and the electric field shown in (b) of fig. 3 may be referred to as a current and an electric field of the DM mode of the line antenna, respectively.

The current, electric field, of the DM mode of the line antenna is generated by the entire line antenna 50 as an antenna operating in the half wavelength mode. The current is strong at the middle position 51 of the line antenna 50 and weak at both ends of the line antenna 50. The electric field is weak at the middle position 51 of the line antenna 50 and strong at both ends of the line antenna 50.

It should be understood that for the radiator of the line antenna, it is understood that the number of metallic structures generating radiation may be one, as shown in fig. 2, or two, as shown in fig. 3, which may be adapted to the actual design or production needs. For example, for the CM mode of the line antenna, as shown in fig. 3, two radiators may be used, two ends of the two radiators are disposed opposite to each other with a gap therebetween, and symmetrical feeding is adopted at two ends of the two radiators close to each other, for example, the same feed signal is fed to two ends of the two radiators close to each other, so that an effect similar to that of the antenna structure shown in fig. 2 may be obtained. Accordingly, for the DM mode of the line antenna, as shown in fig. 2, a radiator may be used, two feeding points are disposed in the middle of the radiator and an antisymmetric feeding mode is adopted, for example, two symmetrical feeding points on the radiator are respectively fed with signals with the same amplitude and opposite phases, and an effect similar to that of the antenna structure shown in fig. 3 may be obtained.

3. CM mode of slot antenna

The slot antenna 60 shown in fig. 4 (a) may be formed by having a hollowed slot or slit 61 in the radiator of the slot antenna, or may be formed by surrounding the slot or slot 61 with the ground (for example, a floor board, may be a PCB). The groove 61 may be formed by grooving the floor. One side of the slot 61 is provided with an opening 62, and the opening 62 may be provided in a specific middle position of the side. The middle position of the side of the slot 61 may be, for example, the geometrical midpoint of the slot antenna, or the midpoint of the electrical length of the radiator, for example, the middle position of the side covered by the area where the opening 62 is open on the radiator. The opening 62 may be connected to a feeding unit and fed in an antisymmetric manner. It should be understood that the anti-symmetric feeding is understood as meaning that the positive and negative poles of the feeding unit are connected to the two ends of the radiator, respectively. The positive and negative electrodes of the feed unit output signals with the same amplitude and opposite phases, for example 180 DEG + -10 DEG phase difference.

Fig. 4 (b) shows the current, electric field, and magnetic current distribution of the slot antenna 60. As shown in fig. 4 (b), the current is distributed in the same direction around the slot 61 on the conductor (e.g., floor, and/or radiator 60) around the slot 61, the electric field is distributed in opposite directions on both sides of the middle of the slot 61, and the magnetic current is distributed in opposite directions on both sides of the middle of the slot 61. As shown in fig. 4 (b), the electric field at the opening 62 (e.g., at the feed) is co-directional and the magnetic current at the opening 62 (e.g., at the feed) is co-directional. Such a feed shown in fig. 4 (a) may be referred to as a slot antenna CM feed based on the magnetic flow co-direction at the opening 62 (feed). Such a slot antenna pattern shown in fig. 4 (b) may be referred to as a CM pattern of the slot antenna (which may also be referred to simply as CM pattern, for example for a slot antenna, CM pattern refers to a CM pattern of the slot antenna) based on the current exhibiting an asymmetric distribution (e.g., a homodromous distribution) on the radiator on both sides of the opening 62, or based on the current exhibiting a homodromous distribution around the slot 61 on the conductor around the slot 61. The electric field, current, magnetic current distribution shown in fig. 4 (b) may be referred to as CM mode electric field, current, magnetic current of the slot antenna.

The CM mode current and electric field of the slot antenna are generated by the slot antenna body on both sides of the middle position of the slot antenna 60 as an antenna operating in the half wavelength mode. The magnetic field is weak at the middle position of the slot antenna 60 and strong at both ends of the slot antenna 60. The electric field is strong at the middle position of the slot antenna 60 and weak at both ends of the slot antenna 60.

4. DM mode of slot antenna

As shown in fig. 5 (a), the slot antenna 70 may be formed by having a hollowed slot or slit 72 in the radiator of the slot antenna, or may be formed by surrounding the slot or slot 72 with the ground (e.g., a floor board, which may be a PCB). The groove 72 may be formed by grooving the floor. The feeding unit is connected in the middle position 71 of the slot 72 and is fed symmetrically. It should be understood that symmetrical feeding is understood to mean that the feeding unit is connected to the radiator at one end and to ground at the other end, wherein the feeding unit and the radiator connection point (feeding point) are located in the center of the radiator, which may be, for example, the midpoint of the aggregate structure or the midpoint of the electrical length (or a region within a certain range around the midpoint). The middle position of one side of the slot 72 is connected with the positive electrode of the power supply unit, and the middle position of the other side of the slot 72 is connected with the negative electrode of the power supply unit. The middle position of the side of the slot 72 may be, for example, the middle position of the slot antenna 60/the middle position of the ground, such as the geometrical midpoint of the slot antenna, or the midpoint of the electrical length of the radiator, such as the middle position 51 where the feed unit and the radiator are connected, covering the side.

Fig. 5 (b) shows the current, electric field, and magnetic current distribution of the slot antenna 70. As shown in fig. 5 (b), on the conductor (e.g., floor, and/or radiator 60) surrounding the slot 72, the current is distributed around the slot 72 and is distributed in opposite directions on both sides of the middle position of the slot 72, the electric field is distributed in the same direction on both sides of the middle position 71, and the magnetic current is distributed in the same direction on both sides of the middle position 71. The magnetic flow at the feed unit is inversely distributed (not shown). Such feeding shown in fig. 5 (a) may be referred to as slot antenna DM feeding based on the magnetic current at the feeding unit being inversely distributed. Such a slot antenna pattern shown in fig. 5 (b) may be referred to as a DM pattern of a slot antenna (which may also be simply referred to as a DM pattern, for example, for a slot antenna, the DM pattern refers to a DM pattern of a slot antenna) based on the current exhibiting a symmetrical distribution (e.g., a reverse distribution) on both sides of the connection of the feeding unit and the radiator, or based on the current exhibiting a symmetrical distribution (e.g., a reverse distribution) around the slot 71. The electric field, current, magnetic current distribution shown in fig. 5 (b) may be referred to as the DM mode electric field, current, magnetic current of the slot antenna.

The current, electric field, of the DM mode of the slot antenna is generated by the entire slot antenna 70 as an antenna operating in the one-time wavelength mode. The current is weak at the middle position of the slot antenna 70 and strong at both ends of the slot antenna 70. The electric field is strong at the middle position of the slot antenna 70 and weak at both ends of the slot antenna 70.

In the field of antennas, antennas operating in CM mode and antennas operating in DM mode generally have high isolation, and frequency bands of antennas of CM mode and DM mode generally tend to be single-mode resonances, and it is difficult to cover numerous frequency bands required for communication. In particular, the space reserved for the antenna structure by the electronic device is increasingly reduced, and for the MIMO system, a single antenna structure is required to realize multiple frequency band coverage, so that the multimode resonance has a high-isolation antenna at the same time, and has high research and practical values.

It will be appreciated that for the radiator of the slot antenna it is understood that the metallic structure that generates the radiation (e.g. comprising a part of the floor) may comprise an opening, as shown in fig. 4, or may be a complete ring, as shown in fig. 5, which may be adapted to the actual design or production requirements. For example, for CM mode of slot antenna, as shown in fig. 5, a complete loop radiator may be used, two feeding points are set at the middle position of the radiator on one side of the slot 61, and an antisymmetric feeding mode is used, for example, signals with the same amplitude and opposite phases are fed at two ends of the original opening position, and an effect similar to that of the antenna structure shown in fig. 4 may be obtained. Correspondingly, for the DM mode of the slot antenna, as shown in fig. 4, a radiator including an opening may be adopted, and symmetrical feeding is adopted at two ends of the opening, for example, two ends of the radiator at two sides of the opening are respectively fed with the same feed signal, so that an effect similar to the antenna structure shown in fig. 5 may be obtained.

The antenna structure can generate two working modes (the electric fields are symmetrically distributed or antisymmetrically distributed) with orthogonal electric fields (the inner product of the electric fields in the far field is zero (integral quadrature)), and the isolation between the two working modes of the antenna structure is good, so that the antenna structure can be applied to a multiple-input multiple-output (MIMO) antenna system in electronic equipment.

Fig. 6 and fig. 7 are schematic diagrams of an antenna structure according to an embodiment of the present application.

As shown in fig. 6 and 7, the radiator of the antenna structure is provided with a slit. By arranging the slots larger than or equal to the slots (the slots can be arranged at any position of the radiator, for example, the slots can be arranged between the feed point and the end part of the radiator), the equivalent radiation caliber of the antenna structure can be increased along with the increase of the number of the slots, the electric field distribution between the radiator and the floor can be more uniform, the dielectric loss is reduced, and the radiation efficiency is improved. In one embodiment, the slot structure may be equivalently a series capacitance in the radiator, and the antenna structure shown in fig. 6 and 7 may be referred to as a metamaterial (metaline) structure.

Meanwhile, with the line antenna structure shown in fig. 6 and the slot antenna structure shown in fig. 7, when the slot antenna structure is asymmetric, the CM mode and the DM mode of the antenna structure can be simultaneously excited. For example, a mode of asymmetrical feeding or asymmetrical radiator structure is adopted. For simplicity of discussion, the present application is described by taking only the CM mode and DM mode of the excitation antenna structure as an example, in which the feeding is performed by means of offset feeding (eccentric feeding).

The term "offset feed" in the present application is understood to mean an edge feed. In one embodiment, the connection point (feed point) between the feed unit and the radiator is offset from the centre of symmetry of the radiator (e.g. the centre point of the radiator). In one embodiment, the connection point (feeding point) between the feeding unit and the radiator is located at the end of the radiator and at a region within a quarter of the electrical length from the end point of the radiator (excluding the position of the quarter of the electrical length), or may be a region within a eighth of the first electrical length from the end point of the radiator, where the electrical length may refer to the electrical length of the radiator.

Fig. 8 and 9 are diagrams of simulation results of the antenna structures shown in fig. 6 and 7.

It should be understood that, in order to facilitate simulation of the CM mode and the DM mode generated by the antenna structure, the antenna structures shown in fig. 6 and fig. 7 are each simulated by adopting a central symmetric feeding manner and a central anti-symmetric feeding manner, so as to obtain simulation results shown in fig. 8 and fig. 9.

As shown in fig. 8 (a), a simulation result diagram of system efficiency and radiation efficiency of the line antenna shown in fig. 6 operating in the DM mode is shown. After the radiator is provided with a gap, the system efficiency and the radiation efficiency of the line antenna are effectively improved in the mode (DM mode). As shown in fig. 8 (b), a simulation result diagram of the system efficiency and the radiation efficiency of the line antenna shown in fig. 6 operating in CM mode is shown. When the radiator is provided with a slit, the system efficiency and the radiation efficiency of the line antenna are not effectively improved in the mode (CM mode).

As shown in fig. 9 (a), a simulation result diagram of the system efficiency and the radiation efficiency of the slot antenna shown in fig. 7 operating in CM mode is shown. After the radiator is provided with a gap, the system efficiency and the radiation efficiency of the slot antenna are effectively improved in the mode (CM mode). As shown in (b) of fig. 9, a graph of simulation results of system efficiency and radiation efficiency of the slot antenna shown in fig. 7 operating in the DM mode is shown. After the radiator is provided with a slot, the system efficiency and the radiation efficiency of the slot antenna are not effectively improved in the mode (DM mode).

Therefore, by opening a slot in the radiator to increase the radiator length of the antenna structure, dielectric loss is reduced, and the efficiency of the DM mode of the line antenna and the CM mode of the slot antenna can be improved, but the efficiency of the CM mode of the line antenna and the DM mode of the slot antenna is not greatly affected.

The embodiment of the application provides electronic equipment, which comprises a radiator and a floor, wherein the electric field between the radiator and the floor is more uniformly distributed by utilizing the inductance arranged between the radiator and the floor, so that the conductor loss is reduced, and the radiation efficiency of an antenna structure can be effectively improved.

Fig. 10 is a schematic diagram of an antenna structure 100 according to an embodiment of the present application, where the antenna structure 100 may be applied to the electronic device shown in fig. 1.

As shown in fig. 10, the antenna structure 100 may include a radiator 110, a ground plane 120, a first inductance 131, and a second inductance 132.

The radiator 110 includes a first end 101 and a second end 102 (the first end 101 and the second end 102 are open ends, and the radiator 110 is not connected to other conductors at the first end 101 and the second end 102), and a ground point 103, a first connection point 111, and a second connection point 112 between the first end 101 and the second end 102. The ground point 103 may be disposed at the central region 104 of the radiator 110. The radiator 110 is grounded at the ground point 103 through the floor 120. The inductance values of the first inductor 131 and the second inductor 132 are both smaller than the first threshold value. The length of the radiator 110 is greater than three-quarters of the first wavelength, and the portion of the radiator from the first end 101 to the second end 102 is used to create a first resonance, the first wavelength being the medium of the first resonance. The first inductor 131 is electrically connected between the first connection point 111 and the ground plate 120, and the second inductor 132 is electrically connected between the second connection point 112 and the ground plate 120. The distance between the first connection point 111 and the first end 101 is less than a quarter of the first wavelength and the second connection point 112 is located between the first connection point 111 and the second end 102.

It is understood that the central region 104 of the radiator 110 may be understood as a region within 5mm from the center of the radiator 110, and the center of the radiator 110 may be the center of the physical length (geometric center) or the center of the electrical length of the radiator 110.

In one embodiment, the radiator 110 may further comprise a feeding point 105, the feeding point 105 being configured to feed the antenna structure 100 with an electrical signal so that it generates radiation.

It should be understood that, in the technical solution provided in the embodiment of the present application, the inductance provided between the radiator and the floor may be utilized, so that when the feeding point feeds in an electrical signal, since the radiator 110 is electrically connected with the first inductance 131 and the second inductance 132 between the floor 120 and the first connection point 111 and the second connection point 112, respectively, the current on the radiator 110 is reversed in the area near the first connection point 111 and the second connection point 112. Correspondingly, the current on the floor board 120 is reversed in the area near the junction of the first inductor 131 and the second inductor 132 on the floor board 120. The current density on the radiator can be dispersed (the intensity of a single current strong point is reduced, so that the current is more uniformly distributed), thereby reducing the loss caused by the radiator and the conductors arranged around the radiator, and further improving the efficiency of the antenna structure.

In addition, since the current on the radiator 110 reverses in the area near the first connection point 111 and the second connection point 112, the electric field cannot reach the zero point at the first connection point 111 and the second connection point 112, so that the electric field generated by the radiator is continuous, no reversal occurs (the electric field reversing area is not included), no zero point exists, the radiation caliber of the antenna structure is increased, the conductor loss is reduced, and the efficiency of the antenna structure is improved. In one embodiment, the electric field generated by the radiator is co-directional from the first end to the second end of the radiator.

In one embodiment, no switch is provided between the radiator 110 and the inductor (e.g., no switch is provided between the first connection point 111 of the radiator 110 and the first inductor 131), or between the inductor and the floor 120 (e.g., no switch is provided between the first inductor 131 and the floor 120). The inductance (e.g., the first inductance 131 and the second inductance 132) connected in series between the radiator 110 and the floor 120 in the embodiment of the present application is used to disperse the current density on the radiator so as to reduce the loss caused by the radiator and the conductors disposed around the radiator. In one embodiment, the first inductance 131 and the second inductance 132 may affect the resonant frequency of the antenna structure to some extent, but are different from a tuning circuit used primarily to adjust the resonant frequency of the antenna structure. In addition, a switch is not arranged at the inductor to switch the frequency band, and the switch can introduce extra insertion loss and lose the radiation performance of the antenna structure.

In one embodiment, the distance between the first connection point 111 and the first end 101 is smaller than a quarter of the first wavelength, which may further improve the efficiency of the antenna structure.

In one embodiment, the feed point 105 is located between the central region 104 and the first end 101 or between the central region 104 and the second end 102. The antenna structure 100 may feed in an electrical signal in a bias feed manner, so that the antenna structure 100 may operate in a CM mode and a DM mode at the same time, and the operating frequency band of the antenna structure 100 is expanded.

It should be understood that, in the embodiments of the present application, for simplicity of discussion, only the CM mode and the DM mode of the antenna structure may be excited by the center symmetrical feed or the center antisymmetric feed in practical application, which is not limited to this, and may be adjusted according to the internal layout of the electronic device, which will be understood correspondingly in the embodiments described below.

In one embodiment, the inductance values of the first inductor 131 and the second inductor 132 may be designed according to the resonant frequency generated by the antenna structure 100. When the frequency of the first resonance is less than or equal to 1GHz, the first threshold is 6nH. The first threshold is 4nH when the frequency of the first resonance is greater than 1GHz and less than or equal to 2.2 GHz. When the frequency of the first resonance is greater than 2.2GHz and less than or equal to 3GHz, the first threshold is 3nH. When the frequency of the first resonance is greater than 3GHz, the first threshold is 2nH.

It should be understood that, the inductance values of the first inductor 131 and the second inductor 132 are designed according to the operating frequency bands of different antenna structures, so that the current distribution on the radiator is more uniform in the operating frequency bands, and the conductor loss is reduced, thereby improving the efficiency of the antenna structure.

In one embodiment, the electronic device further includes a conductive bezel 11, the bezel 11 having a first location 141 and a second location 142 thereon, the bezel 11 between the first location 141 and the second location 142 acting as the radiator 110, as shown in fig. 11. It should be appreciated that the first and second locations 141 and 142 may correspond to the first and second ends 101 and 102.

In one embodiment, the first and second positions 141 and 142 of the frame 11 may be provided with slits, so that the first and second positions 141 and 142 are not connected to other parts of the frame 11, so as to realize that the ends of the radiators of the first and second positions 141 and 142 are open ends. It should be understood that the first and second positions 141 and 142 may be located on the same side of the frame 11, the radiator 110 may be linear, or the first and second positions 141 and 142 may be located on two adjacent sides of the frame 11, and the radiator 110 may be of a polygonal line type, for example, an L-type.

The inductors (the first inductor 131, the second inductor 132, or other inductors described below) described in all embodiments of the present application may be lumped elements, or may be distributed elements, or a combination of lumped elements and distributed elements, which the present application is not limited to. In one embodiment, the first inductor 131 and/or the second inductor 132 may comprise distributed elements. For example, an inwardly extending conductive member on the bezel; and/or a conductive member extending over the middle frame; and/or a conductive member extending over the PCB; and/or metal traces on the PCB, etc. In one embodiment, as shown in fig. 11, the first inductor 131 may include a connection rib disposed between the inner frame 11 and the middle frame/PCB 17 of the electronic device. In one embodiment, as shown in fig. 11, the second inductor 132 may comprise a length of wire on the PCB 14.

In one embodiment, the first connection point 111 and the second connection point 112 are disposed on two sides of the ground point 103, respectively. The first connection point 111 is located between the first end 101 and the ground point 103, and the second connection point 112 is located between the second end 102 and the ground point 103. In one embodiment, the distance between the first connection point 111 and the first end 101 is less than a quarter of the first wavelength. In one embodiment, the distance between the second connection point 112 and the second end 102 is less than one quarter of the first wavelength.

It should be appreciated that the inductors are electrically connected to the two sides of the grounding point 103, so that the current on the radiator 110 on the two sides of the grounding point 103 is affected by the grounding inductance, and the current distribution on the radiator 110 is more uniform. Meanwhile, the electric field generated by the radiator 110 at two sides of the grounding point 103 does not comprise an electric field reversing area, so that the radiation caliber of the antenna structure is increased, the conductor loss is reduced, and the efficiency of the antenna structure is improved.

In one embodiment, the antenna structure 100 may further include at least one third inductor electrically connected between the respective at least one third connection point and the ground plane 120, and the at least one third inductor and the at least one third connection point may be in one-to-one correspondence, and the at least one third connection point is located between the ground point 103 and the first connection point 111.

In one embodiment, the antenna structure 100 may further include at least one fourth inductor electrically connected between the respective at least one fourth connection point and the ground plane 120, the at least one fourth inductor and the at least one fourth connection point may be in one-to-one correspondence, and the at least one fourth connection point is located between the ground point 103 and the second connection point 112.

It will be appreciated that increasing the number of inductances in the electrical connection between the radiator 110 and the floor 120 can result in a more uniform distribution of current density across the radiator, thereby reducing losses associated with the radiator and conductors disposed around the radiator. Meanwhile, the position of each radiator connected with the inductor comprises a current reversing area, so that the electric field cannot reach zero, the electric field generated by the radiator is continuous, the reverse direction (not comprising the electric field reversing area) does not occur, the radiation caliber of the antenna structure is increased, the conductor loss is reduced, and the efficiency of the antenna structure is improved. After setting the plurality of inductance values, the inductance threshold value needs to be increased accordingly, for example, when the number of inductances electrically connected between the radiator 110 and the floor 120 is greater than or equal to 3, and when the frequency of the first resonance is less than or equal to 1GHz, the first threshold value is 12nH. The first threshold is 8nH when the frequency of the first resonance is greater than 1GHz and less than or equal to 2.2 GHz. The first threshold is 6nH when the frequency of the first resonance is greater than 2.2GHz and less than or equal to 3 GHz. The first threshold is 4nH at a frequency of the first resonance greater than 3 GHz.

In one embodiment, the radiator 110 may be provided with one or more slits. It should be appreciated that providing an inductance between the radiator 110 and the floor 120 may improve the efficiency of the antenna structure 100 in CM mode, and providing a slot in the radiator 110 may improve the efficiency of the antenna structure 100 in DM mode. In one embodiment, the slit structure formed on the radiator 110 may be equivalent to a capacitor, so that the radiator 110 is equivalent to a metamaterial structure with a series capacitor.

Fig. 12 to 14 are schematic diagrams of a set of antenna structures according to an embodiment of the present application.

As shown in fig. 12 to 14, the different structures of the line antennas are schematic diagrams. The antenna structure shown in fig. 13 is different from the antenna structure shown in fig. 12 in that two slots are formed in the radiator, and the location of the slots (or capacitors) can be referred to in the foregoing embodiments. The antenna structure shown in fig. 14 is different from the antenna structure shown in fig. 12 in that two inductors are provided between the radiator and the floor, and the positions of the inductors can be referred to in the foregoing embodiments.

In one embodiment, as shown in fig. 13, the provision of a slot in the radiator may be considered as an equivalent capacitance (e.g., distributed capacitance) provided on the radiator. In one embodiment, the width of the slit is greater than or equal to 0.1mm and less than or equal to 2mm. In one embodiment, the two ends of the slit opened on the radiator may be connected in series with a capacitor (e.g., lumped capacitor) to form a metamaterial structure of the series capacitor. It should be appreciated that for purposes of visual presentation of a comparison of antenna efficiency for a line antenna operating in CM mode, an antenna configuration is described using a centrosymmetric feed as an example. Meanwhile, the antenna structure shown in fig. 12 to 14 is operated in a half wavelength mode in CM mode, and the operation frequency band thereof includes 1.9GHz for example. To ensure that the antenna structures shown in fig. 12 to 14 operate in the same frequency band, the length of the radiator in the antenna structure is adjusted. In the antenna structure shown in fig. 12, the radiator has a length of 36mm. In the antenna structure shown in fig. 13, the radiator has a length of 60mm, and the equivalent capacitance value of the distributed capacitor at both ends of the slot or the capacitance value of the series lumped capacitor is 0.75pF. In the antenna structure shown in fig. 14, the radiator length was 58mm, and the inductance values of the series inductance were 2.7nH.

Fig. 15 and 16 are diagrams of simulation results of the antenna structures shown in fig. 12 to 14. Fig. 15 is an S-parameter diagram of the antenna structure shown in fig. 12 to 14 according to an embodiment of the present application. Fig. 16 is a diagram of simulation results of system efficiency and radiation efficiency of the antenna structures shown in fig. 12 to 14 according to an embodiment of the present application.

As shown in fig. 15, taking S11< -4dB as an example, the antenna structure shown in fig. 12 to 14 operates in CM mode, the operating frequency bands each include 1.87GHz to 1.97GHz, and the bandwidth generated by resonance of the antenna structure shown in fig. 13 is wider.

As shown in fig. 16, in the above frequency band, the efficiency (system efficiency and radiation efficiency) of the antenna structure shown in fig. 13 is substantially the same as that of the antenna structure shown in fig. 12. The antenna structure shown in fig. 14 has a significant improvement in system efficiency at 1.92Hz, which is about 1dB improvement in radiation efficiency, compared to the antenna structure shown in fig. 12, due to the increased inductance provided between the radiator and the floor.

Fig. 17 to 19 are schematic diagrams of currents and electric fields of the antenna structures shown in fig. 12 to 14. Wherein fig. 17 is a schematic diagram of the current and electric field of the antenna structure of fig. 12. Fig. 18 is a schematic diagram of the current and electric field of the antenna structure of fig. 13. Fig. 19 is a schematic diagram of the current and electric field of the antenna structure of fig. 14.

As shown in fig. 17 (a), the antenna structure operates in a half wavelength mode in CM mode, and the current on the radiator at resonance does not have a zero point, and the current is concentrated in a region near the ground point. As shown in (b) of fig. 17, an electric field generated between the radiator and the floor when the antenna structure resonates is concentrated at both ends of the radiator.

As shown in fig. 18 (a), the antenna structure operates in a half wavelength mode in CM mode, and the current on the radiator at resonance does not have a zero point, and the current is concentrated in a region near the ground point. As shown in (b) of fig. 18, an electric field generated between the radiator and the floor when the antenna structure resonates is concentrated at both ends of the radiator and an area near the opened slit.

As shown in fig. 19 (a), the antenna structure operates in the half-wavelength mode in CM mode, and the current on the radiator at resonance has zero points in the area (on the radiator and the floor) near the junction inductance, and the current density is more dispersed than the simulation diagrams shown in fig. 17 and 18. As shown in fig. 19 (b), since the current density is more dispersed, the electric field generated between the radiator and the floor when the antenna structure resonates is reduced compared to the simulation diagrams shown in fig. 17 and 18, and the conductor loss can be reduced, thereby improving the efficiency of the antenna structure.

Fig. 20 is a schematic diagram of another antenna structure according to an embodiment of the present application

As for the antenna structure shown in fig. 20, the arrangement position of the inductors can be referred to the previous embodiment, and is different from the antenna structure shown in fig. 14 in that 4 inductors are arranged between the radiator and the floor.

In order to facilitate visual display of comparison of antenna efficiency of the line antenna operating in CM mode, the antenna structure is illustrated by using central symmetric feed as an example. To ensure that the antenna structures shown in fig. 12, 14 and 20 operate in the same frequency band, the length of the radiator in the antenna structure is adjusted. In the antenna structure shown in fig. 12, the radiator has a length of 35.6mm (about one-half of the first wavelength). In the antenna structure shown in fig. 14, the length of the radiator is 51.6mm (about three quarters of the first wavelength), the inductance values of the two series inductors are 2.7nH, and the two inductors are respectively located at two sides of the grounding point. In the antenna structure shown in fig. 20, the length of the radiator is 67mm (about the first wavelength), the inductance values of the inductors near both sides of the ground point are 5nH, and the inductance values of the inductors near both ends of the radiator are 5.5nH. Meanwhile, in order to ensure that the antenna structure shown in fig. 14 and 20 is identical to the resonance frequency point of the antenna structure shown in fig. 12, an inductance of 1.5nH is provided between the ground point of the radiator of the antenna structure shown in fig. 14 and the floor, and an inductance of 3nH is provided between the ground point of the radiator of the antenna structure shown in fig. 20 and the floor.

Fig. 21 to 23 are diagrams of simulation results of the antenna structures shown in fig. 12, 14 and 20. Fig. 21 is an S-parameter diagram of the antenna structure shown in fig. 12, fig. 14, and fig. 20 according to an embodiment of the present application. Fig. 22 is a graph of simulation results of the system efficiency and radiation efficiency of the antenna structure of fig. 14 and 20 at a radiator conductivity of the order of 105 provided by an embodiment of the present application. Fig. 23 is a graph of simulation results of the system efficiency and radiation efficiency of the antenna structure of fig. 14 and 20 at a radiator conductivity of the order of 106 provided by an embodiment of the present application.

As shown in fig. 21, taking S11< -4dB as an example, the antenna structure shown in fig. 12, 14 and 20 operates in CM mode, with a resonance frequency band around 1.85GHz, and with an increase in the number of inductors provided between the radiator and the floor, the resonance bandwidth thereof gradually widens.

As shown in fig. 22 and 23, as the number of inductors provided between the radiator and the floor increases, both the radiation efficiency and the system efficiency of the antenna structure increase significantly.

At a radiator conductivity of 10 ⁵ In the order of magnitude, at 1.85Hz, the antenna structure shown in fig. 20 has a radiation efficiency improvement of about 2.3dB as compared to the antenna structure shown in fig. 12, as shown in fig. 22.

At a radiator conductivity of 10 ⁶ In the order of magnitude, at 1.85Hz, the antenna structure shown in fig. 20 has a radiation efficiency improvement of about 1.4dB as compared to the antenna structure shown in fig. 12, as shown in fig. 23.

It should be appreciated that due to the inductance provided between the radiator and the floor, the radiator length of the antenna structure is extended from one half wavelength (the antenna structure shown in fig. 12) to one time wavelength (the antenna structure shown in fig. 20), the radiation aperture is increased, and the conductor loss is reduced, as shown in table 1 below. The conductor loss is the loss of radiation generated by the material (aluminum AL) of the radiator and the PCB where the floor is located. Dielectric losses are losses to radiation caused by plastic (ABS) and glass cover plates (CG) placed around the radiator.

TABLE 1

As shown in table 1 above, the inductance provided between the radiator and the floor can reduce the conductor loss, but the improvement in dielectric loss is not significant. And, as shown in fig. 22 and 23, the efficiency of the antenna structure is improved more remarkably after the conductivity of the radiator is reduced.

Fig. 24 to 26 are schematic diagrams of current distribution of the antenna structures shown in fig. 12, 14 and 20 operating in the same frequency band (e.g. around 1.85 GHz), respectively.

As shown in fig. 24 to 26, as the number of inductors electrically connected between the radiator and the floor increases, the zero point of the current on the radiator in the vicinity of the connection inductors (on the radiator and the floor) increases during resonance, so that the current density can be more dispersed, the conductor loss during radiation can be reduced, and the efficiency of the antenna structure can be improved.

As the antenna structure shown in fig. 27, the arrangement position of the inductors can be referred to the previous embodiment, which differs from the antenna structure shown in fig. 14 and 20 in that the number of inductors arranged between the radiator and the floor is 3 or more, for example, 6 inductors are arranged.

It will be appreciated that as the number of inductances provided between the radiator and the floor increases, the current distribution becomes more uniform as the antenna structure radiates, as shown in fig. 28.

Fig. 29 to 32 are schematic diagrams of a set of antenna structures according to an embodiment of the present application.

As shown in fig. 29 to 32, the different structures of the line antennas are schematic diagrams. The antenna structure shown in fig. 30 is different from the antenna structure shown in fig. 29 in that two slots are opened in the radiator. The antenna structure shown in fig. 31 is different from the antenna structure shown in fig. 30 in that two inductors are provided between the radiator and the floor. The antenna structure shown in fig. 32 is different from the antenna structure shown in fig. 29 in that two slots are opened in the radiator, and two inductors are provided between the radiator and the floor.

As shown in fig. 30 and 32, in one embodiment, the opening of the slot on the radiator may be regarded as an equivalent capacitance (e.g., a distributed capacitance) disposed on the radiator, and the location of the slot (or capacitance) and the inductance may be referred to in the previous embodiments. In one embodiment, the two ends of the slit opened on the radiator may be connected in series with a capacitor (e.g., lumped capacitor) to form a metamaterial structure of the series capacitor.

It should be appreciated that for purposes of visual illustration of comparison of antenna efficiency for a line antenna operating in CM and DM modes, the description will be given of an antenna configuration employing offset feed to excite both CM and DM modes. Meanwhile, the antenna structure shown in fig. 29 to 32 is operated in the CM mode and the half wavelength mode in DM, and the operation frequency band corresponding to the CM mode includes 1.95GHz and the operation frequency band corresponding to the DM mode includes 2.25GHz for example. To ensure that the antenna structures shown in fig. 29 to 32 operate in the same frequency band, the length of the radiator in the antenna structure is adjusted. In the antenna structure shown in fig. 29, the radiator has a length of 40mm. In the antenna structure shown in fig. 30, the length of the radiator is 54mm, and the feeding position of the antenna structure is asymmetric, so that the equivalent capacitance value of the distributed capacitor or the capacitance value of the lumped capacitor near the feeding point is 1pF, and the equivalent capacitance value of the distributed capacitor or the capacitance value of the lumped capacitor far from the feeding point is 1.4pF. In the antenna structure shown in fig. 31, the radiator has a length of 50mm, and the inductance of the inductor connected in series near the feeding point is 1.5nH, and the inductance of the inductor connected in series far from the feeding point is 3.3nH. In the antenna structure shown in fig. 32, the length of the radiator is 60mm, the equivalent capacitance value of the distributed capacitance or the capacitance value of the lumped capacitance at both ends of the slot close to the feeding point is 1pF, the inductance value of the inductance close to the feeding point is 2.5nH, the equivalent capacitance value of the distributed capacitance or the capacitance value of the lumped capacitance at both ends of the slot far from the feeding point is 1pF, and the inductance value of the inductance far from the feeding point is 4nH.

Fig. 33 and 34 are diagrams of simulation results of the antenna structures shown in fig. 29 to 32. Fig. 33 is an S-parameter diagram of the antenna structure shown in fig. 29 to 32 according to an embodiment of the present application. Fig. 34 is a diagram of simulation results of system efficiency and radiation efficiency of the antenna structure shown in fig. 29 to 32 according to an embodiment of the present application.

As shown in fig. 33, taking S11< -4dB as an example, the antenna structure shown in fig. 29 to 32 operates in CM mode and DM mode, and the operating frequency bands respectively include 1.9GHz to 2GHz (CM mode) and 2.2GHz to 2.3GHz (DM mode), and the bandwidth generated by the resonance of the antenna structure shown in fig. 32 is wider.

As shown in fig. 34, in the above frequency band, the antenna structure shown in fig. 30 can improve efficiency in the DM mode (2.2 GHz to 2.3 GHz) and the antenna structure shown in fig. 31 can improve efficiency in the CM mode (1.9 GHz to 2 GHz) compared to the efficiency (system efficiency and radiation efficiency) of the antenna structure shown in fig. 29. Because the antenna structure shown in fig. 32 combines the characteristics of the antenna structure shown in fig. 30 and the antenna structure shown in fig. 31, the efficiency of the antenna structure can be improved in both DM mode (2.2 GHz to 2.3 GHz) and CM mode (1.9 GHz to 2 GHz) by using the slots provided on the radiator and the inductance provided between the radiator and the floor.

The SAR values of the antenna structures shown in fig. 29 to 32 are shown in table 2 below, and are described by taking 24dbm as an example of input power.

TABLE 2

As shown in table 2 above, the SAR value at 2.25GHz (DM mode) is better for the antenna structure shown in fig. 30 than for the antenna structure shown in fig. 29, and the SAR value at 1.95GHz (CM mode) is better for the antenna structure shown in fig. 31. Since the antenna structure shown in fig. 32 combines the characteristics of the antenna structure shown in fig. 30 and the antenna structure shown in fig. 31, it exhibits good SAR values at 1.95GHz (CM mode) and 2.25GHz (DM mode).

As shown in fig. 35, the antenna structure 200 includes a radiator 210, a ground plate 220, a first inductance 231, and a feeding point 205.

Wherein the radiator 210 comprises a first portion 241, the first portion 241 comprising a first end 201 and a second end 202 (the second end 202 being an open end, the radiator 210 being unconnected to other conductors at the second end 102), and a first connection point 211 between the first end 201 and the second end 202. The radiator 210 is grounded at a first end 201 through a floor 220. The first inductor 231 is electrically connected between the first connection point 211 and the floor 220, and an inductance value of the first inductor 231 is smaller than a first threshold value. The length of the first portion 241 is greater than three-eighths of the first wavelength, which is used to create a first resonance, the first wavelength being the medium wavelength of the first resonance. The first connection point 211 is arranged between the feeding point 241 and the first end 201. The distance between the first connection point 211 and the second end 102 is less than or equal to a quarter of the first wavelength.

In one embodiment, the antenna structure 200 may include a second inductance 232. The second inductor 232 is electrically connected between the second connection point 212 and the ground 220, and the second connection point 212 is located between the first connection point 211 and the first end 201.

It should be understood that the technical solution provided in the embodiment of the present application may be applied to an inverted-L antenna (inverted L antenna) or an inverted-F antenna (inverted F antenna) (the feeding point 205 is close to the first end 201 (the ground end)), and for brevity of discussion, the embodiment of the present application is only described by taking the feeding point 205 as an example, and applying it to a left-hand antenna as an example. At least one inductor is provided between the first portion 241 and the floor 220, the current on the first portion 241 being reversed in the vicinity of the first connection point 211, wherein the current reversal area comprises the first connection point 211. Correspondingly, in the vicinity of the junction of the first inductor 231 and the second inductor 232 with the floor 220, the current on the floor 220 is reversed. The current density on the radiator can be dispersed (the intensity of a single current strong point is reduced, so that the current is uniformly distributed), thereby reducing conductor loss caused by the radiator and conductors arranged around the radiator, and further improving the efficiency of the antenna structure. In addition, since the current on the first portion 241 reverses in the vicinity of the first connection point 211 and the second connection point 212, the electric field cannot reach a zero point at the first connection point 211 and the second connection point 212, so that the electric field generated by the radiator is continuous, no reversal occurs (no electric field reversing area is included), no zero point exists, the radiation aperture of the antenna structure is increased, the conductor loss is reduced, and the efficiency of the antenna structure is improved. In one embodiment, the electric field between the first portion 241 of the radiator and the floor 220 is co-directional.

In one embodiment, the length of the first portion 241 is greater than one half of the first wavelength, wherein the distance between the first connection point 211 and the second connection point 212 is less than one half of the first wavelength, so as to disperse the current density on the radiator, and improve the efficiency of the antenna structure. In one embodiment, the distance between the first connection point 211 and the second connection point 212 may be less than a quarter of the first wavelength, so that the current density on the radiator is more dispersed, and the efficiency of the antenna structure is further improved.

In one embodiment, the radiator 210 also includes a second portion 242, as shown in fig. 36. The second portion 242 of the radiator 210 includes a third end 203 and a fourth end 204, and a third connection point 213 between the third end 203 and the fourth end 204. The first end 201 of the first portion 241 is connected to the third end 203 of the second portion 242 to form a continuous radiator 210 (the radiator 210 is an integrally formed structure, with the first portion 241 and the second portion 242 of the radiator being continuous in a grounded position (first end 201)). The antenna structure 200 further includes a third inductor 233, the third inductor 233 is electrically connected between the third connection point 213 and the ground 220, and an inductance value of the third inductor 233 is less than a second threshold. The length of the first portion 241 is different from the length of the second portion 242. The second portion 242 has a length greater than three-eighths of the second wavelength, the second portion being configured to produce a second resonance, the second wavelength being a medium wavelength of the second resonance. The third connection point 213 is at a distance of less than or equal to one quarter of the second wavelength from the fourth end 204.

It should be understood that the technical solution provided in the embodiment of the present application may be applied to an asymmetric T-shaped antenna, where the length of the first portion 241 is different from the length of the second portion 242 (for example, the difference between the length of the first portion 241 and the length of the second portion 242 is greater than 5 mm), so that the antenna structure 200 may be used to expand the operating frequency band of the antenna structure when the first portion 241 and the second portion 242 respectively operate in two different CM modes. Meanwhile, the inductance provided between the first portion 241 and the floor 220 determines an inductance value according to a first resonance generated by the first portion 241, and the inductance provided between the second portion 242 and the floor 220 determines an inductance value according to a second resonance generated by the second portion 242.

In one embodiment, the first threshold is 6nH when the frequency of the first resonance is less than or equal to 1 GHz. When the frequency of the first resonance is greater than 1GHz and less than or equal to 2.2GHz, the first threshold is 4nH. When the frequency of the first resonance is greater than 2.2GHz and less than or equal to 3GHz, the first threshold is 3nH. When the frequency of the first resonance is greater than 3GHz, the first threshold is 2nH.

In one embodiment, the second threshold is 6nH when the frequency of the second resonance is less than or equal to 1 GHz. The second threshold is 4nH when the frequency of the second resonance is greater than 1GHz and less than or equal to 2.2 GHz. When the frequency of the second resonance is greater than 2.2GHz and less than or equal to 3GHz, the second threshold is 3nH. When the frequency of the second resonance is greater than 3GHz, the second threshold is 2nH.

It should be appreciated that the inductance values of the first inductor 231, the second inductor 232 and the third inductor 233 are designed according to the operating frequency bands of different antenna structures, so that the current distribution on the radiator is more uniform in the operating frequency bands, and the conductor loss is reduced, thereby improving the efficiency of the antenna structure.

In one embodiment, the electronic device further includes a conductive bezel having a first location, a second location, and a third location thereon, the first location being located between the second location and the third location. The frame between the first position and the second position may be the first portion, and the frame between the first position and the third position may be the second portion. It should be appreciated that the first position may correspond to the first end, the second position may correspond to the second end, and the third position may correspond to the third end.

In one embodiment, the third and second positions of the frame may be provided with slits such that the third and second positions are not connected to other portions of the frame, so as to realize that the ends of the radiator in the third and second positions are open ends.

For the antenna structure 200 shown in fig. 35 and 36, the technical solution shown in fig. 10 may also be adopted, for example, at least one fourth inductor is disposed between the grounding point and the first inductor 231, so as to make the current density distribution on the radiator more uniform, thereby reducing the loss caused by the radiator and the medium disposed around the radiator. Meanwhile, the position of each radiator connected with the inductor comprises a current reversing area, so that the electric field cannot reach zero, the electric field generated by the radiator is continuous, the reverse direction (not comprising the electric field reversing area) does not occur, the radiation caliber of the antenna structure is increased, the conductor loss is reduced, and the efficiency of the antenna structure is improved.

It should be understood that, in the above embodiment, only two or three inductors are provided between the radiator and the floor 220 as an example, and the technical solution provided in the embodiment of the present application may also provide more than or equal to 3 inductors between the radiator and the floor 220, so that the current density distribution on the radiator is more uniform, thereby reducing the loss caused by the radiator and the medium/conductor provided around the radiator.

It should be understood that in the above embodiment, only two slots are provided on the radiator as an example, and the technical solution provided in the embodiment of the present application may also be that a number of slots greater than two, for example, 3 slots, 6 slots, etc., are provided on the radiator, and the slots (or capacitors) and the positions of the inductors may be referred to the foregoing embodiments.

In one embodiment, more than two inductors may be provided between the radiator and the floor as shown in fig. 36. Further, in one embodiment, the radiator may further be provided with a number of slits greater than two.

In one embodiment, the radiator of the T-shaped antenna has a ground point directly electrically connected to the ground plate 220, such as at the first end 201 of the first portion 241 and/or the third end 203 of the second portion 242 shown in FIG. 36. In one embodiment, the first end 201 of the first portion 241 and the third end 203 of the second portion 242 may be implemented by the same ground (e.g., an electrical conductor extending inside the bezel or coupled to the bezel). In one embodiment, the radiator of the T-shaped antenna may not be provided with a ground point directly electrically connected to the ground 220, such as the first end 201 of the first portion 241 and/or the third end 203 of the second portion 242 shown in fig. 36, may be electrically grounded. In one embodiment, the first end 201 of the first portion 241 and the third end 203 of the second portion 242 are grounded through the same inductor.

It should be understood that in the above embodiment, only the symmetric T-type antenna, the asymmetric T-type antenna and the inverted-F-type antenna are taken as examples for illustration, and the technical solution provided in the embodiment of the present application may also be applied to other types of line antennas, and for brevity of discussion, the embodiment of the present application only takes these three types of line antennas as examples for illustration, and the types of line antennas are not limited.

Fig. 37 to 40 are schematic diagrams of a set of antenna structures according to an embodiment of the present application.

As shown in fig. 37 to 40, different structures of the inverted-L antenna are shown. The antenna structure shown in fig. 38 is different from the antenna structure shown in fig. 37 in that a slit is formed in a radiator. It should be understood that the capacitive devices connected in series in the slots shown in the figures are only examples, and in practical applications, the slots may be filled with a medium, and the capacitance value of the capacitance equivalent to the slots may be adjusted by parameters such as the dielectric constant of the medium or the width of the slots. In one embodiment, the width of the slit may be between 0.1mm and 2 mm. The antenna structure shown in fig. 39 is different from the antenna structure shown in fig. 37 in that an inductance is electrically connected between the radiator and the floor. The antenna structure shown in fig. 40 is different from the antenna structure shown in fig. 37 in that a slot is formed in the radiator, and an inductor is provided between the radiator and the floor.

It will be appreciated that to ensure that the antenna structure as shown in figures 37 to 40 operates in the same frequency band (e.g. around 1.85 GHz), the length of the radiator in the antenna structure is adjusted. In the antenna structure shown in fig. 37, the radiator has a length of 18.4mm, and a capacitance of 0.5pF is connected in series at the feed point. In the antenna structure shown in fig. 38, the radiator has a length of 33.4mm, the capacitance value of the capacitor provided in the slot (or the equivalent capacitance value of the slot) is 0.65pF, and a capacitor of 1pF is connected in series at the feeding point. In the antenna structure shown in fig. 39, the length of the radiator is 33.4mm, the inductance value of the inductor connected in series between the radiator and the ground is 1.7nH, and a capacitor of 0.5pF is connected in series at the feeding point. In the antenna structure shown in fig. 40, the length of the radiator is 33.4mm, the capacitance value of the capacitor disposed in the slot (or the equivalent capacitance value of the slot) is 1.1pF, the inductance value of the inductor connected in series between the radiator and the floor is 3nH, and a capacitor of 0.6pF is connected in series at the feeding point.

Fig. 41 and 42 are simulation result diagrams of the antenna structures shown in fig. 37 to 40. Fig. 41 is an S-parameter diagram of the antenna structure shown in fig. 37 to 40 according to an embodiment of the present application. Fig. 42 is a diagram showing simulation results of system efficiency and radiation efficiency of the antenna structures shown in fig. 37 to 40 according to an embodiment of the present application.

As shown in fig. 41, taking S11< -4dB as an example, the antenna structures shown in fig. 37 to 40 operate in CM mode, the operating frequency bands are all around 1.85GHz, and the bandwidth generated by the resonance of the antenna structure shown in fig. 40 is wider.

As shown in fig. 42, in the above frequency bands, the efficiency (system efficiency and radiation efficiency) of the antenna structure shown in fig. 38 to 40 is improved compared to the antenna structure shown in fig. 37. The antenna structure shown in fig. 40 has the most obvious improvement in system efficiency and radiation efficiency compared with the antenna structure shown in fig. 37 due to the increase of inductance electrically connected between the radiator and the floor and the opening of the slot (or the series capacitance of the slot through the opening), the improvement in system efficiency is about 1dB at 1.85Hz, and the improvement in radiation efficiency is also about 0.6 dB.

Fig. 43 to 45 are schematic diagrams showing the distribution of current and electric field of the antenna structures shown in fig. 38 to 40, respectively.

As shown in fig. 43 (a), when the antenna structure resonates, a slot is formed in the radiator (or a capacitor is disposed in the slot), so that the electric field is reversed in a region near the position, the electric field cannot reach a zero point at the position, and an electric field distribution in the form of a standing wave under an unnatural boundary is formed, so that the electric field is weakened, and the dielectric loss of the antenna structure is reduced, thereby improving the efficiency of the antenna structure.

As shown in fig. 43 (b), when the antenna structure resonates, the current is not changed (the current near the ground terminal is strong), and the current is still distributed in a quarter mode, so that the current density is not changed much, and the conductor loss is only improved slightly.

As shown in fig. 44 (a), when the antenna structure resonates, the electric field is not changed, and the distribution corresponding to the quarter mode is still maintained, and the electric field is not dispersed, so that the dielectric loss is not changed.

As shown in fig. 44 (b), when the antenna structure resonates, since the inductance is provided between the radiator and the floor, the current on the radiator reverses in the area near the connection point, so that the electric field generated by the radiator is continuous, no reversal (excluding the electric field reversal area) occurs, no null point exists, the radiation aperture of the antenna structure is increased, the conductor loss is reduced, and the efficiency of the antenna structure is improved.

Since the antenna structure shown in fig. 40 has the characteristics of the antenna structures shown in fig. 38 and 39 at the same time, both the generated electric field and current are changed compared with the distribution corresponding to the quarter mode, as shown in (a) and (b) of fig. 45, so that better conductor loss and dielectric loss can be obtained.

The conductor loss and dielectric loss of the antenna structures shown in fig. 37 to 40 are shown in table 3 below.

TABLE 3 Table 3

Fig. 46 and 47 are schematic views of another antenna structure according to an embodiment of the present application.

The antenna structure shown in fig. 46 and 47 is different from the antenna structure shown in fig. 37 and 39 in the number of inductances electrically connected between the radiator and the floor.

To ensure that the antenna structures shown in fig. 37, 39, 46 and 47 operate in the same frequency band, the length of the radiator in the antenna structure is adjusted. In the antenna structure shown in fig. 37, the radiator has a length of 18.4mm. In the antenna structure shown in fig. 39, the radiator length is 33.4mm, and the inductance value of the series inductance is 1.5nH. In the antenna structure shown in fig. 46, the length of the radiator is 43.4mm, and the inductance value of the inductance close to the ground terminal (first terminal) is 3nH, and the inductance value of the inductance far from the ground terminal (first terminal) is 3.5nH, among the two series inductors. In the antenna structure shown in fig. 47, the length of the radiator is 53.4mm, and among three inductors connected in series, the ground terminal (first terminal) points to the feeding point, and the inductance values of the inductors are 3nh, and 3.8nh in order.

Fig. 48 to 53 are simulation result diagrams of the antenna structures shown in fig. 37, 39, 46 and 47. Fig. 48 is an S-parameter diagram of the antenna structures shown in fig. 37, fig. 39, fig. 46, and fig. 47 according to an embodiment of the present application. Fig. 49 is a graph of simulation results of system efficiency and radiation efficiency of the antenna structures of fig. 37, 39, 46 and 47 provided by an embodiment of the present application. Fig. 50 is a schematic diagram of the current distribution of the antenna structure of fig. 37. Fig. 51 is a schematic diagram of the current distribution of the antenna structure of fig. 39. Fig. 52 is a schematic diagram of the current distribution of the antenna structure of fig. 46. Fig. 53 is a current distribution diagram of the antenna structure shown in fig. 47.

As shown in fig. 48, taking S11< -4dB as an example, the resonance frequency band of the antenna structure shown in fig. 37, 39, 46 and 47 is around 1.85GHz, and the resonance bandwidth thereof gradually widens as the number of inductors provided between the radiator and the floor increases.

As shown in fig. 49, as the number of inductances provided between the radiator and the floor increases, both the radiation efficiency and the system efficiency of the antenna structure increase significantly.

As shown in fig. 50 to 53, as the number of inductors provided between the radiator and the floor increases, the current distribution becomes more uniform when the antenna structure generates radiation.

It will be appreciated that the radiator length of the antenna structure is extended from 18.4mm (the antenna structure shown in fig. 37) to 53.4mm (the antenna structure shown in fig. 47) due to the inductance provided between the radiator and the floor, the radiating aperture is increased, and the conductor loss is reduced, as shown in table 4 below.

TABLE 4 Table 4

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As shown in table 4 above, the inductance provided between the radiator and the floor can reduce the conductor loss, but the improvement in dielectric loss is not significant.

As shown in fig. 54, the antenna structure 300 may include a radiator 310, a ground plane 320, a first inductance 331, and a second inductance 332.

Wherein the radiator 310 comprises a first end 301 and a second end 302, and a first connection point 311 and a second connection point 312 between the first end 301 and the second end 302. The radiator 310 is grounded at the first end 301 and the second end 302 by a floor 320. The inductance values of the first inductor 331 and the second inductor 332 are both smaller than the first threshold value. The length of the radiator 310 is greater than three-quarters of the first wavelength, the portion of the radiator from the first end 301 to the second end 302 being used to create a first resonance, the first wavelength being the dielectric wavelength of the first resonance. The first inductor 331 is electrically connected between the first connection point 311 and the ground plate 320, and the second inductor 332 is electrically connected between the second connection point 312 and the ground plate 320. The distance between the first connection point 311 and the center of the radiator 310 is less than one eighth of the first wavelength, and the second connection point 312 is located between the first connection point 311 and the second end 302.

It should be understood that the center of the radiator 310 may be understood as the midpoint of the physical length of the radiator 310 or, alternatively, the midpoint of the electrical length of the radiator 310. When radiator 210 is slotted in the central region, the center of radiator 310 can also be understood as the midpoint of the physical length that falls on the slot.

In one embodiment, the radiator 310 may further comprise a feeding point 303, the feeding point 303 being used to feed the antenna structure 300 with an electrical signal so that it generates radiation.

It should be understood that the technical solution provided in the embodiment of the present application may utilize an inductance electrically connected between the radiator and the floor, so that when the feeding point feeds an electrical signal, since the radiator 310 is electrically connected to the first inductance 331 and the second inductance 332 between the floor 320 and the first connection point 311 and the second connection point 312, respectively, a current on the radiator 320 is reversed in a vicinity of the first connection point 311 and the second connection point 312. In one embodiment, the current reversing region includes a first connection point 311 and a second connection point 312. Correspondingly, at the connection between the first inductor 331 and the second inductor 332 and the floor 320, the current on the floor 320 is reversed. In one embodiment, the current reversing area on the floor includes the connection of the first inductor 331 and the second inductor 332 to the floor 320. The current density on the radiator can be dispersed (the intensity of a single current strong point is reduced, so that the current is uniformly distributed), thereby reducing the loss caused by the radiator and the medium arranged around the radiator, and further improving the efficiency of the antenna structure.

In addition, since the current on the radiator 320 reverses in the area near the first connection point 311 and the second connection point 312, the electric field cannot reach the zero point at the first connection point 311 and the second connection point 312, so that the electric field generated by the radiator is continuous, no reversal occurs (the electric field reversing area is not included), no zero point exists, the radiation caliber of the antenna structure is increased, the conductor loss is reduced, and the efficiency of the antenna structure is improved. In one embodiment, the electric field is co-directional between the radiator 320 and the floor 320 between the first end 301 and the second end 302.

In one embodiment, the feed point 303 is located between the center of the radiator 310 and the first end 301 or the center of the radiator 310 and the second end 302. The antenna structure 300 may feed in an electrical signal in a bias feed manner, so that the antenna structure 300 may operate in a CM mode and a DM mode at the same time, and the operating frequency band of the antenna structure 300 is extended.

It should be understood that, in the embodiments of the present application, for simplicity of discussion, the DM mode and CM mode of the antenna structure may be excited by center-symmetrical feeding or center-antisymmetric feeding in practical application, which is not limited thereto, and may be adjusted according to the internal layout of the electronic device, which may be also understood in the following embodiments.

In one embodiment, the inductance values of the first inductor 331 and the second inductor 332 may be adjusted according to the resonant frequency generated by the antenna structure 300. When the frequency of the first resonance is less than or equal to 1GHz, the first threshold is 6nH. The first threshold is 4nH when the frequency of the first resonance is greater than 1GHz and less than or equal to 2.2 GHz. When the frequency of the first resonance is greater than 2.2GHz and less than or equal to 3GHz, the first threshold is 3nH. When the frequency of the first resonance is greater than 3GHz, the first threshold is 2nH.

It should be appreciated that, the inductance values of the first inductor 331 and the second inductor 332 are designed according to the operating frequency bands of different antenna structures, so that the current distribution on the radiator is more uniform in the operating frequency bands, and the conductor loss is reduced, thereby improving the efficiency of the antenna structure.

In one embodiment, the electronic device further includes a conductive bezel having a first location and a second location thereon, the bezel between the first location and the second location acting as the radiator 310. The frame is continuous with the rest of the frame at the first and second positions, and the frame is not provided with an insulating slit at the first and second positions.

In one embodiment, the first connection point 311 and the second connection point 312 are disposed on both sides of the center of the radiator 310, respectively. A first connection point 311 is located between the first end 301 and the center of the radiator 310 and a second connection point 312 is located between the second end 302 and the center of the radiator 310. The distance between the second connection point 312 and the center of the radiator 310 is less than one eighth of the first wavelength.

It should be appreciated that the inductors are electrically connected to the two sides of the center of the radiator 310, so that the current on the radiator 310 on the two sides of the center of the radiator 310 is affected by the grounding inductor, and thus the current distribution on the radiator 310 is more uniform. Meanwhile, the electric field generated by the radiator 310 at the two sides of the center does not include the electric field reverse region, so that the radiation caliber of the antenna structure is increased, the conductor loss is reduced, and the efficiency of the antenna structure is improved.

In one embodiment, the antenna structure 300 may further include at least one third inductor electrically connected between the respective at least one third connection point and the ground plane 320, the at least one third inductor and the at least one third connection point may be in one-to-one correspondence, and the at least one third connection point is located between the first end 301 of the radiator 310 and the first connection point 311.

In one embodiment, the antenna structure 100 may further include at least one fourth inductor electrically connected between the respective at least one fourth connection point and the ground plane 320, the at least one fourth inductor and the at least one fourth connection point may be in one-to-one correspondence, and the at least one fourth connection point is located between the second end 302 of the radiator 310 and the second connection point 312.

It will be appreciated that increasing the number of inductors provided on the radiator 310 and the floor 320 may result in a more uniform current density distribution across the radiator, thereby reducing losses associated with the radiator and conductors disposed around the radiator. Meanwhile, the position of each radiator connected with the inductor comprises a current reversing area, so that the electric field cannot reach zero, the electric field generated by the radiator is continuous, the reverse direction (not comprising the electric field reversing area) does not occur, the radiation caliber of the antenna structure is increased, the conductor loss is reduced, and the efficiency of the antenna structure is improved.

In one embodiment, the radiator 310 may be provided with one or more slots 304, where the slots (or capacitors) may be disposed in reference to the previous embodiment, and the slot structure provided on the radiator 310 may be equivalent to a capacitor, so that the radiator 310 is equivalent to a metamaterial structure with a series capacitor. It should be appreciated that providing an inductance between the radiator 310 and the floor 320 may improve the efficiency of the antenna structure 300 in the DM mode, and providing a slot in the radiator 310 may improve the efficiency of the antenna structure 300 in the CM mode. Meanwhile, the center of the radiator 310 may fall outside the radiator, for example, when the lengths of the radiators 310 at both sides of the slit 304 are the same or substantially the same, the center of the radiator 310 is located in the slit.

Fig. 55 to 57 are schematic diagrams of a set of antenna structures according to an embodiment of the present application.

As shown in fig. 55 to 57, schematic views of different structures of slot antennas are shown. The antenna structure shown in fig. 55 is a slot antenna with an opening. The antenna structure shown in fig. 56 is different from the antenna structure shown in fig. 55 in that two slots are added to the radiator. The antenna structure shown in fig. 57 is different from the antenna structure shown in fig. 55 in that two inductors are provided between the radiator and the floor. It should be appreciated that the number of inductances may also be increased on the basis of the antenna structure shown in fig. 57, for example, the number of inductances provided between the radiator and the floor being greater than two, for example, 6.

In one embodiment, as shown in fig. 56, the provision of a slot in the radiator may be considered as an equivalent capacitance (e.g., distributed capacitance) provided on the radiator. In one embodiment, the two ends of the slit opened on the radiator may be connected in series with a capacitor (e.g., lumped capacitor) to form a metamaterial structure of the series capacitor.

It should be understood that, for convenience of visual illustration of comparison of antenna efficiency of the slot antenna operating in DM mode, the antenna structure is illustrated using a center symmetric feed as an example. Meanwhile, the antenna structure shown in fig. 55 to 57 is operated in a half wavelength mode in a DM mode, and an operation frequency band thereof including 2.3GHz is illustrated as an example. To ensure that the antenna structures shown in fig. 55 to 57 operate in the same frequency band, the length of the radiator in the antenna structure is adjusted. In the antenna structure shown in fig. 55, the radiator has a length of 34mm. In the antenna structure shown in fig. 56, the radiator has a length of 64mm, and the equivalent capacitance value of the distributed capacitance across the added slot or the capacitance value of the lumped capacitance connected in series is 0.1pF. In the antenna structure shown in fig. 57, the length of the radiator is 64mm, and the inductance values of the series inductance are all 2.3nH.

Fig. 58 and 59 are diagrams of simulation results of the antenna structures shown in fig. 55 to 57. Fig. 58 is an S-parameter diagram of the antenna structure shown in fig. 55 to 57 according to an embodiment of the present application. Fig. 59 is a diagram showing simulation results of system efficiency and radiation efficiency of the antenna structure shown in fig. 55 to 57 according to an embodiment of the present application.

As shown in fig. 58, taking S11< -4dB as an example, the antenna structure shown in fig. 55 to 57 operates in DM mode, the operating frequency bands each include 2.25GHz to 2.35GHz, and the bandwidth generated by resonance of the antenna structure shown in fig. 57 is wider.

As shown in fig. 59, in the above frequency band, the efficiency (system efficiency and radiation efficiency) of the antenna structure shown in fig. 56 is substantially the same as that of the antenna structure shown in fig. 55. The antenna structure shown in fig. 57 has a significant improvement in system efficiency of the antenna structure compared to the antenna structure shown in fig. 55 due to the increased inductance provided between the radiator and the floor, an improvement of about 1.8dB at 2.3Hz, and an improvement in radiation efficiency of about 2.4 dB.

Fig. 60 to 62 are schematic diagrams of currents and electric fields of the antenna structures shown in fig. 55 to 57. Wherein fig. 60 is a schematic diagram of the current and electric field of the antenna structure of fig. 55. Fig. 61 is a schematic diagram of the current and electric field of the antenna structure of fig. 56. Fig. 62 is a schematic diagram of the current and electric field of the antenna structure of fig. 57.

As shown in (a) of fig. 60, the antenna structure operates in a half wavelength mode in the DM mode, and the current on the radiator at resonance is concentrated at the ground positions at both ends. As shown in (b) of fig. 60, an electric field generated between the radiator and the floor when the antenna structure resonates is concentrated at a center symmetrical feeding position.

As shown in fig. 61 (a), the antenna structure operates in a half wavelength mode in the DM mode, and the current on the radiator at resonance is concentrated in a region near the ground point. As shown in (b) of fig. 61, an electric field generated between the radiator and the floor when the antenna structure resonates is concentrated in a region near the increased gap of the radiator.

As shown in fig. 62 (a), the antenna structure operates in the half wavelength mode in the DM mode, and the current on the radiator at resonance has a zero point at the connection inductance, and the current density is more dispersed than the simulation diagrams shown in fig. 60 and 61. As shown in fig. 62 (b), since the current density is more dispersed, the electric field generated between the radiator and the floor when the antenna structure resonates is reduced compared to the simulation diagrams shown in fig. 60 and 61, and the conductor loss can be reduced, thereby improving the efficiency of the antenna structure.

Fig. 63 is a schematic view of another antenna structure according to an embodiment of the present application

The antenna structure shown in fig. 63 is different from the antenna structure shown in fig. 57 in that 4 inductors are provided between the radiator and the floor.

In order to facilitate visual display of comparison of antenna efficiency of the slot antenna operating in the DM mode, the antenna structure is illustrated by taking a central symmetrical feed as an example. To ensure that the antenna structures shown in fig. 55, 57 and 63 operate in the same frequency band, the length of the radiator in the antenna structure is adjusted. In the antenna structure shown in fig. 55, the radiator has a length of 35.6mm (about one-half of the first wavelength). In the antenna structure shown in fig. 57, the length of the radiator is 51.6mm (about three quarters of the first wavelength), the inductance values of the two series inductors are 5.5nH, and the two inductors are respectively located at two sides of the grounding point. In the antenna structure shown in fig. 63, the radiator has a length of 67.6mm (about the first wavelength), and the inductance of the inductance near the ground point is 5.5nH among the four series inductors, and the inductance of the inductance near the slot is 5.8nH. In order to further increase the length of the radiator, expand the radiation aperture, reduce the inductance value in the antenna structure shown in fig. 63, the length of the radiator is 79mm, and the inductance value of the inductor is 4nH in the four inductors connected in series.

Fig. 64 to 66 are simulation result diagrams of the antenna structures shown in fig. 55, 57 and 63. Fig. 64 is an S-parameter diagram of the antenna structure shown in fig. 55, fig. 57, and fig. 63 according to an embodiment of the present application. Fig. 65 shows the antenna structure of fig. 55, 57 and 63 with a radiator conductivity of 10 according to an embodiment of the present application ⁵ Simulation results for system efficiency and radiation efficiency of magnitude. Fig. 66 shows the antenna structure of fig. 55, 57 and 63 with a radiator conductivity of 10 according to an embodiment of the present application ⁶ Simulation results for system efficiency and radiation efficiency of magnitude.

As shown in fig. 64, taking S11< -4dB as an example, the antenna structure shown in fig. 55, 57 and 63 operates in DM mode, with a resonance frequency band around 2.25GHz, and with an increase in the number of inductors provided between the radiator and the floor, the resonance bandwidth thereof is gradually widened. When the number of the inductors arranged between the radiator and the floor is the same, the inductance value of the inductor is reduced, and the resonance bandwidth is gradually widened.

As shown in fig. 65 and 66, as the number of inductors provided between the radiator and the floor increases, both the radiation efficiency and the system efficiency of the antenna structure increase significantly. When the quantity of the inductors arranged between the radiator and the floor is the same, the inductance value of the inductors is reduced, and the radiation efficiency and the system efficiency of the antenna structure are obviously increased.

At a radiator conductivity of 10 ⁵ In order of magnitude, at 2.25Hz, the antenna structure shown in FIG. 63 (corresponding antenna structure at small inductance value) is compared to the figure55, as shown in fig. 65.

At a radiator conductivity of 10 ⁶ In order of magnitude, at 2.25Hz, the antenna structure shown in fig. 63 (corresponding antenna structure at small inductance value) has a radiation efficiency improvement of about 2.4dB as compared with the antenna structure shown in fig. 55, as shown in fig. 66.

It will be appreciated that the radiator length of the antenna structure is extended from 35.6mm (the antenna structure shown in fig. 55) to 67.6mm (the antenna structure shown in fig. 63) due to the inductance provided between the radiator and the floor, the radiating aperture is increased, and conductor losses are reduced, as shown in table 5 below. When the quantity of the inductors arranged between the radiator and the floor is the same, the inductance value of the inductors is reduced, the length of the radiator of the antenna structure can be further expanded to 79mm, the radiation caliber is increased, and the efficiency of the antenna structure can be further improved.

TABLE 5

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As shown in table 5 above, the inductance provided between the radiator and the floor can reduce the conductor loss, but the improvement in dielectric loss is not significant. And, as shown in fig. 64 and 66, the efficiency of the antenna structure is improved more significantly after the conductivity of the radiator is reduced.

Fig. 67 to 70 are current distribution diagrams of the antenna structures shown in fig. 55, 57 and 63, respectively. Fig. 67 is a schematic diagram of current distribution of the antenna structure shown in fig. 55. Fig. 68 is a current distribution diagram of the antenna structure of fig. 57. Fig. 69 is a schematic diagram of a current distribution corresponding to the antenna structure shown in fig. 63 when the inductance value is large. Fig. 70 is a schematic diagram of a current distribution corresponding to the antenna structure shown in fig. 63 when the inductance value is small.

As shown in fig. 67 to 69, as the number of inductors provided between the radiator and the floor increases, the zero point of the current on the radiator in the vicinity of the connection inductor increases during resonance, so that the current density can be more dispersed, the conductor loss during radiation can be reduced, and the efficiency of the antenna structure can be improved.

As shown in fig. 69 and 70, when the number of inductors provided between the radiator and the floor is the same, the inductance value of the inductor is reduced, and the current density can be further dispersed, reducing the conductor loss.

Fig. 71 to 74 are schematic diagrams of a set of antenna structures according to an embodiment of the present application.

As shown in fig. 71 to 74, which are schematic views of different structures of slot antennas, are different from the slot antennas shown in fig. 54 in the feeding manner, the antenna structure shown in fig. 54 excites CM mode of the slot antennas in the center feeding manner, and improves efficiency by using inductance electrically connected between the radiator and the floor, while the antenna structure shown in fig. 71 to 74 excites CM mode and DM mode simultaneously in the offset feeding manner, and improves efficiency by using inductance electrically connected between the radiator and the floor and a slot opened in the radiator.

. The antenna structure shown in fig. 71 is a slot antenna having an opening (or slot, slit, or the like). The antenna structure shown in fig. 72 is different from the antenna structure shown in fig. 71 in that two slots are added to the radiator in fig. 71. The antenna structure shown in fig. 73 is different from the antenna structure shown in fig. 71 in that two or more inductors, for example, three inductors are provided between the radiator and the floor. The antenna structure shown in fig. 74 is different from the antenna structure shown in fig. 71 in that two slots are added to the radiator, and two inductors are provided between the radiator and the floor.

It should be understood that in the above embodiments, only two or three slots are provided on the radiator as an example, and the technical solution provided in the embodiments of the present application may also be that a number of slots greater than two, for example, 3 slots, 6 slots, etc. are provided on the radiator.

In one embodiment, a greater number of inductances than two may be provided between the radiator and the floor. Further, in one embodiment, the radiator may further be provided with a number of slits greater than two.

As shown in fig. 71 and 74, in one embodiment, opening a slot in the radiator may be considered as an equivalent capacitance (e.g., a distributed capacitance) disposed on the radiator. In one embodiment, the two ends of the slit opened on the radiator may be connected in series with a capacitor (e.g., lumped capacitor) to form a metamaterial structure of the series capacitor.

It should be appreciated that for purposes of visual presentation of a comparison of antenna efficiency for slot antennas operating in CM and DM modes, the description will be given of an antenna configuration employing offset feed with simultaneous excitation in CM and DM modes. Meanwhile, the antenna structure shown in fig. 71 to 74 is operated in the CM mode and the half wavelength mode in DM, and the operation frequency band corresponding to the CM mode includes 1.75GHz, and the operation frequency band corresponding to the DM mode includes 2.2GHz for example. To ensure that the antenna structures shown in fig. 71 to 74 operate in the same frequency band, the length of the radiator in the antenna structure is adjusted. In the antenna structure shown in fig. 71, the radiator has a length of 34mm. In the antenna structure shown in fig. 72, the length of the radiator is 64mm, the equivalent capacitance of the distributed capacitor 341 or the capacitance of the lumped capacitor 341 is 0.5pF, the equivalent capacitance of the distributed capacitor 342 or the capacitance of the lumped capacitor 342 is 0.65pF, and the equivalent capacitance of the distributed capacitor 343 or the capacitance of the lumped capacitor 343 is 0.15pF. In the antenna structure shown in fig. 73, the length of the radiator is 64mm, the equivalent capacitance value of the distributed capacitor 351 or the capacitance value of the lumped capacitor 351 is 0.1pF, the inductance value of the inductor 352 is 3.5nH, the inductance value of the inductor 353 is 6.5nH, and the inductance value of the inductor 354 is 10nH. In the antenna structure shown in fig. 74, the length of the radiator is 70mm, the equivalent capacitance of the distributed capacitor 361 or the capacitance of the lumped capacitor 361 is 0.6pF, the equivalent capacitance of the distributed capacitor 362 or the capacitance of the lumped capacitor 362 is 0.55pF, the equivalent capacitance of the distributed capacitor 363 or the capacitance of the lumped capacitor 363 is 0.35pF, the inductance of the inductor 364 is 3.5nH, the inductance of the inductor 365 is 4.5nH, and the inductance of the inductor 366 is 10nH.

Fig. 75 and 76 are diagrams of simulation results of the antenna structures shown in fig. 71 to 74. Fig. 75 is an S-parameter diagram of the antenna structure shown in fig. 71 to 74 according to an embodiment of the present application. Fig. 76 is a diagram of simulation results of system efficiency and radiation efficiency of the antenna structures shown in fig. 71-74 provided by an embodiment of the present application.

As shown in fig. 75, taking S11< -4dB as an example, the antenna structure shown in fig. 71 to 74 operates in CM mode and DM mode, and the operating frequency band includes 1.68GHz to 1.85GHz (CM mode) and 2.15GHz to 2.3GHz (DM mode), respectively, and the bandwidth generated by the resonance of the antenna structure shown in fig. 74 is wider.

As shown in fig. 76, in the above frequency band, the antenna structure shown in fig. 72 can improve efficiency in CM mode (1.68 GHz to 1.85 GHz) and the antenna structure shown in fig. 73 can improve efficiency in DM mode (2.15 GHz to 2.3 GHz) compared to the efficiency (system efficiency and radiation efficiency) of the antenna structure shown in fig. 71. Because the antenna structure shown in fig. 74 combines the characteristics of the antenna structure shown in fig. 72 and the antenna structure shown in fig. 73, the efficiency of the antenna structure can be improved in both CM mode (1.68 GHz to 1.85 GHz) and DM mode (2.15 GHz to 2.3 GHz) by using the capacitance provided on the radiator and the inductance provided between the radiator and the floor. For example, the system efficiency (at 2.45 GHz) of the antenna structure may be improved by more than 3dB by increasing the inductance provided between the radiator and the floor.

The SAR values of the antenna structures shown in fig. 71 to 74 are shown in table 6 below, and are described by taking 24dbm as an example of the input power.

TABLE 6

As shown in table 6 above, the antenna structure shown in fig. 72 exhibited good SAR values at 1.75GHz (CM mode) and 2.2GHz (DM mode) as compared to the antenna structure shown in fig. 71, and the antenna structure shown in fig. 73 exhibited good SAR values at 1.75GHz (CM mode) and 2.2GHz (DM mode). Since the antenna structure shown in fig. 74 combines the characteristics of the antenna structure shown in fig. 72 and the antenna structure shown in fig. 73, it exhibits good SAR values at 1.75GHz (CM mode) and 2.2GHz (DM mode).

As shown in fig. 77, the antenna structure 400 may include a radiator 410, a ground plane 420, a first inductance 431 and a second inductance 432.

Wherein the radiator 410 comprises a first end 401 and a second end 402, and a first connection point 411 and a second connection point 412 between the first end 401 and the second end 402. The radiator 410 is grounded at the first end 401 and the second end 402 through the floor 420. The inductance values of the first inductor 431 and the second inductor 432 are both smaller than the first threshold value. The length of the radiator 410 is greater than three-quarters of the first wavelength, and the portion of the radiator from the first end 401 to the second end 402 is configured to generate a first resonance, the first wavelength being the dielectric wavelength of the first resonance. The first inductor 431 is electrically connected between the first connection point 411 and the ground 420, and the second inductor 432 is electrically connected between the second connection point 412 and the ground 420. The distance between the first connection point 411 and the center of the radiator 410 is less than one eighth of the first wavelength, and the second connection point 412 is located between the first connection point 411 and the second end 402.

The antenna structure 400 shown in fig. 77 (a) is different from the antenna structure 300 shown in fig. 54 in that the length of the radiator 310 of the antenna structure 300 is equal to the distance between the first end 301 and the second end 302, the radiator 310 and the floor 320 enclose a linear (e.g., bar-shaped) slot, while the length of the radiator 410 of the antenna structure 400 is much greater than the distance between the first end 401 and the second end 402, and the radiator 410 and the floor 420 enclose a nonlinear (T-shaped or bent) slot. In one embodiment, antenna structure 300 is a slot antenna (slot antenna). In one embodiment, the antenna structure 400 is a loop antenna (loop antenna). In one embodiment, the distance L1 between the first end and the second end is substantially the same as the length L2 of the radiator, which may be understood as L2X10.ltoreq.L1.ltoreq.L2X10%, such as L2X10.ltoreq.L1.ltoreq.L2X10%. In one embodiment, the length L2 of the radiator is much greater than the distance L1 between the first and second ends, it being understood that L1 is less than or equal to L2×50%, such as L1 is less than or equal to L2×30%. It is understood that when the ratio of the distance L1 between the first end and the second end to the length L2 of the radiator is between the ratio of forming the loop antenna and the slot antenna (e.g., L2X10%. Ltoreq.L1. Ltoreq.L2X180%), the antenna structure may have the characteristics of both the slot antenna and the loop antenna.

In one embodiment, radiator 410 may be disposed on an antenna support within the electronic device by LDS, or may be disposed on a rear cover, which is not limited by the present application.

In one embodiment, the first threshold is 20nH when the frequency of the first resonance is less than or equal to 1 GHz. The first threshold is 16nH when the frequency of resonance of the first resonance is greater than 1GHz and less than or equal to 2.2 GHz. The first threshold is 12nH when the frequency of the first resonance is greater than 2.2GHz and less than or equal to 3 GHz. When the frequency of the first resonance is greater than 3GHz, the first threshold is 10nH.

In one embodiment, the radiator 410 may be provided with one or more slots, and the positions of the slots (or the capacitors) may refer to the previous embodiment, and the slot structure provided on the radiator 410 may be equivalent to a capacitor, so that the radiator 410 is equivalent to a metamaterial structure with a series capacitor. It should be appreciated that providing an inductance between the radiator 410 and the floor 420 may improve the efficiency of the antenna structure 400 in the DM mode, and providing a slot in the radiator 410 may improve the efficiency of the antenna structure 400 in the CM mode. Meanwhile, the center of the radiator 410 may fall outside the radiator, for example, when lengths of the radiators 410 at both sides of the slit are the same or substantially the same, the center of the radiator 410 is located in the slit.

In one embodiment, the radiator 410 may further include a feeding point for feeding the antenna structure 400 with an electrical signal to cause it to radiate.

As shown in fig. 77 (b), the first feeding point and the second feeding point are respectively disposed at two ends of the slot of the radiator 410, or the first feeding point and the second feeding point are respectively disposed at the third end 403 and the fourth end 404 of the radiator 410, so as to provide central antisymmetry for the radiator 410, or may be asymmetric feeding. The first feeding point and the second feeding point correspond to the same feed source, for example, signals of the first feeding point and the second feeding point may be radio frequency signals with equal amplitude and different phases.

As shown in fig. 77 (c), the first feeding point and the second feeding point are respectively disposed at both ends of the slot of the radiator 410, or, the first feeding point and the second feeding point are respectively disposed at the third end 403 and the fourth end 404 of the radiator 410, to provide central symmetrical feeding to the radiator 410. Wherein the first and second feed points correspond to the same feed source, e.g., the first and second feed points are electrically connected at the same location as the feed source.

In one embodiment, the feed point is located between the first end 401 or the second end 402 of the radiator 410. The antenna structure 400 may feed in an electrical signal in a bias feed manner, so that the antenna structure 400 may operate in a CM mode and a DM mode at the same time, and the operating frequency band of the antenna structure 400 is extended. In practical application, the CM mode and the DM mode of the antenna structure can be excited by the central symmetrical feed or the central antisymmetric feed, the application is not limited to this, and can be adjusted according to the internal layout of the electronic device, and can be correspondingly understood in the following embodiments.

It should be understood that the technical solution provided in the embodiment of the present application may be applied to the loop antenna shown in fig. 77, and the inductance provided between the radiator and the ground plate may be used, so that when the feeding point feeds the electric signal, since the radiator 410 is provided with the first inductance 431 and the second inductance 432 between the first connection point 411 and the second connection point 412 and the ground plate 420, respectively, the current on the radiator 420 is reversed in the area near the first connection point 411 and the second connection point 412. Correspondingly, at the junction of the first inductor 431 and the second inductor 432 on the floor 420, the current on the floor 420 is reversed. The current density on the radiator can be dispersed (the intensity of a single current strong point is reduced, so that the current is uniformly distributed), thereby reducing the loss caused by the radiator and the medium arranged around the radiator, and further improving the efficiency of the antenna structure.

In addition, since the current on the radiator 420 is reversed in the area near the first connection point 411 and the second connection point 412, the electric field cannot reach the zero point at the first connection point 411 and the second connection point 412, so that the electric field generated by the radiator is continuous, no reversal (excluding the electric field reversal area) occurs, no zero point exists, the radiation caliber of the antenna structure is increased, the conductor loss is reduced, and the efficiency of the antenna structure is improved.

Fig. 78 to 81 are schematic diagrams of a set of antenna structures according to an embodiment of the present application.

As shown in fig. 78 to 81, the different structures of the loop antenna are schematic diagrams. The antenna structure shown in fig. 78 is a loop antenna in which an opening is provided at the center of a radiator. The antenna structure shown in fig. 79 is different from the antenna structure shown in fig. 78 in that two slots are added to the radiator in fig. 79. The antenna structure shown in fig. 80 is different from the antenna structure shown in fig. 78 in that two inductors are provided between the radiator and the floor. The antenna structure shown in fig. 81 is different from the antenna structure shown in fig. 78 in that two slots are added to the radiator, and two inductors are provided between the radiator and the floor.

As shown in fig. 79 and 81, in one embodiment, opening a slot in the radiator can be considered as an equivalent capacitance (e.g., a distributed capacitance) disposed on the radiator. In one embodiment, the two ends of the slit opened on the radiator may be connected in series with a capacitor (e.g., lumped capacitor) to form a metamaterial structure of the series capacitor.

Fig. 82 and 83 are graphs of simulation results of the antenna structure shown in fig. 78 to 81 operating in CM mode. Fig. 82 is an S-parameter diagram of the antenna structure shown in fig. 78 to 81 in CM mode according to an embodiment of the present application. Fig. 83 is a diagram of simulation results of system efficiency and radiation efficiency in CM mode for the antenna structures shown in fig. 78 to 81 according to an embodiment of the present application.

It should be appreciated that for purposes of visual presentation of a comparison of antenna efficiency for a loop antenna operating in CM mode, a CM mode is illustrated in which the antenna structure is excited with a center symmetrical feed. Meanwhile, the antenna structure as shown in fig. 82 and 83 operates in the half wavelength mode of the CM mode. To ensure that the antenna structures shown in fig. 78-81 operate in the same frequency band, the length of the radiator in the antenna structure is adjusted. In the antenna structure shown in fig. 78, the radiator has a length of 42.8mm. In the antenna structure shown in fig. 79, the radiator has a length of 62.8mm, and the distributed or lumped capacitances 441 and 442 have capacitance values of 0.35pF. In the antenna structure shown in fig. 80, the length of the radiator is 62.8mm, and the inductance values of the inductor 451 and the inductor 452 are 15nH. In the antenna structure shown in fig. 81, the length of the radiator is 62.8mm, the capacitance values of the distributed or lumped capacitance 461 and the distributed or lumped capacitance 362 are 0.4pF, and the inductance values of the inductance 463 and the inductance 464 are 12nH. It should be understood that the above inductance values are merely examples, and in the embodiment of the present application, in the antenna structure having both the slot and the ground inductance, a specific value of the ground inductance is not limited.

As shown in fig. 82, taking S11< -4dB as an example, the antenna structure shown in fig. 78 to 81 operates in CM mode, the operating frequency bands each include 1.7GHz to 1.78GHz, and the bandwidth generated by resonance of the antenna structure shown in fig. 81 is wider.

As shown in fig. 83, in the above frequency band, the antenna structure shown in fig. 79 is substantially the same as the antenna structure shown in fig. 78 in terms of efficiency (system efficiency and radiation efficiency) as compared with the antenna structure shown in fig. 78. The antenna structures shown in fig. 80 and 81 can improve the efficiency of the antenna structure. For example, the system efficiency (at 1.75 GHz) of the antenna structure shown in FIG. 81 is improved by more than 1.1 dB.

Fig. 84 and 85 are graphs of simulation results of the antenna structure shown in fig. 78 to 81 operating in the DM mode. Fig. 84 is an S-parameter diagram of the antenna structure shown in fig. 78 to 81 in the DM mode according to the embodiment of the present application. Fig. 85 is a diagram of simulation results of system efficiency and radiation efficiency of the antenna structure shown in fig. 78 to 81 in the DM mode according to an embodiment of the present application.

It should be understood that, for convenience of visual display of comparison of antenna efficiency of the loop antenna operating in the DM mode, the DM mode is illustrated by exciting the antenna structure in a central antisymmetric feed manner. Meanwhile, the antenna structure as shown in fig. 84 and 85 operates in a half wavelength mode of the DM mode. To ensure that the antenna structures shown in fig. 78-81 operate in the same frequency band, the length of the radiator in the antenna structure is adjusted. In the antenna structure shown in fig. 78, the radiator has a length of 42.8mm. In the antenna structure shown in fig. 79, the radiator has a length of 62.8mm, and the equivalent capacitance value of the capacitor 441 and the capacitor 442 is 0.2pF. In the antenna structure shown in fig. 80, the length of the radiator is 62.8mm, and the inductance values of the inductor 451 and the inductor 452 are 2nH. In the antenna structure shown in fig. 81, the length of the radiator is 62.8mm, the equivalent capacitance value of the capacitor 461 and the capacitor 362 is 0.6pF, and the inductance value of the inductor 463 and the inductor 464 is 3.5nH.

As shown in fig. 84, taking S11< -4dB as an example, the antenna structure shown in fig. 78 to 81 operates in DM mode, the operating frequency bands each include 1.7GHz to 1.78GHz, and the bandwidth generated by the resonance of the antenna structure shown in fig. 81 is wider.

As shown in fig. 85, in the above frequency band, the antenna structure shown in fig. 79, the antenna structure shown in fig. 80 and 81 can improve the efficiency of the antenna structure compared with the efficiency (system efficiency and radiation efficiency) of the antenna structure shown in fig. 78. For example, the system efficiency (at 1.75 GHz) of the antenna structure shown in FIG. 81 is improved by more than 2 dB.

Fig. 86 and 87 are graphs of simulation results of the antenna structure shown in fig. 78 to 81 operating in CM and DM modes.

Fig. 86 is an S-parameter diagram of the antenna structure shown in fig. 78 to 81 according to an embodiment of the present application. Fig. 87 is a diagram showing simulation results of system efficiency and radiation efficiency of the antenna structures shown in fig. 78 to 81 according to an embodiment of the present application.

It should be appreciated that for purposes of visual presentation of a comparison of antenna efficiency for a loop antenna operating in CM and DM modes, a description will be given of a mode in which the antenna structure is excited in both CM and DM modes in a feed-biased manner. To ensure that the antenna structures shown in fig. 78-81 operate in the same frequency band, the length of the radiator in the antenna structure is adjusted. In the antenna structure shown in fig. 78, the radiator has a length of 42.8mm. In the antenna structure shown in fig. 79, the length of the radiator is 62.8mm, the equivalent capacitance of the distributed capacitor 441 or the capacitance of the lumped capacitor 441 is 0.4pF, the equivalent capacitance of the distributed capacitor 442 or the capacitance of the lumped capacitor 442 is 0.1pF, and a capacitor is disposed at the center slot, and the capacitance thereof is 0.45pF. In the antenna structure shown in fig. 80, the length of the radiator is 62.8mm, the inductance value of the inductor 451 and the inductance 452 is 8nH, and a capacitor is provided at the center slit, and the capacitance value thereof is 0.1pF. In the antenna structure shown in fig. 81, the length of the radiator is 62.8mm, the equivalent capacitance value of the distributed capacitor 461 or the capacitance value of the lumped capacitor 461 is 0.2pF, the equivalent capacitance value of the distributed capacitor 462 or the capacitance value of the lumped capacitor 462 is 0.4pF, the inductance value of the inductor 463 is 8nH, the inductance value of the inductor 464 is 5nH, and the distributed capacitor or the lumped capacitor is disposed through the center slot, and the equivalent capacitance value thereof is 0.15pF.

As shown in fig. 86, taking S11< -4dB as an example, the antenna structure shown in fig. 78 to 81 operates in CM mode and DM mode, the operating frequency bands corresponding to CM mode each include 2.05GHz to 2.2GHz, the operating frequency bands corresponding to DM mode each include 1.74GHz to 1.8GHz, and the bandwidth generated by resonance of the antenna structure shown in fig. 81 is wider.

As shown in fig. 87, in the above frequency band, the antenna structure shown in fig. 79 can improve the efficiency of the antenna structure in the DM mode, but does not significantly improve the efficiency in the CM mode, compared to the efficiency (system efficiency and radiation efficiency) of the antenna structure shown in fig. 78. The antenna structure shown in fig. 80 and 81 can improve the efficiency of the antenna structure in both CM mode and DM mode. For example, the system efficiency of the antenna structure shown in FIG. 81 in CM mode and DM mode is improved by 1.3dB and 0.7dB or more (at 2.1GHz and 1.75 GHz), respectively.

The SAR values of the antenna structures shown in fig. 78 to 81 are shown in table 7 below, and are described by taking 24dbm as an example of input power.

TABLE 7

As shown in table 7 above, the antenna structure shown in fig. 79 is excellent in SAR values at 1.75GHz (CM mode) and 2.1GHz (DM mode) as compared to the antenna structure shown in fig. 78, and the antenna structure shown in fig. 80 is excellent in SAR values at 1.75GHz (CM mode) and 2.1GHz (DM mode). Since the antenna structure shown in fig. 81 combines the characteristics of the antenna structure shown in fig. 79 and the antenna structure shown in fig. 80, it exhibits the best SAR values at both 1.75GHz (CM mode) and 2.1GHz (DM mode).

Those skilled in the art may implement the described functionality using different approaches for each particular application, but such implementation is not intended to be limiting.

It will be clear to those skilled in the art that, for convenience and brevity of description, specific working procedures of the above-described systems, apparatuses and units may refer to corresponding procedures in the foregoing method embodiments, and are not repeated herein.

In the several embodiments provided by the present application, it should be understood that the disclosed systems, devices, and methods may be implemented in other manners. For example, the apparatus embodiments described above are merely illustrative, e.g., the division of the units is merely a logical function division, and there may be additional divisions when actually implemented, e.g., multiple units or components may be combined or integrated into another system, or some features may be omitted or not performed. Alternatively, the coupling or direct coupling or communication connection shown or discussed may be through some interface, device or unit, or may be in electrical or other form.

The foregoing is merely illustrative of the present application, and the present application is not limited thereto, and any person skilled in the art will readily recognize that variations or substitutions are within the scope of the present application. Therefore, the protection scope of the present application shall be subject to the protection scope of the claims.

Claims

1. An electronic device, comprising:

the radiator comprises a first end, a second end, a grounding point, a first connecting point and a second connecting point, wherein the grounding point, the first connecting point and the second connecting point are positioned between the first end and the second end, the grounding point is arranged in the central area of the radiator, and the first end and the second end are both open ends;

a floor through which the radiator is grounded at the grounding point;

the first inductor and the second inductor have inductance values smaller than or equal to a first threshold value;

wherein the length of the radiator from the first end to the second end is greater than three-quarters of a first wavelength, the portion of the radiator from the first end to the second end being for generating a first resonance, wherein the first wavelength is a medium wavelength of the first resonance;

The first inductor is electrically connected between the first connection point and the floor, and the second inductor is electrically connected between the second connection point and the floor;

the distance between the first connection point and the first end is less than a quarter of the first wavelength, and the second connection point is located between the first connection point and the second end.

2. The electronic device of claim 1, wherein the electronic device comprises a memory device,

when the frequency of the first resonance is less than or equal to 1GHz, the first threshold is 6nH;

when the frequency of the first resonance is greater than 1GHz and less than or equal to 2.2GHz, the first threshold is 4nH;

when the frequency of the first resonance is greater than 2.2GHz and less than or equal to 3GHz, the first threshold is 3nH;

when the frequency of the first resonance is greater than 3GHz, the first threshold is 2nH.

3. The electronic device according to claim 1 or 2, characterized in that,

the first connection point is located between the first end and the ground point, and the second connection point is located between the second end and the ground point;

the distance between the second connection point and the second end is less than a quarter of the first wavelength.

4. The electronic device of any one of claims 1-3, wherein the electronic device further comprises:

the third inductor is electrically connected between a third connection point and the ground plate, and the third connection point is positioned between the grounding point and the first connection point; and/or

And the fourth inductor is electrically connected between a fourth connection point and the ground plate, and the fourth connection point is positioned between the grounding point and the second connection point.

5. The electronic device of any one of claims 1 to 4, wherein the radiator is provided with one or more insulating slits, each slit having a width of greater than or equal to 0.1mm and less than or equal to 2mm.

6. The electronic device of any one of claim 1 to 5, wherein,

the electronic device further comprises a conductive frame, wherein the frame is provided with a first position and a second position, the frame between the first position and the second position is used as the radiator, the central area of the radiator is an area within 5mm from the center of the radiator, and the frame is respectively provided with an insulation gap at the first position and the second position.

7. An electronic device, comprising:

A radiator including a first end and a second end, and a first connection point and a second connection point between the first end and the second end;

a floor through which the radiator is grounded at the first and second ends;

the first inductor and the second inductor have inductance values smaller than a first threshold value;

wherein the length of the radiator is greater than three-quarters of a first wavelength, the portion of the radiator from the first end to the second end being configured to produce a first resonance, wherein the first wavelength is a medium wavelength of the first resonance;

the first connection point is located between the center of the radiator and the first end and is less than one eighth of the first wavelength from the center of the radiator, and the second connection point is located between the first connection point and the second end.

8. The electronic device of claim 7, wherein the electronic device comprises a memory device,

the first end and the second end being spaced apart a distance equal to the length of the radiator, wherein

when the frequency of the first resonance is greater than 3GHz, the first threshold is 2nH;

alternatively, the first end and the second end are separated by a distance less than the length of the radiator, wherein;

when the frequency of the first resonance is less than or equal to 1GHz, the first threshold is 20nH;

when the frequency of the first resonance is greater than 1GHz and less than or equal to 2.2GHz, the first threshold is 16nH;

when the frequency of the first resonance is greater than 2.2GHz and less than or equal to 3GHz, the first threshold is 12nH;

when the frequency of the first resonance is greater than 3GHz, the first threshold is 10nH.

9. The electronic device according to claim 7 or 8, characterized in that,

the second connection point is located between the second end and the center of the radiator;

the distance between the second connection point and the center of the radiator is less than one eighth of the first wavelength.

10. The electronic device of any one of claims 7 to 9, wherein the electronic device further comprises:

the third inductor is electrically connected between a third connection point and the floor, and the third connection point is positioned between the center of the radiator and the first connection point; and/or

And the fourth inductor is electrically connected between a fourth connecting point and the floor, and the fourth connecting point is positioned between the center of the radiator and the second connecting point.

11. The electronic device of any one of claims 7 to 10, wherein the radiator is provided with one or more insulating slits, each slit having a width of greater than or equal to 0.1mm and less than or equal to 2mm.

12. The electronic device according to any one of the claims 7 to 11, characterized in that,

the electronic device further comprises a conductive frame, wherein the frame is provided with a first position and a second position, the frame between the first position and the second position is used as the radiator, and the frame is continuous with the rest part of the frame at the first position and the second position.

13. An electronic device, comprising:

a radiator comprising a first portion, the first portion of the radiator comprising a first end and a second end, and a first connection point and a feed point between the first end and the second end, wherein the second end is an open end;

A floor through which the radiator is grounded at the first end;

a first inductor, the inductance value of which is smaller than a first threshold value;

wherein the length of the first portion is greater than three-eighths of a first wavelength, the first portion being for generating a first resonance, the first wavelength being a medium wavelength of the first resonance;

the first inductor is electrically connected between the first connection point and the floor, and the first connection point is arranged between the feed point and the first end;

the first connection point is less than a quarter of the first wavelength from the second end.

14. The electronic device of claim 13, wherein the electronic device comprises a memory device,

the radiator further comprises a second connection point located between the first connection point and the first end;

the electronic device further includes a second inductor electrically connected between the second connection point and the floor.

15. The electronic device of claim 13 or 14, wherein the electronic device comprises a display device,

the radiator further comprises a second portion comprising a third end and a fourth end, and a third connection point between the third end and the fourth end, the first end of the first portion being connected to the third end of the second portion to form a continuous radiator, wherein the fourth end is an open end;

A third inductor electrically connected between the third connection point and the floor, wherein an inductance value of the third inductor is smaller than the second threshold value;

the length of the first portion is different from the length of the second portion;

the second portion having a length greater than three-eighths of a second wavelength, the second portion being configured to produce a second resonance, the second wavelength being a medium wavelength of the second resonance;

the third connection point is less than a quarter of the second wavelength from the fourth end.

16. The electronic device of claim 15, wherein the electronic device comprises a memory device,

when the frequency of the second resonance is less than or equal to 1GHz, the second threshold is 6nH;

when the frequency of the second resonance is greater than 1GHz and less than or equal to 2.2GHz, the second threshold is 4nH;

when the frequency of the second resonance is greater than 2.2GHz and less than or equal to 3GHz, the second threshold is 3nH;

when the frequency of the second resonance is greater than 3GHz, the second threshold is 2nH.

17. The electronic device of any one of claims 13 to 16, wherein the electronic device comprises a display device,

18. An electronic device, comprising:

a floor through which the radiator is grounded;

the first inductor is electrically connected between the first connecting point and the floor, and the inductance value of the first inductor is smaller than or equal to a first threshold value;

the second inductor is electrically connected between the second connection point and the floor, and the inductance value of the second inductor is smaller than or equal to the first threshold value;

the portion of the radiator from the first end to the second end is used for generating first resonance, the current of the radiator in a first area and/or the current of the floor in a second area comprise a current reversing area, the first area comprises the first connection point and the second connection point, and the second area comprises the first inductor and the floor connection point and the second inductor and the floor connection point; and/or

When the radiator generates the first resonance, a magnetic field generated by the radiator between the first area and the floor is in the same direction.

19. The electronic device of claim 18, wherein no switch is included between the first inductance and either the radiator or the floor, and no switch is included between the second inductance and either the radiator or the floor.

20. The electronic device of claim 18 or 19, wherein the electronic device comprises a memory device,

the radiator is provided with an insulation gap;

when the radiator generates the first resonance, the current of the radiator in a fifth area does not comprise a current reversing area, and the fifth area comprises the insulation gap; and/or

The magnetic field of the radiator in the fifth region includes a magnetic field reversal region when the radiator generates the first resonance.