CN116260343A - Low-ripple adjustable direct-current stabilized power supply control method based on Buck-Boost inverter circuit - Google Patents

Low-ripple adjustable direct-current stabilized power supply control method based on Buck-Boost inverter circuit Download PDF

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CN116260343A
CN116260343A CN202310349695.3A CN202310349695A CN116260343A CN 116260343 A CN116260343 A CN 116260343A CN 202310349695 A CN202310349695 A CN 202310349695A CN 116260343 A CN116260343 A CN 116260343A
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inverter circuit
voltage
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张小平
谈宜雯
李毅凡
龚俊
余萍
周鹏
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Hunan University of Science and Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from DC input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/12—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only

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Abstract

The invention provides a low-ripple adjustable direct-current stabilized power supply control method based on a Buck-Boost inverter circuit, which adopts a proportional integral-vector proportional integral composite control algorithm to calculate the deviation between a capacitor reference voltage and an actual voltage in the inverter circuit, converts the obtained capacitor reference current into an inductance reference current, adopts the proportional integral-vector proportional integral composite control algorithm to calculate the deviation between the inductance reference current and the actual current, and controls a corresponding power switch in the inverter circuit according to the obtained duty ratio, so that the purpose of effectively improving the steady-state accuracy of the output voltage of the direct-current stabilized power supply can be achieved on the basis of keeping the actual output voltage of the direct-current stabilized power supply to accurately track the set reference output voltage without static difference. The control method provided by the invention has the characteristics of simple control algorithm, high steady-state accuracy of output voltage, small ripple, good dynamic performance and the like.

Description

基于Buck-Boost逆变电路的低纹波可调直流稳压电源控制 方法Low ripple adjustable DC regulated power supply control method based on Buck-Boost inverter circuit

技术领域Technical Field

本发明涉及直流稳压电源领域，尤其涉及一种基于Buck-Boost逆变电路的低纹波可调直流稳压电源控制方法。The invention relates to the field of direct current regulated power supplies, and in particular to a low-ripple adjustable direct current regulated power supply control method based on a Buck-Boost inverter circuit.

背景技术Background Art

直流稳压电源是由交流电源经整流稳压等环节而形成的，已在国民经济各领域得到了广泛应用。直流稳压电源输出电压稳态精度和纹波等技术指标对于其应用对象将产生重要影响，尤其对于一些精密仪器设备如扫描电镜、透射式电镜等来说，决定电镜分辨率的关键因素是其低纹波高压直流供电电源输出电压的高稳定性，目前在有关低纹波高稳定性直流稳压电源方面已开展了大量研究，提出了诸如整流-高频逆变器-变压器升压-整流等多种主电路方案，虽然取得了较好的效果，但仍存在电路结构复杂、体积大等不足。为此，中国发明专利申请CN202211033703.5-一种低纹波可调直流稳压电源及其控制方法提出了一种可调直流稳压电源拓扑结构及相应的控制方法，不仅简化了主电路结构(仅包括依次串联的三相PWM整流电路、三相交错并联Buck-Boost中频逆变电路及三相桥式不可控整流电路)，而且具有输出电压任意可调等特点，但其仍未能解决输出电压高稳态精度和低纹波的技术要求。The DC regulated power supply is formed by the AC power supply through rectification and voltage stabilization, and has been widely used in various fields of the national economy. The technical indicators such as the steady-state accuracy and ripple of the DC regulated power supply output voltage will have an important impact on its application objects, especially for some precision instruments and equipment such as scanning electron microscopes and transmission electron microscopes. The key factor that determines the resolution of the electron microscope is the high stability of the output voltage of its low-ripple high-voltage DC power supply. At present, a lot of research has been carried out on low-ripple and high-stability DC regulated power supplies, and a variety of main circuit schemes such as rectification-high-frequency inverter-transformer boost-rectification have been proposed. Although good results have been achieved, there are still shortcomings such as complex circuit structure and large volume. To this end, Chinese invention patent application CN202211033703.5 - A low-ripple adjustable DC regulated power supply and its control method proposes an adjustable DC regulated power supply topology structure and a corresponding control method, which not only simplifies the main circuit structure (only includes a three-phase PWM rectifier circuit connected in series, a three-phase staggered parallel Buck-Boost medium-frequency inverter circuit and a three-phase bridge uncontrolled rectifier circuit), but also has the characteristics of arbitrarily adjustable output voltage. However, it still fails to solve the technical requirements of high steady-state accuracy and low ripple of the output voltage.

发明内容Summary of the invention

为了解决上述技术问题，本发明提供一种基于Buck-Boost逆变电路的低纹波可调直流稳压电源控制方法，所述控制方法通过采用比例积分-矢量比例积分复合控制算法对Buck-Boost逆变电路中的电容参考电压与其实际电压的偏差进行计算得电容参考电流，将所得电容参考电流换算为电感参考电流，再继续采用比例积分-矢量比例积分复合控制算法对电感参考电流与其实际电流的偏差进行计算得占空比，根据所得占空比对Buck-Boost逆变电路中对应功率开关进行控制。In order to solve the above technical problems, the present invention provides a low ripple adjustable DC regulated power supply control method based on a Buck-Boost inverter circuit. The control method adopts a proportional integral-vector proportional integral composite control algorithm to calculate the deviation between the capacitor reference voltage and its actual voltage in the Buck-Boost inverter circuit to obtain a capacitor reference current, converts the obtained capacitor reference current into an inductor reference current, and then continues to use the proportional integral-vector proportional integral composite control algorithm to calculate the deviation between the inductor reference current and its actual current to obtain a duty cycle, and controls the corresponding power switch in the Buck-Boost inverter circuit according to the obtained duty cycle.

优选地，上述控制方法包括以下步骤：Preferably, the control method comprises the following steps:

(1)实时检测直流稳压电源的输出电压实测值UDC，根据直流稳压电源的输出电压预设值UDCref，计算得三相交错并联Buck-Boost逆变电路的输出电压参考值uref；(1) Real-time detection of the output voltage measured value U DC of the DC regulated power supply, and calculation of the output voltage reference value u ref of the three-phase interleaved parallel Buck-Boost inverter circuit according to the output voltage preset value U DCref of the DC regulated power supply;

(2)根据步骤(1)所得Buck-Boost逆变电路的输出电压参考值uref，得该逆变电路中的电容参考电压uCref；(2) according to the output voltage reference value u ref of the Buck-Boost inverter circuit obtained in step (1), obtain the capacitor reference voltage u Cref in the inverter circuit;

(3)实时检测电容的实际电压uC，根据步骤(2)所得电容参考电压uCref，计算得其偏差ΔuC，经比例积分-矢量比例积分复合控制算法处理，得电容参考电流iCref；(3) Detecting the actual voltage u C of the capacitor in real time, calculating its deviation Δu C based on the capacitor reference voltage u Cref obtained in step (2), and processing it by proportional integral-vector proportional integral composite control algorithm to obtain the capacitor reference current i Cref ;

(4)实时检测Buck-Boost逆变电路的实际输出电流i、Buck-Boost逆变电路输入侧直流电压

Figure BDA0004161029070000021
及电容电压实际值uC，根据步骤(3)所得电容参考电流iCref，计算得Buck-Boost逆变电路中的电感参考电流iLref；(4) Real-time detection of the actual output current i of the Buck-Boost inverter circuit and the DC voltage on the input side of the Buck-Boost inverter circuit
Figure BDA0004161029070000021
and the actual value of the capacitor voltage u C , and according to the capacitor reference current i Cref obtained in step (3), the inductor reference current i Lref in the Buck-Boost inverter circuit is calculated;

(5)实时检测电感实际电流iL，根据步骤(4)所得电感的参考电流iLref，计算得其偏差ΔiL，经比例积分-矢量比例积分复合控制算法处理，得电感参考电压uLref；(5) Real-time detection of the actual inductor current i L , and calculation of its deviation Δi L based on the inductor reference current i Lref obtained in step (4), and processing by a proportional-integral-vector proportional-integral composite control algorithm to obtain an inductor reference voltage u Lref ;

(6)根据步骤(5)所得的电感参考电压uLref，以及实时检测的Buck-Boost逆变电路输入侧直流电压

Figure BDA0004161029070000022
及电容电压实际值uC，求得Buck-Boost逆变电路中对应功率开关的占空比d；(6) Based on the inductor reference voltage u Lref obtained in step (5) and the real-time detected DC voltage at the input side of the Buck-Boost inverter circuit
Figure BDA0004161029070000022
and the actual value of the capacitor voltage u C , and obtain the duty cycle d of the corresponding power switch in the Buck-Boost inverter circuit;

(7)根据步骤(6)所得占空比d及相应的开关周期，对Buck-Boost逆变电路中对应功率开关进行控制。(7) According to the duty cycle d and the corresponding switching period obtained in step (6), the corresponding power switch in the Buck-Boost inverter circuit is controlled.

更优选地，通过公式(1)计算步骤(1)中所述Buck-Boost逆变电路的输出电压参考值uref：More preferably, the output voltage reference value u ref of the Buck-Boost inverter circuit in step (1) is calculated by formula (1):

Figure BDA0004161029070000023
Figure BDA0004161029070000023

式中：UDCref为直流稳压电源的输出电压参考值预设值，ω和θ分别为Buck-Boost逆变电路输出电压参考值的角频率和初始相位角，t为Buck-Boost逆变电路运行的某一时刻，L-1为拉氏反变换运算符，ΔU(s)为输出电压偏差ΔU的拉普拉斯象函数，G3(s)为PI控制器的传递函数。Wherein: U DCref is the preset value of the output voltage reference value of the DC regulated power supply, ω and θ are the angular frequency and initial phase angle of the output voltage reference value of the Buck-Boost inverter circuit, t is a certain moment when the Buck-Boost inverter circuit is running, L -1 is the Laplace inverse transform operator, ΔU(s) is the Laplace image function of the output voltage deviation ΔU, and G 3 (s) is the transfer function of the PI controller.

更优选地，通过公式(3)计算步骤(2)中电容的参考电压uCref：More preferably, the reference voltage u Cref of the capacitor in step (2) is calculated by formula (3):

Figure BDA0004161029070000031
Figure BDA0004161029070000031

式中：k为直流偏置电压系数，UDCref为直流稳压电源输出电压参考值预设值，uref为Buck-Boost逆变电路的输出电压参考值，L-1为拉氏反变换运算符，ΔU(s)为输出电压偏差ΔU的拉普拉斯象函数，G3(s)为PI控制器的传递函数。Wherein: k is the DC bias voltage coefficient, U DCref is the preset value of the DC regulated power supply output voltage reference value, u ref is the output voltage reference value of the Buck-Boost inverter circuit, L -1 is the Laplace inverse transform operator, ΔU(s) is the Laplace image function of the output voltage deviation ΔU, and G 3 (s) is the transfer function of the PI controller.

进一步，通过公式(2)计算PI控制器的传递函数G3(s)：Furthermore, the transfer function G 3 (s) of the PI controller is calculated by formula (2):

Figure BDA0004161029070000032
Figure BDA0004161029070000032

式中：KP和KI分别为比例系数和积分系数，s为微分算子。In the formula: K P and KI are the proportional coefficient and integral coefficient respectively, and s is the differential operator.

更优选地，通过公式(4)计算步骤(3)中逆变电路中的电容参考电流iCref：More preferably, the capacitor reference current i Cref in the inverter circuit in step (3) is calculated by formula (4):

iCref＝L-1[G1(s)·ΔuC(s)] (4)i Cref =L -1 [G 1 (s)·Δu C (s)] (4)

式中：L-1为拉氏反变换运算符，ΔuC(s)为电容电压偏差ΔuC的拉普拉斯象函数，G1(s)为比例积分-矢量比例积分复合控制器的传递函数，其中：Where: L -1 is the Laplace inverse transform operator, Δu C (s) is the Laplace image function of the capacitor voltage deviation Δu C , G 1 (s) is the transfer function of the proportional integral-vector proportional integral compound controller, where:

Figure BDA0004161029070000033
Figure BDA0004161029070000033

式中：a＝KCP/rC，b1＝-KCP+rCCKCI+2rCCKCV，b2＝-25KCPω2+2rCCKCR，b3＝-25KCIrCCω2，c1＝rC 2C，c2＝rC，c3＝25rC(1+rCC)ω2，其中KCP和KCI分别为比例积分控制的比例系数和积分系数，KCV和KCR分别为矢量比例积分控制的比例系数和增益系数，其中KCR＝8KCVRf/π2L，Rf为负载电阻，ω为Buck-Boost逆变电路输出电压角频率，C为Buck-Boost逆变电路中的电容值，rC为电容C的等效电阻，s为微分算子。In the formula: a＝K CP /r C , b 1 ＝-K CP +r C CK CI +2r C CK CV , b 2 ＝-25K CP ω 2 +2r C CK CR , b 3 ＝-25K CI r C Cω 2 , c 1 ＝r C 2 C, c 2 ＝r C , c 3 ＝25r C (1+r C C)ω 2 , where K CP and K CI are the proportional coefficient and integral coefficient of proportional-integral control respectively, K CV and K CR are the proportional coefficient and gain coefficient of vector proportional-integral control respectively, where K CR ＝8K CV R f /π 2 L, R f is the load resistance, ω is the output voltage angular frequency of the Buck-Boost inverter circuit, C is the capacitance value in the Buck-Boost inverter circuit, r C is the equivalent resistance of capacitor C, and s is the differential operator.

更优选地，通过公式(6)得步骤(4)所述电感参考电流iLref：More preferably, the inductor reference current i Lref in step (4) is obtained by formula (6):

Figure BDA0004161029070000034
Figure BDA0004161029070000034

式中：i为Buck-Boost逆变电路的实际输出电流，uC为电容电压，

Figure BDA0004161029070000035
为Buck-Boost逆变电路输入侧直流电压。Where: i is the actual output current of the Buck-Boost inverter circuit, u C is the capacitor voltage,
Figure BDA0004161029070000035
It is the DC voltage on the input side of the Buck-Boost inverter circuit.

更优选地，通过公式(7)得步骤(5)中所述电感参考电压uLref：More preferably, the inductor reference voltage u Lref in step (5) is obtained by formula (7):

uLref＝L-1[G2(s)·ΔiL(s)] (7)u Lref =L -1 [G 2 (s)·Δi L (s)] (7)

式中：L-1为拉氏反变换运算符，ΔiL(s)为电感电流偏差ΔiL的拉普拉斯象函数，ΔiL＝iL-iLref，G2(s)为比例积分-矢量比例积分复合控制器的传递函数，其中：Where: L -1 is the Laplace inverse transform operator, Δi L (s) is the Laplace image function of the inductor current deviation Δi L , Δi L =i L -i Lref , G 2 (s) is the transfer function of the proportional integral-vector proportional integral compound controller, where:

Figure BDA0004161029070000041
Figure BDA0004161029070000041

式中：d1＝KLP，d2＝KLI+2KLV，d3＝2KLR+25KLPω2，d4＝25KLIω2，e1＝L，e2＝rL，e3＝25Lω2,e4＝25rLω2，其中KLP和KLI分别为比例积分控制的比例系数和积分系数，KLV和KLR分别为矢量比例积分控制的比例系数和增益系数，其中KCR＝8KCVRf/π2L，Rf为负载电阻，ω为Buck-Boost逆变电路输出电压角频率，L为Buck-Boost逆变电路中的电感值，rL为电感L的等效电阻，T为Buck-Boost逆变电路中功率开关的开关周期，s为微分算子。In the formula: d 1 =K LP , d 2 =K LI +2K LV , d 3 =2K LR +25K LP ω 2 , d 4 =25K LI ω 2 , e 1 =L, e 2 =r L , e 3 =25Lω 2 , e 4 =25r L ω 2 , where K LP and K LI are the proportional coefficient and integral coefficient of proportional-integral control respectively, K LV and K LR are the proportional coefficient and gain coefficient of vector proportional-integral control respectively, where K CR =8K CV R f /π 2 L, R f is the load resistance, ω is the output voltage angular frequency of the Buck-Boost inverter circuit, L is the inductance value in the Buck-Boost inverter circuit, r L is the equivalent resistance of the inductor L, T is the switching period of the power switch in the Buck-Boost inverter circuit, and s is the differential operator.

更优选地，步骤(6)中，通过公式(9)得占空比d：More preferably, in step (6), the duty cycle d is obtained by formula (9):

Figure BDA0004161029070000042
Figure BDA0004161029070000042

式中：uC为电容电压实测值，

Figure BDA0004161029070000043
为Buck-Boost逆变电路输入侧直流电压的实测值。Where: u C is the measured value of capacitor voltage,
Figure BDA0004161029070000043
It is the measured value of the DC voltage on the input side of the Buck-Boost inverter circuit.

本发明的有益效果在于：本发明提供的基于Buck-Boost逆变电路的低纹波可调直流稳压电源控制方法输出电压参考值，通过采用比例积分-矢量比例积分复合控制算法对Buck-Boost逆变电路中的电容参考电压与其实际电压的偏差进行计算，将所得电容参考电流换算为电感参考电流，再继续采用比例积分-矢量比例积分复合控制算法对电感参考电流与其实际电流的偏差进行计算，得Buck-Boost逆变电路中对应功率开关的占空比；根据所得占空比对Buck-Boost逆变电路中对应功率开关进行控制，即可实现在保持其直流稳压电源的实际输出电压对其设定的参考输出电压无静差准确跟踪的基础上，达到有效提高其输出电压稳态精度并降低其输出纹波的目的。本发明所提控制方法具有控制算法简单、输出电压稳态精度高、纹波小、动态性能好等特点。The beneficial effects of the present invention are as follows: the output voltage reference value of the low ripple adjustable DC regulated power supply control method based on the Buck-Boost inverter circuit provided by the present invention is calculated by using the proportional integral-vector proportional integral composite control algorithm to calculate the deviation between the capacitor reference voltage and its actual voltage in the Buck-Boost inverter circuit, converting the obtained capacitor reference current into the inductor reference current, and then continuing to use the proportional integral-vector proportional integral composite control algorithm to calculate the deviation between the inductor reference current and its actual current, and obtaining the duty cycle of the corresponding power switch in the Buck-Boost inverter circuit; according to the obtained duty cycle, the corresponding power switch in the Buck-Boost inverter circuit is controlled, so that the actual output voltage of the DC regulated power supply can be accurately tracked to the reference output voltage set without static error, so as to effectively improve the steady-state accuracy of the output voltage and reduce the output ripple. The control method proposed by the present invention has the characteristics of simple control algorithm, high steady-state accuracy of output voltage, small ripple, good dynamic performance, etc.

附图说明BRIEF DESCRIPTION OF THE DRAWINGS

图1为基于Buck-Boost逆变电路的低纹波可调直流稳压电源主电路拓扑结构图；FIG1 is a main circuit topology diagram of a low ripple adjustable DC regulated power supply based on a Buck-Boost inverter circuit;

图2为本发明提供的基于Buck-Boost逆变电路的低纹波可调直流稳压电源控制方法原理框图；FIG2 is a principle block diagram of a low ripple adjustable DC regulated power supply control method based on a Buck-Boost inverter circuit provided by the present invention;

图3为本发明提供的基于Buck-Boost逆变电路的低纹波可调直流稳压电源输出电压参考值为1000V的输出直流电压波形图。FIG3 is an output DC voltage waveform diagram of a low ripple adjustable DC regulated power supply based on a Buck-Boost inverter circuit provided by the present invention, wherein the output voltage reference value is 1000V.

具体实施方式DETAILED DESCRIPTION

下面结合附图和实施例对本发明作进一步的说明。The present invention will be further described below in conjunction with the accompanying drawings and embodiments.

图1为本发明所提供的基于Buck-Boost逆变电路的低纹波可调直流稳压电源主电路的拓扑结构图。该拓扑结构采用AC-DC-AC-DC结构形式，包括三相PWM整流电路、三相交错并联Buck-Boost中频逆变电路及三相桥式不可控整流电路3部分，其中：Figure 1 is a topological diagram of the main circuit of the low-ripple adjustable DC regulated power supply based on the Buck-Boost inverter circuit provided by the present invention. The topological structure adopts an AC-DC-AC-DC structure, including three-phase PWM rectifier circuit, three-phase interleaved parallel Buck-Boost intermediate frequency inverter circuit and three-phase bridge uncontrolled rectifier circuit, wherein:

三相PWM整流电路由6只全控型功率开关构成，用于将三相输入交流电压整流为PWM调制的直流电压；三相交错并联Buck-Boost中频逆变电路由3组Buck-Boost升降压电路采用相位交错并联的方式构成，用于将三相PWM整流电路输出的PWM调制直流电压逆变为幅值和频率任意可调的三相对称中频正弦交流电压；三相桥式不可控整流电路由6只整流二极管和1个滤波电容构成，用于将三相交错并联Buck-Boost中频逆变电路输出的三相对称中频正弦交流电压整流为直流电压。The three-phase PWM rectifier circuit is composed of 6 fully controlled power switches, which are used to rectify the three-phase input AC voltage into a PWM modulated DC voltage; the three-phase interleaved parallel Buck-Boost intermediate frequency inverter circuit is composed of 3 groups of Buck-Boost buck-boost circuits in a phase-interleaved parallel manner, which is used to invert the PWM modulated DC voltage output by the three-phase PWM rectifier circuit into a three-phase symmetrical intermediate frequency sinusoidal AC voltage with arbitrarily adjustable amplitude and frequency; the three-phase bridge uncontrolled rectifier circuit is composed of 6 rectifier diodes and 1 filter capacitor, which is used to rectify the three-phase symmetrical intermediate frequency sinusoidal AC voltage output by the three-phase interleaved parallel Buck-Boost intermediate frequency inverter circuit into a DC voltage.

采用上述Buck-Boost中频逆变电路的低纹波可调直流稳压电源的控制方法具体步骤如下：The specific steps of the control method of the low ripple adjustable DC regulated power supply using the above-mentioned Buck-Boost intermediate frequency inverter circuit are as follows:

(1)根据直流稳压电源的输出电压预设值UDCref和输出电压实测值UDC，通过公式(1)计算得三相交错并联Buck-Boost中频逆变电路的输出电压参考值uref：(1) According to the output voltage preset value U DCref of the DC regulated power supply and the output voltage measured value U DC , the output voltage reference value u ref of the three-phase interleaved parallel Buck-Boost intermediate frequency inverter circuit is calculated by formula (1):

Figure BDA0004161029070000051
Figure BDA0004161029070000051

式中：UDCref为直流稳压电源的输出电压参考值预设值，ω和θ分别为Buck-Boost逆变电路输出电压参考值的角频率和初始相位角，t为Buck-Boost逆变电路运行的某一时刻，L-1为拉氏反变换运算符，ΔU(s)为输出电压偏差ΔU的拉普拉斯象函数，ΔU＝UDC-UDCref，G3(s)为PI控制器的传递函数，其函数关系式为：Wherein: U DCref is the preset value of the output voltage reference value of the DC regulated power supply, ω and θ are the angular frequency and initial phase angle of the output voltage reference value of the Buck-Boost inverter circuit respectively, t is a certain moment when the Buck-Boost inverter circuit is running, L -1 is the Laplace inverse transform operator, ΔU(s) is the Laplace image function of the output voltage deviation ΔU, ΔU＝U DC -U DCref , G 3 (s) is the transfer function of the PI controller, and its functional relationship is:

Figure BDA0004161029070000061
Figure BDA0004161029070000061

式中：KP和KI分别为比例系数和积分系数，s为微分算子。In the formula: K P and KI are the proportional coefficient and integral coefficient respectively, and s is the differential operator.

(2)根据步骤(1)所得Buck-Boost中频逆变电路的输出电压参考值uref，得该逆变电路中的电容参考电压uCref，具体为：(2) According to the output voltage reference value u ref of the Buck-Boost intermediate frequency inverter circuit obtained in step (1), the capacitor reference voltage u Cref in the inverter circuit is obtained, which is specifically:

Figure BDA0004161029070000062
Figure BDA0004161029070000062

式中：k为直流偏置电压系数，由计算机仿真结果而得，在本实施例中取值为1.5，UDCref为直流稳压电源输出电压参考值预设值，uref为Buck-Boost中频逆变电路的输出电压参考值。Wherein: k is the DC bias voltage coefficient, obtained from computer simulation results, and in this embodiment is taken as 1.5, U DCref is the preset value of the DC regulated power supply output voltage reference value, and u ref is the output voltage reference value of the Buck-Boost intermediate frequency inverter circuit.

(3)根据步骤(2)所得的电容参考电压uCref，同时实时检测电容的实际电压uC，通过公式(4)计算得该逆变电路中的电容参考电流iCref，具体为：(3) Based on the capacitor reference voltage u Cref obtained in step (2), the actual voltage u C of the capacitor is detected in real time, and the capacitor reference current i Cref in the inverter circuit is calculated by formula (4), which is specifically:

iCref＝L-1[G1(s)·ΔuC(s)] (4)i Cref =L -1 [G 1 (s)·Δu C (s)] (4)

式中：L-1为拉氏反变换运算符，ΔuC(s)为电容电压偏差ΔuC的拉普拉斯象函数，ΔuC＝uC-uCref，G1(s)为比例积分-矢量比例积分复合控制器的传递函数，其函数关系式为：Wherein: L -1 is the Laplace inverse transform operator, Δu C (s) is the Laplace image function of the capacitor voltage deviation Δu C , Δu C =u C -u Cref , G 1 (s) is the transfer function of the proportional integral-vector proportional integral compound controller, and the functional relationship is:

Figure BDA0004161029070000063
Figure BDA0004161029070000063

式中：a＝KCP/rC，b1＝-KCP+rCCKCI+2rCCKCV，b2＝-25KCPω2+2rCCKCR，b3＝-25KCIrCCω2，

Figure BDA0004161029070000064
c2＝rC，c3＝25rC(1+rCC)ω2，其中KCP和KCI分别为比例积分控制的比例系数和积分系数，KCV和KCR分别为矢量比例积分控制的比例系数和增益系数，其中KCR＝8KCVRf/π2L，Rf为负载电阻，ω为Buck-Boost逆变电路输出电压参考值的角频率，C为Buck-Boost中频逆变电路中的电容值，rC为电容C的等效电阻，s为微分算子。In the formula: a＝K CP /r C , b 1 ＝-K CP +r C CK CI +2r C CK CV , b 2 ＝-25K CP ω 2 +2r C CK CR , b 3 ＝-25K CI r C Cω2 ,
Figure BDA0004161029070000064
c 2 = r C , c 3 = 25 r C (1 + r C C) ω 2 , where K CP and K CI are the proportional coefficient and integral coefficient of proportional integral control, respectively, and K CV and K CR are the vector proportional integral control The proportional coefficient and gain coefficient are KCR = 8K CV Rf / π2L , Rf is the load resistance, ω is the angular frequency of the output voltage reference value of the Buck-Boost inverter circuit, and C is the Buck-Boost intermediate frequency inverter. The capacitance value in the circuit, r C is the equivalent resistance of capacitor C, and s is the differential operator.

(4)根据步骤(3)所得电容参考电流iCref，和实时检测的Buck-Boost中频逆变电路的实际输出电流i、Buck-Boost中频逆变电路输入侧直流电压

Figure BDA0004161029070000071
及电容电压实际值uC，通过公式(6)计算得Buck-Boost中频逆变电路中的电感参考电流iLref：(4) Based on the capacitor reference current i Cref obtained in step (3), the actual output current i of the Buck-Boost intermediate frequency inverter circuit detected in real time, and the DC voltage at the input side of the Buck-Boost intermediate frequency inverter circuit
Figure BDA0004161029070000071
and the actual value of the capacitor voltage u C , the inductor reference current i Lref in the Buck-Boost medium frequency inverter circuit is calculated by formula (6):

Figure BDA0004161029070000072
Figure BDA0004161029070000072

式中：i为Buck-Boost中频逆变电路的实际输出电流，uC为电容电压实际值，

Figure BDA0004161029070000073
为Buck-Boost中频逆变电路输入侧直流电压。Where: i is the actual output current of the Buck-Boost medium frequency inverter circuit, u C is the actual value of the capacitor voltage,
Figure BDA0004161029070000073
It is the DC voltage at the input side of the Buck-Boost medium frequency inverter circuit.

(5)根据步骤(4)所得电感参考电流iLref，与实时检测的电感电流实际值iL，通过公式(7)计算得电感参考电压uLref：(5) Based on the inductor reference current i Lref obtained in step (4) and the real-time detected inductor current actual value i L , the inductor reference voltage u Lref is calculated by formula (7):

uLref＝L-1[G2(s)·ΔiL(s)] (7)u Lref =L -1 [G 2 (s)·Δi L (s)] (7)

式中：L-1为拉氏反变换运算符，ΔiL(s)为电感电流偏差ΔiL的拉普拉斯象函数，ΔiL＝iL-iLref，G2(s)为比例积分-矢量比例积分复合控制器的传递函数，其函数关系式为：Where: L -1 is the Laplace inverse transform operator, Δi L (s) is the Laplace image function of the inductor current deviation Δi L , Δi L =i L -i Lref , G 2 (s) is the transfer function of the proportional integral-vector proportional integral compound controller, and the functional relationship is:

Figure BDA0004161029070000074
Figure BDA0004161029070000074

式中：d1＝KLP，d2＝KLI+2KLV，d3＝2KLR+25KLPω2，d4＝25KLIω2，e1＝L，e2＝rL，e3＝25Lω2,e4＝25rLω2，其中KLP和KLI分别为比例积分控制的比例系数和积分系数，KLV和KLR分别为矢量比例积分控制的比例系数和增益系数，其中KCR＝8KCVRf/π2L，Rf为负载电阻，ω为Buck-Boost逆变电路输出电压参考值的角频率，L为Buck-Boost中频逆变电路中的电感值，rL为电感L的等效电阻，T为Buck-Boost中频逆变电路中功率开关的开关周期，s为微分算子。In the formula: d 1 =K LP , d 2 =K LI +2K LV , d 3 =2K LR +25K LP ω 2 , d 4 =25K LI ω 2 , e 1 =L, e 2 =r L , e 3 =25Lω 2 , e 4 =25r L ω 2 , where K LP and K LI are the proportional coefficient and integral coefficient of proportional-integral control respectively, K LV and K LR are the proportional coefficient and gain coefficient of vector proportional-integral control respectively, where K CR =8K CV R f /π 2 L, R f is the load resistance, ω is the angular frequency of the output voltage reference value of the Buck-Boost inverter circuit, L is the inductance value in the Buck-Boost intermediate frequency inverter circuit, r L is the equivalent resistance of the inductor L, T is the switching period of the power switch in the Buck-Boost intermediate frequency inverter circuit, and s is the differential operator.

(6)根据步骤(5)所得电感的参考电压uLref，以及上述检测的Buck-Boost中频逆变电路输入侧直流电压

Figure BDA0004161029070000075
及电容电压实际值uC，通过公式(9)计算得Buck-Boost中频逆变电路中对应功率开关的占空比d：(6) The reference voltage u Lref of the inductor obtained in step (5) and the DC voltage at the input side of the Buck-Boost intermediate frequency inverter circuit detected above are
Figure BDA0004161029070000075
And the actual value of capacitor voltage u C , the duty cycle d of the corresponding power switch in the Buck-Boost medium frequency inverter circuit is calculated by formula (9):

Figure BDA0004161029070000081
Figure BDA0004161029070000081

式中：uC为电容电压实测值，

Figure BDA0004161029070000082
为Buck-Boost中频逆变电路输入侧直流电压的实测值。Where: u C is the measured value of capacitor voltage,
Figure BDA0004161029070000082
It is the measured value of the DC voltage on the input side of the Buck-Boost medium frequency inverter circuit.

(7)根据步骤(6)所得占空比d及相应的开关周期，对Buck-Boost中频逆变电路中对应功率开关进行控制，即可通过调节占空比来调节电感电流，再通过电感电流来调节电容电压，最后使电容电压与其参考值保持一致，在实现Buck-Boost中频逆变电路实际输出电压对其参考输出电压准确跟踪的前提下，有效抑制其输出电压波形中的谐波含量，从而达到有效降低该直流稳压电源输出电压纹波的目的。(7) According to the duty cycle d and the corresponding switching period obtained in step (6), the corresponding power switch in the Buck-Boost medium frequency inverter circuit is controlled, so that the inductor current is adjusted by adjusting the duty cycle, and the capacitor voltage is adjusted by the inductor current, and finally the capacitor voltage is kept consistent with its reference value. Under the premise of achieving accurate tracking of the actual output voltage of the Buck-Boost medium frequency inverter circuit with its reference output voltage, the harmonic content in its output voltage waveform is effectively suppressed, thereby achieving the purpose of effectively reducing the output voltage ripple of the DC regulated power supply.

图2为本发明提供的基于Buck-Boost中频逆变电路的低纹波可调直流稳压电源的控制方法原理框图，对本发明提供的一种基于Buck-Boost中频逆变电路的低纹波可调直流稳压电源控制方法做进一步具体的说明：对Buck-Boost中频逆变电路中电容电压与电感电流两状态变量分别构建相应的控制闭环，其中以电容电压为控制外环，电感电流为控制内环。FIG2 is a principle block diagram of a control method for a low ripple adjustable DC regulated power supply based on a Buck-Boost intermediate frequency inverter circuit provided by the present invention, and further specifically describes a control method for a low ripple adjustable DC regulated power supply based on a Buck-Boost intermediate frequency inverter circuit provided by the present invention: corresponding control closed loops are constructed for the two state variables of the capacitor voltage and the inductor current in the Buck-Boost intermediate frequency inverter circuit, wherein the capacitor voltage is used as the control outer loop and the inductor current is used as the control inner loop.

为验证本发明所提供的一种基于Buck-Boost中频逆变电路的低纹波可调直流稳压电源控制方法的效果，同时为便于与专利申请“一种低纹波可调直流稳压电源及其控制方法”(申请号：202211033703.5)(简称对比文件)中的控制方法进行对比分析，因而选取和对比文件中相同的主电路参数进行相应的对比分析研究，其主电路参数如表1所示，并设本发明所提控制方法所对应的控制参数如表2所示。In order to verify the effect of the low ripple adjustable DC regulated power supply control method based on the Buck-Boost medium frequency inverter circuit provided by the present invention, and to facilitate comparative analysis with the control method in the patent application "A low ripple adjustable DC regulated power supply and its control method" (application number: 202211033703.5) (hereinafter referred to as the comparative document), the main circuit parameters that are the same as those in the comparative document are selected for corresponding comparative analysis and research. The main circuit parameters are shown in Table 1, and the control parameters corresponding to the control method proposed in the present invention are shown in Table 2.

表1直流稳压电源主电路参数Table 1 DC regulated power supply main circuit parameters

序号Serial number 名称name 参数parameter 11 Buck-Boost中频逆变电路中电感L1 Inductor L1 in Buck-Boost medium frequency inverter circuit 7uH7uH 22 Buck-Boost中频逆变电路中电容C1 Capacitor C1 in Buck-Boost medium frequency inverter circuit 9uF9uF 33 输出滤波电容Cf Output filter capacitor C f 100uF100uF 44 负载电阻Ro Load resistance R o 3kΩ3kΩ

表2本发明控制方法相关控制参数Table 2 Control parameters related to the control method of the present invention

Figure BDA0004161029070000083
Figure BDA0004161029070000083

Figure BDA0004161029070000091
Figure BDA0004161029070000091

和对比文件中一致，设该直流稳压电源的三相交流输入电压为380V/50Hz，其Buck-Boost中频逆变电路的输出频率为1kHz，并取该直流稳压电源的输出直流参考电压分别为200V、300V、400V、500V、600V、700V、800V、900V、1000V，则根据表1所示主电路参数及表2所示控制参数，利用上述控制方法得到相应的分析结果，如表3所示，在对比文件中所得分析结果则如表4所示。Consistent with the comparative document, assuming that the three-phase AC input voltage of the DC regulated power supply is 380V/50Hz, the output frequency of its Buck-Boost medium frequency inverter circuit is 1kHz, and the output DC reference voltage of the DC regulated power supply is 200V, 300V, 400V, 500V, 600V, 700V, 800V, 900V, and 1000V, respectively, then according to the main circuit parameters shown in Table 1 and the control parameters shown in Table 2, the corresponding analysis results are obtained by using the above control method, as shown in Table 3, and the analysis results obtained in the comparative document are shown in Table 4.

表3本发明控制方法所得分析结果Table 3 Analysis results obtained by the control method of the present invention

输出电压参考值Output voltage reference value 实际输出电压Actual output voltage 输出电压偏差Output voltage deviation 输出纹波电压Output ripple voltage 200V200V 199.99V199.99V 0.01V0.01V 0.052V0.052V 300V300V 299.98V299.98V 0.02V0.02V 0.054V0.054V 400V400V 399.98V399.98V 0.02V0.02V 0.055V0.055V 500V500V 499.98V499.98V 0.02V0.02V 0.057V0.057V 600V600V 599.97V599.97V 0.03V0.03V 0.057V0.057V 700V700V 699.97V699.97V 0.03V0.03V 0.058V0.058V 800V800V 799.96V799.96V 0.04V0.04V 0.058V0.058V 900V900V 899.96V899.96V 0.04V0.04V 0.059V0.059V 1000V1000V 999.96V999.96V 0.04V0.04V 0.058V0.058V

图3为表3中输出电压参考值为1000V所对应的输出直流电压波形图，由图3可知，其输出电压波形纹波小、稳态精度高。FIG3 is a waveform diagram of the output DC voltage corresponding to the output voltage reference value of 1000V in Table 3. As can be seen from FIG3 , the output voltage waveform has a small ripple and a high steady-state accuracy.

表4对比文件中所得分析结果Table 4 Analysis results obtained in the comparative documents

输出电压参考值Output voltage reference value 实际输出电压Actual output voltage 输出电压偏差Output voltage deviation 输出纹波电压Output ripple voltage 200V200V 199.98V199.98V 0.02V0.02V 0.1V0.1V 300V300V 299.98V299.98V 0.02V0.02V 0.11V0.11V 400V400V 399.97V399.97V 0.03V0.03V 0.12V0.12V 500V500V 499.97V499.97V 0.03V0.03V 0.14V0.14V 600V600V 599.97V599.97V 0.03V0.03V 0.14V0.14V 700V700V 699.96V699.96V 0.04V0.04V 0.18V0.18V 800V800V 799.95V799.95V 0.05V0.05V 0.20V0.20V 900V900V 899.94V899.94V 0.06V0.06V 0.25V0.25V 1000V1000V 999.93V999.93V 0.07V0.07V 0.30V0.30V

根据表3和表4可见，本发明所提供的基于Buck-Boost逆变电路的低纹波可调直流稳压电源控制方法，相对于对比文件中所采用的双闭环PI控制方法，不仅明显减小了其实际直流输出电压相对于其参考输出电压间的稳态误差，而且显著降低了其输出电压中的纹波分量，从而有效提高了其输出电压的波形质量，具有较好的应用价值。It can be seen from Table 3 and Table 4 that the low ripple adjustable DC regulated power supply control method based on Buck-Boost inverter circuit provided by the present invention not only significantly reduces the steady-state error between its actual DC output voltage and its reference output voltage, but also significantly reduces the ripple component in its output voltage, thereby effectively improving the waveform quality of its output voltage, and has good application value.

Claims (10)

1. The control method is characterized in that a capacitance reference current is calculated by adopting a proportional integral-vector proportional integral composite control algorithm to calculate the deviation between capacitance reference voltage and actual voltage in the Buck-Boost inverter circuit, the obtained capacitance reference current is converted into an inductance reference current, and then the proportional integral-vector proportional integral composite control algorithm is continuously adopted to calculate the deviation between the inductance reference current and the actual current to obtain a duty ratio, and a corresponding power switch in the Buck-Boost inverter circuit is controlled according to the obtained duty ratio.
2. The control method of the low-ripple adjustable direct-current stabilized power supply based on the Buck-Boost inverter circuit as claimed in claim 1, comprising the following steps:
(1) Real-time detection of output voltage actual measurement value U of direct-current stabilized power supply DC According to the preset value U of the output voltage of the direct current stabilized power supply DCref Calculating an output voltage reference value u of the three-phase staggered parallel Buck-Boost inverter circuit ref ；
(2) According to the output voltage reference value u of the Buck-Boost inverter circuit obtained in the step (1) ref Obtaining a capacitance reference voltage u in the inverter circuit Cref ；
(3) Detecting the actual voltage u of the capacitor in real time C According to the capacitance reference voltage u obtained in the step (2) Cref Calculate the deviation Deltau C The capacitance reference current i is obtained through the processing of a proportional integral-vector proportional integral composite control algorithm Cref ；
(4) Real-time detection of actual output current i of Buck-Boost inverter circuit and direct-current voltage at input side of Buck-Boost inverter circuit
Figure FDA0004161029060000011
Actual value u of capacitance voltage C According to the capacitance reference current i obtained in the step (3) Cref The inductance reference current i in the Buck-Boost inverter circuit is calculated Lref ；
(5) Real-time detection of inductor actual current i L The reference current i of the inductor obtained according to the step (4) Lref Calculate the deviation Δi L The inductance reference voltage u is obtained through the processing of a proportional integral-vector proportional integral composite control algorithm Lref ；
(6) According to step (5)The obtained inductance reference voltage u Lref And real-time detection of direct current voltage at input side of Buck-Boost inverter circuit
Figure FDA0004161029060000012
Actual value u of capacitance voltage C Obtaining the duty ratio d of a corresponding power switch in the Buck-Boost inverter circuit;
(7) And (3) controlling a corresponding power switch in the Buck-Boost inverter circuit according to the duty ratio d and the corresponding switching period obtained in the step (6).
3. The method for controlling a low ripple adjustable dc voltage regulator based on a Buck-Boost inverter according to claim 2, wherein the output voltage reference u of the Buck-Boost inverter in step (1) is calculated by equation (1) ref ：
Figure FDA0004161029060000021
Wherein: u (U) DCref The reference value of the output voltage of the direct-current stabilized power supply is preset, omega and theta are respectively the angular frequency and the initial phase angle of the reference value of the output voltage of the Buck-Boost inverter circuit, t is a certain moment of operation of the Buck-Boost inverter circuit, and L -1 For the Laplace inverse transformation operator, deltaU(s) is the Laplace image function of the output voltage deviation DeltaU, G 3 (s) is the transfer function of the PI controller.
4. The control method of the low-ripple adjustable direct-current stabilized power supply based on the Buck-Boost inverter circuit according to claim 2, wherein the reference voltage u of the capacitor in the step (2) is calculated by the formula (3) Cref ：
Figure FDA0004161029060000022
Wherein: k is a direct current bias voltage coefficient, U DCref Is a direct-current regulated power supplyOutput voltage reference value preset value u ref Is the output voltage reference value L of the Buck-Boost inverter circuit -1 For the Laplace inverse transformation operator, deltaU(s) is the Laplace image function of the output voltage deviation DeltaU, G 3 (s) is the transfer function of the PI controller.
5. The control method of the low ripple adjustable direct current regulated power supply based on the Buck-Boost inverter circuit according to claim 3 or 4, wherein the transfer function G of the PI controller is calculated by the formula (2) 3 (s)：
Figure FDA0004161029060000023
Wherein: k (K) P And K I The proportional coefficient and the integral coefficient are respectively, and s is a differential operator.
6. The control method of the low-ripple adjustable direct-current regulated power supply based on the Buck-Boost inverter circuit according to claim 2, wherein the capacitance reference current i in the inverter circuit in the step (3) is calculated by the formula (4) Cref ：
i Cref ＝L -1 [G 1 (s)·Δu C (s)] (4)
Wherein: l (L) -1 For the Law's inverse transform operator, deltau C (s) is the capacitance voltage deviation Deltau C Laplace image function, G 1 And(s) is a transfer function of the proportional-integral-vector proportional-integral composite controller.
7. The control method of the low-ripple adjustable direct-current stabilized power supply based on the Buck-Boost inverter circuit as claimed in claim 6, wherein the transfer function G 1 (s) is determined by formula (5):
Figure FDA0004161029060000031
wherein: a=k CP /r C ，b 1 ＝-K CP +r C CK CI +2r C CK CV ，b 2 ＝-25K CP ω 2 +2r C CK CR ，b 3 ＝-25K CI r C Cω 2 ，
Figure FDA0004161029060000034
c 2 ＝r C ，c 3 ＝25r C (1+r C C)ω 2 Wherein K is CP And K CI Proportional and integral coefficients, K, of proportional and integral control, respectively CV And K CR The proportional coefficient and the gain coefficient of the vector proportional integral control are respectively, wherein K CR ＝8K CV R f /π 2 L，R f Omega is the output voltage angular frequency of the Buck-Boost inverter circuit, C is the capacitance value in the Buck-Boost inverter circuit, and r is the load resistance C The equivalent resistance of the capacitor C, and s is a differential operator.
8. The control method of the low-ripple adjustable direct-current regulated power supply based on the Buck-Boost inverter circuit according to claim 2, wherein the inductance reference current i in the step (4) is obtained by a formula (6) Lref ：
Figure FDA0004161029060000032
Wherein: i is the actual output current of the Buck-Boost inverter circuit, u C In the form of a capacitor voltage, the capacitor voltage,
Figure FDA0004161029060000033
the DC voltage at the input side of the Buck-Boost inverter circuit.
9. The control method of the low-ripple adjustable direct-current regulated power supply based on the Buck-Boost inverter circuit according to claim 2, wherein the inductance in the step (5) is obtained by the formula (7)Reference voltage u Lref ：
u Lref ＝L -1 [G 2 (s)·Δi L (s)] (7)
Wherein: l (L) -1 For the Law's inverse transform operator Δi L (s) is the inductor current deviation Δi L Laplace image function, Δi L ＝i L -i Lref ，G 2 And(s) is a transfer function of the proportional-integral-vector proportional-integral composite controller.
10. The control method of the low ripple adjustable direct current stabilized power supply based on the Buck-Boost inverter circuit according to claim 9, wherein the transfer function G of the proportional-integral-vector proportional-integral composite controller is calculated by the formula (8) 2 (s)：
Figure FDA0004161029060000041
Wherein: d, d 1 ＝K LP ，d 2 ＝K LI +2K LV ，d 3 ＝2K LR +25K LP ω 2 ，d 4 ＝25K LI ω 2 ，e 1 ＝L，e 2 ＝r L ，e 3 ＝25Lω 2 ,e 4 ＝25r L ω 2 Wherein K is LP And K LI Proportional and integral coefficients, K, of proportional and integral control, respectively LV And K LR The proportional coefficient and the gain coefficient of the vector proportional integral control are respectively, wherein K CR ＝8K CV R f /π 2 L，R f Omega is the output voltage angular frequency of the Buck-Boost inverter circuit, L is the inductance value in the Buck-Boost inverter circuit, and r is the load resistance L And the equivalent resistance of the inductor L is T is the switching period of a power switch in the Buck-Boost inverter circuit, and s is a differential operator.
CN202310349695.3A 2023-04-04 2023-04-04 Low-ripple adjustable direct-current stabilized power supply control method based on Buck-Boost inverter circuit Pending CN116260343A (en)

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CN115224720A (en) * 2022-05-19 2022-10-21 盐城工学院 Multi-resonance VPI and PI combined control single-phase photovoltaic grid-connected inverter control method
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CN115224720A (en) * 2022-05-19 2022-10-21 盐城工学院 Multi-resonance VPI and PI combined control single-phase photovoltaic grid-connected inverter control method
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