CN114726189A - 400Hz intermediate frequency power supply control method and device based on Buck-Boost matrix converter - Google Patents

400Hz intermediate frequency power supply control method and device based on Buck-Boost matrix converter Download PDF

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CN114726189A
CN114726189A CN202210546126.3A CN202210546126A CN114726189A CN 114726189 A CN114726189 A CN 114726189A CN 202210546126 A CN202210546126 A CN 202210546126A CN 114726189 A CN114726189 A CN 114726189A
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bbmc
voltage
module
current
detection module
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张小平
钟达栩
龚俊
肖华银
余萍
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Hunan University of Science and Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/007—Regulation of charging or discharging current or voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
    • H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
    • H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
    • H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M5/4585—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only having a rectifier with controlled elements
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Power Engineering (AREA)
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Abstract

The invention provides a 400Hz intermediate frequency power supply control method and a device based on a Buck-Boost matrix converter, wherein the method comprises the steps of processing a reference value of a capacitor voltage in a control outer loop of a BBMC through a quasi-proportional resonant controller according to the deviation of the reference value and an actual value of the capacitor voltage in the control outer loop to obtain a reference value of an inductor current in the control inner loop, and processing the reference value of the inductor current in the control outer loop through the quasi-proportional resonant controller according to the deviation of the reference value and the actual value of the inductor current to obtain a duty ratio control signal of a corresponding power switch in the BBMC; and controlling corresponding power switches in the BBMC according to the obtained duty ratio control signal to realize that the actual output voltage of the BBMC is consistent with the reference voltage of the BBMC. The device comprises a BBMC rectification module, a BBMC inversion module, a network side voltage detection module, a direct current side voltage detection module, a capacitance voltage detection module, an inductive current detection module, an output current detection module, a DSP controller, a rectification IGBT driving module and an inversion IGBT driving module. The control method and the control device provided by the invention have the characteristics of high steady-state precision, good dynamic performance, few control parameters and the like.

Description

400Hz intermediate frequency power supply control method and device based on Buck-Boost matrix converter
Technical Field
The invention relates to the field of 400Hz intermediate frequency power supplies, in particular to a method and a device for controlling a 400Hz intermediate frequency power supply based on a Buck-Boost matrix converter.
Background
The 400Hz medium-frequency power supply is widely applied to the fields of military equipment, civil airports, industrial induction heating and the like. However, the current 400Hz intermediate frequency power supply has the defects of complex topological structure, large volume, heavy weight and the like, and causes adverse effects on the practical application of the power supply, so that the research on the topological structure of the 400Hz intermediate frequency power supply with a simpler structure has important significance.
The Buck-Boost matrix converter is a novel power converter which has a simple topological structure, can adjust output voltage and frequency at will and can directly output high-quality sine waves without a filtering link, so that the Buck-Boost matrix converter is very suitable for being applied to a 400Hz intermediate frequency power supply. However, in the current research on control strategies developed for BBMC, the output voltage frequency is in the low-frequency application field based on asynchronous motor speed regulation control, and when BBMC is required to be applied to a 400Hz intermediate frequency power supply, the existing control strategies are difficult to meet the requirements of steady-state control accuracy and dynamic performance.
Disclosure of Invention
In order to solve the technical problems, the invention provides a 400Hz intermediate frequency power supply control method and device based on a Buck-Boost matrix converter.
The invention solves the technical problem by constructing corresponding control closed loops for two state variables of capacitance voltage and inductance current in a Buck-Boost Matrix Converter (BBMC), wherein the capacitance voltage is used as a control outer loop, and the inductance current is used as a control inner loop; obtaining a reference value of corresponding capacitor voltage in a control outer ring of the BBMC through correlation transformation according to a reference output voltage signal of the BBMC, and processing the deviation of the reference value and an actual value of the reference value through a quasi-proportional resonant controller to obtain a reference value of the inductance current of the control inner ring; similarly, according to the deviation between the reference value of the obtained inductive current and the actual value of the inductive current, the duty ratio control signal of the corresponding power switch in the BBMC is obtained through the processing of the quasi-proportional resonant controller; and controlling the corresponding power switch in the BBMC according to the obtained duty ratio control signal, so that the actual output voltage of the BBMC can be kept consistent with the reference voltage thereof.
A400 Hz intermediate frequency power supply control method based on a Buck-Boost matrix converter comprises the following steps:
(1) superposing the direct current bias of the Buck-Boost matrix converter with a reference output voltage signal to obtain a corresponding capacitor voltage reference value uC1ref；
(2) Reference value u of capacitor voltageC1refAnd its actual value uC1Comparing to obtain a capacitor voltage deviation value delta uC1＝uC1-uC1ref；
(3) The deviation value delta u of the capacitor voltageC1As input of voltage control outer ring quasi-proportional resonant controller, the quasi-proportional resonant controller applies the voltage deviation value Delaut of capacitorC1Processing the signals to obtain a capacitance current reference value iC1refAnd an inductor current reference value iL1ref；
(4) Real-time detection of actual value i of inductor currentL1According to the reference value i of the inductive current obtained in the step (3)L1refCalculating to obtain the current deviation value delta i of the inductorL1＝iL1-iL1refAnd obtaining an inductance voltage reference value u through the processing of a current control inner ring quasi-proportional resonant controllerL1refThen according to the obtained reference value u of the inductor voltageL1refObtaining the duty ratio d of the corresponding power switch in the BBMC1；
(5) According to the duty ratio d obtained in the step (4)1And the set IGBT switching period is used for controlling the corresponding power switch in the BBMC, so that the output voltage consistent with the reference voltage of the BBMC can be obtained at the output end of the BBMC.
Preferably, in the step (3), the reference value i of the capacitance current is obtained by the formula (1)C1ref：
iC1ref＝L-1[GCPR(s)·ΔuC1(s)] (1)
In the formula: l is-1For the inverse Las transform operator, Δ uC1(s) is the deviation value of the capacitor voltage Deltau uC1Is of LapuLas elephant function, GCPR(s) is a transfer function of the quasi-proportional resonant controller, and the functional relation is as follows:
Figure BDA0003649587810000021
in the formula: kCPAnd KCRProportional control gain and resonant control gain, omega, of the voltage-controlled outer quasi-proportional resonant controller, respectivelycTo cut-off frequency, ω0Is the resonance frequency and s is a complex variable.
Preferably, in step (3), the reference value i of the inductor current is obtained by formula (3)L1ref：
Figure BDA0003649587810000031
In the formula: i.e. i1For BBMC output current measured value, uC1Is the measured value of the voltage of the capacitor,
Figure BDA0003649587810000032
the measured value of the BBMC direct-current side voltage is shown.
Preferably, in the step (4), the reference value u of the inductive voltage is obtained by the formula (4)L1ref：
uL1ref＝L-1[GLPR(s)ΔiL1(s)] (4)
In the formula: l is-1For the inverse Las transform operator, Δ iL1(s) is the inductor current deviation value Δ iL1Of the Laplace elephant function, GLPR(s) is a transfer function of the quasi-proportional resonant controller, and the functional relation is as follows:
Figure BDA0003649587810000033
in the formula: kLPAnd KLRProportional control gain and resonance control gain, omega, of the current-controlled inner loop quasi-proportional resonance controller, respectivelycIn order to cut-off the frequency of the frequency,ω0is the resonance frequency and s is a complex variable.
Preferably, in step (4), the duty ratio d is obtained by formula (6)1：
Figure BDA0003649587810000034
In the formula: u. ofC1Is the measured value of the capacitor voltage,
Figure BDA0003649587810000035
the measured value of the BBMC direct-current side voltage is shown.
Compared with the prior art, the invention firstly provides that the quasi-proportional resonance controller is adopted to sequentially process the deviation between the reference values and the actual values of the capacitor voltage and the inductor current to obtain the duty ratio control signals of the corresponding power switches in the BBMC, and the corresponding power switches in the BBMC can be controlled according to the obtained duty ratio control signals, so that the actual output voltage of the BBMC is consistent with the reference voltage thereof, and the purpose of accurately controlling the output voltage of the BBMC is achieved. The control method provided by the invention has the characteristics of high steady-state precision, good dynamic performance, few control parameters and the like.
Drawings
FIG. 1 is a step diagram of a BBMC-based 400Hz IF power supply control method provided by the present invention;
FIG. 2 is a main circuit topology structure diagram of a 400Hz intermediate frequency power control system based on BBMC provided by the present invention;
FIG. 3 is a schematic structural diagram of a BBMC-based 400Hz IF power control apparatus according to the present invention;
FIG. 4 is a schematic block diagram of a capacitor voltage control outer loop of the present invention;
FIG. 5 is a schematic block diagram of an inductor current control inner loop of the present invention;
FIG. 6 is a simulated waveform of the output voltage corresponding to quasi-proportional resonant control in accordance with the present invention;
fig. 7 is a simulated waveform of an output voltage corresponding to the composite control based on the repetitive control.
Detailed Description
The invention is further described below with reference to the figures and examples.
As shown in fig. 2, a main circuit topology structure diagram of the BBMC of the present invention is shown, the BBMC includes two parts, a rectification stage and an inverter stage, wherein the rectification stage is a three-phase PWM rectification circuit, which rectifies three-phase ac into PWM-modulated dc voltage; the inverter stage is a three-phase Buck-Boost inverter which is composed of three Buck-Boost DC/DC converters with the same structure.
As shown in fig. 3, a schematic structural diagram of the apparatus of the present invention includes a BBMC rectification module, a BBMC inversion module, a network side voltage detection module, a dc side voltage detection module, a capacitor voltage detection module, an inductor current detection module, an output current detection module, a DSP controller, a rectification-stage IGBT driving module, and an inversion-stage IGBT driving module. The input end of the BBMC rectification module is connected with a power grid, the output end of the BBMC rectification module is connected with the input end of the BBMC inversion module, and the output end of the BBMC inversion module is connected with a load; the input end of the network side voltage detection module is connected with a power grid, and the output end of the network side voltage detection module is connected with the DSP controller; the input end of the direct current side voltage detection module is connected with the output end of the BBMC rectification module, and the output end of the direct current side voltage detection module is connected with the input end of the DSP controller; the input ends of the capacitor voltage detection module, the inductive current detection module and the output current detection module are respectively connected with the BBMC inversion module, and the output ends of the capacitor voltage detection module, the inductive current detection module and the output current detection module are respectively connected with the input end of the DSP controller; the input end of the rectifier IGBT driving module is connected with the output end of the DSP controller, and the output end of the rectifier IGBT driving module is connected with the control signal input end of the BBMC rectifying module; the input end of the inverter IGBT driving module is connected with the output end of the DSP controller, and the output end of the inverter IGBT driving module is connected with the control signal input end of the BBMC inverter module.
Specifically, the grid side voltage detection module detects the voltage amplitude and the phase of each phase of the three-phase alternating current of the power grid and inputs the voltage amplitude and the phase into the DPS controller for calculation, and the DSP controller adopts the zero-vector-free methodA space vector modulation strategy (particularly, see a novel Buck-Boost matrix converter, information and control, 2008,37(1):40-45, Zhang Xiao Heng et al) calculates the on-off time of an IGBT (insulated Gate Bipolar transistor) in a BBMC rectification module, and an on-off pulse signal output by a DSP controller is amplified by a rectification stage IGBT driving module and then drives the IGBT in the BBMC rectification module, so that three-phase alternating current of a power grid is rectified into direct current; inputting the rectified direct current into a BBMC inversion module, and respectively detecting the direct current side voltage detection module, the capacitance voltage detection module, the inductance current detection module and the output current detection module to obtain a direct current side voltage measured value
Figure BDA0003649587810000051
Three-phase capacitance voltage measured value uC(1,2,3)Three-phase inductive current measured value iL(1,2,3)And three-phase output current measured value i(1,2,3)And the switching-on and switching-off pulse signals output by the DSP controller are amplified by the inverter stage IGBT driving module and then drive the IGBT in the BBMC inverter module, so that direct current is inverted into three-phase 400Hz medium-frequency alternating current.
FIG. 1 is a step diagram of a BBMC-based 400Hz IF power supply control method, which includes the following steps:
fig. 4 is a schematic block diagram of the capacitor voltage control outer loop of the present invention. The control loop is used for determining an inductor current reference value i of the inductor current control inner loopL1refFirstly, a capacitance voltage reference value u is obtained according to a reference output voltage signal of the BBMC through correlation transformationC1refNamely, 1.5 times of the amplitude of the reference output voltage of the BBMC is taken as the direct current bias, and the direct current bias is superposed with the reference output voltage signal to obtain the reference value u of the capacitor voltageC1ref(ii) a Then the reference value u of the capacitor voltage is calculatedC1refAnd the actual value u of the capacitor voltageC1Comparing to obtain the capacitance voltage deviation delta uC1Then using the deviation as the input of the voltage control outer ring quasi-proportional resonant controllerThe controller processes the reference value i of the capacitance currentC1refThe method specifically comprises the following steps:
iC1ref＝L-1[GCPR(s)·ΔuC1(s)] (1)
in the formula: l is-1For the inverse Las transform operator, Δ uC1(s) is the deviation value of the capacitor voltage DeltauC1Of the Laplace elephant function, GCPR(s) is a transfer function of the quasi-proportional resonant controller, and the functional relation is as follows:
Figure BDA0003649587810000052
in the formula: kCPAnd KCRProportional control gain and resonant control gain, omega, of the voltage-controlled outer quasi-proportional resonant controller, respectivelycTo cut-off frequency, ω0Is the resonance frequency and s is a complex variable.
Obtaining a reference value i of the capacitance current through the processing of the quasi-proportional resonant controllerC1refAnd simultaneously, the capacitor voltage u is respectively detected by the capacitor voltage detection module, the output current detection module and the direct current side voltage detection moduleC1Output current i1And DC side voltage
Figure BDA0003649587810000061
And obtaining the reference value i of the inductive current by correlation operation processingL1refThe concrete formula is as follows:
Figure BDA0003649587810000062
in the formula: i.e. i1For BBMC output current measured value, uC1Is the measured value of the capacitor voltage,
Figure BDA0003649587810000063
the measured value of the BBMC direct-current side voltage is shown.
Fig. 5 is a schematic block diagram of an inductor current control inner loop according to the present invention. The function of the control loopConsists in determining the duty cycle d of the corresponding power switch in the BBMC1By referencing the inductor current to value iL1refWith its actual value iL1Comparing to obtain the deviation delta i of the inductive currentL1And the deviation is used as the input of a current control inner ring quasi-proportional resonant controller, and the reference value u of the inductance voltage is obtained through the processing of the quasi-proportional resonant controllerL1refThe method specifically comprises the following steps:
uL1ref＝L-1[GLPR(s)ΔiL1(s)] (4)
in the formula: l is-1For the inverse Las transform operator, Δ iL1(s) is the inductor current deviation value Δ iL1Of the Laplace elephant function, GLPR(s) is a transfer function of the quasi-proportional resonant controller, and the functional relation is as follows:
Figure BDA0003649587810000064
in the formula: kLPAnd KLRProportional control gain and resonance control gain, omega, of the current-controlled inner loop quasi-proportional resonance controller, respectivelycTo cut-off frequency, ω0Is the resonance frequency and s is a complex variable.
Obtaining a reference value u of the inductance voltage through the quasi-proportional resonant controllerL1refAnd simultaneously, the capacitor voltage u is respectively detected by the capacitor voltage detection module and the direct current side voltage detection moduleC1And DC side voltage
Figure BDA0003649587810000065
And obtaining the duty ratio d of the corresponding power switch in the BBMC through correlation operation processing1The concrete formula is as follows:
Figure BDA0003649587810000071
in the formula: u. ofC1Is the measured value of the capacitor voltage,
Figure BDA0003649587810000072
the measured value of the BBMC direct-current side voltage is shown.
According to the obtained duty ratio d1And corresponding switching period, and corresponding power switches in the BBMC are controlled, so that output voltage consistent with the reference voltage can be obtained at the output end of the BBMC. Duty ratio d, as exemplified by a first phase Buck-Boost DC/DC converter1Corresponding control power switch tube T1On-time of the power switch tube T2And T1In complementary operating states, i.e. T1When conducting, T2Cutoff and vice versa; by controlling the power switch transistor T1And T1The on-time of the inductor and the capacitor changes according to the set reference value, thereby achieving the purpose of controlling the output voltage.
In order to verify the control effect of the control method, MATLAB is adopted to construct a corresponding simulation model for simulation verification, and meanwhile, comparison simulation analysis is carried out with the traditional composite control strategy based on repeated control. The BBMC main technical indexes are shown in table 1, the quasi-proportional resonance control related control parameters are shown in table 2, and the composite control related control parameters based on repetitive control are shown in table 3.
TABLE 1BBMC Main technical index
Serial number Main technical indexes Numerical value
1 Rated input voltage/V 220
2 Rated input frequency/Hz 50
3 Rated output voltage/V 115
4 Rated output frequency/Hz 400
5 Main circuit inductance parameter/H 4.91×10-5
6 Main circuit capacitance parameter/F 6.15×10-5
7 Rated load/omega 20
TABLE 2 quasi-proportional resonant control related control parameters
Serial number Parameter(s) Numerical value
1 Voltage control outer loop proportional gain KCP 5.59
2 Voltage controlled outer loop resonant gain KCR 800
3 Current controlled inner loop proportional gain KLP 65.34
4 Current control inner loop resonance gain KLR 1200
5 Cut-off frequency omegac 5
6 Resonant frequency omega0 800π
TABLE 3 composite controller-related control parameters based on repetitive control
Figure BDA0003649587810000073
Figure BDA0003649587810000081
Simulation analysis is carried out according to the parameters shown in tables 1-3, the simulation waveform of the output voltage corresponding to the quasi-proportional resonance control obtained according to the steps (1) - (5) is shown in FIG. 6, the simulation waveform corresponding to the output voltage is shown in FIG. 7 on the basis of the composite control strategy of the Buck-Boost matrix converter (electronic measurement and instrument report, 2016,30(06): 931-936), Zhang Xiaoping, etc.), and the related simulation result is shown in Table 4.
Table 4 simulation results corresponding to two control methods
Control method Steady state error voltage/V Degree of harmonic distortion/%) Overshoot/% of
Quasi-proportional resonance control 0 0.28 6.64％
Compound control based on repetitive control 0.4 0.81 23.74％
Based on the simulation waveforms shown in fig. 6-7 and the simulation results shown in table 4, the quasi-proportional resonance control and the conventional composite control based on repetitive control are analyzed as follows:
1) the output voltage corresponding to the quasi-proportional resonance control is basically consistent with the reference voltage thereof in a steady state, and a 0.4V steady-state error exists between the output voltage corresponding to the traditional composite control based on repeated control and the reference voltage thereof;
2) the harmonic distortion degree of the output voltage waveform corresponding to the quasi-proportional resonance control is 0.28%, while the harmonic distortion degree of the output voltage waveform corresponding to the traditional composite control based on the repeated control reaches 0.81%;
3) the overshoot of the output voltage waveform corresponding to the quasi-proportional resonance control is 6.64%, while the overshoot of the output voltage waveform corresponding to the traditional composite control based on the repeated control reaches 23.74%;
4) in actual control, the control parameters to be adjusted in the quasi-proportional resonance control are 4, and are respectively KCP、KCR、KLP、KLRAnd the traditional composite control based on repetitive control needs 6 parameters to be adjusted, which are respectively as follows: qCP、QCI、QLP、QLI、WC、WL。
In summary, for a 400Hz intermediate frequency power supply based on a Buck-Boost matrix converter, compared with the traditional composite control method based on repeated control, the quasi-proportional resonance control method provided by the invention has the characteristics of high steady-state precision, good dynamic performance, good output voltage waveform quality, few adjustable control parameters and the like.

Claims (8)

1. The 400Hz intermediate frequency power supply control method based on the Buck-Boost matrix converter is characterized by comprising the following steps of:
2. superposing the direct current bias of the Buck-Boost matrix converter with a reference output voltage signal to obtain a corresponding capacitor voltage reference value uC1ref；
3. Reference value u of capacitor voltageC1refAnd its actual value uC1Comparing to obtain a capacitor voltage deviation value delta uC1；
(3) The deviation value delta u of the capacitor voltageC1As input of voltage control outer ring quasi-proportional resonant controller, the quasi-proportional resonant controller applies the voltage deviation value Delaut of capacitorC1Processing the signals to obtain a capacitance current reference value iC1refAnd an inductor current reference value iL1ref；
(4) Real-time detection of actual value i of inductor currentL1According to the reference value i of the inductive current obtained in the step (3)L1refCalculating the inductance current deviation value delta iL1And obtaining an inductance voltage reference value u through the processing of a current control inner ring quasi-proportional resonant controllerL1refThen according to the obtained reference value u of the inductor voltageL1refObtaining the duty ratio d of the corresponding power switch in the BBMC1；
(5) According to the duty ratio d obtained in the step (4)1And the set IGBT switching period is used for controlling the corresponding power switch in the BBMC, so that the output voltage consistent with the reference voltage of the BBMC can be obtained at the output end of the BBMC.
2. The Buck-Boost matrix converter-based 400Hz intermediate frequency power supply control method according to claim 1, characterized in that in the step (3), the capacitance current reference value i is obtained by the formula (1)C1ref：
iC1ref＝L-1[GCPR(s)·ΔuC1(s)] (1)
In the formula: l is-1For the inverse Las transform operator, Δ uC1(s) is the deviation value of the capacitor voltage Deltau uC1Of the Laplace elephant function, GCPR(s) is the transfer function of the quasi-proportional resonant controller.
3. The Buck-Boost matrix converter-based 400Hz intermediate frequency power supply control method according to claim 2, characterized in that GCPR(s) is calculated by equation (2):
Figure FDA0003649587800000011
in the formula: kCPAnd KCRProportional control gain and resonant control gain, omega, of a voltage controlled outer quasi-proportional resonant controller, respectivelycTo cut-off frequency, ω0Is the resonance frequency and s is a complex variable.
4. The Buck-Boost matrix converter-based 400Hz intermediate frequency power supply control method according to claim 1, characterized in that in the step (3), the reference value i of the inductor current is obtained by the formula (3)L1ref：
Figure FDA0003649587800000021
In the formula: i.e. i1For BBMC output current measured value, uC1Is the measured value of the capacitor voltage, u \ udcThe measured value of the BBMC direct-current side voltage is shown.
5. The Buck-Boost matrix converter-based 400Hz intermediate frequency power supply control method according to claim 1, characterized in that in the step (4), the reference value u of the inductor voltage is obtained by the formula (4)L1ref：
uL1ref＝L-1[GLPR(s)ΔiL1(s)] (4)
In the formula: l is-1For the inverse Las transform operator, Δ iL1(s) is the inductor current deviation value Δ iL1Of the Laplace elephant function, GLPR(s) is the transfer function of the quasi-proportional resonant controller.
6. The Buck-Boost matrix converter-based 400Hz intermediate frequency power supply control method according to claim 5, characterized in that GLPR(s) is calculated by equation (5):
Figure FDA0003649587800000022
in the formula: kLPAnd KLRProportional control gain and resonance control gain, omega, of the current-controlled inner loop quasi-proportional resonance controller, respectivelycTo cut-off frequency, ω0Is the resonance frequency and s is a complex variable.
7. Buck-Boos-based according to claim 1the 400Hz intermediate frequency power supply control method of the t-matrix converter is characterized in that in the step (4), the duty ratio d is obtained through a formula (6)1：
Figure FDA0003649587800000023
In the formula: u. uC1Is the measured value of the voltage of the capacitor,
Figure FDA0003649587800000024
the measured value of the BBMC direct-current side voltage is shown.
8. 400Hz intermediate frequency power supply control device based on Buck-Boost matrix converter, its characterized in that: the control device comprises a BBMC rectification module, a BBMC inversion module, a network side voltage detection module, a direct current side voltage detection module, a capacitance voltage detection module, an inductive current detection module, an output current detection module, a DSP controller, a rectification IGBT driving module and an inversion IGBT driving module; the input end of the BBMC rectification module is connected with a power grid, the output end of the BBMC rectification module is connected with the input end of a BBMC inversion module, and the output end of the BBMC inversion module is connected with a load; the input end of the network side voltage detection module is connected with a power grid, and the output end of the network side voltage detection module is connected with the DSP controller; the input end of the direct current side voltage detection module is connected with the output end of the BBMC rectification module, and the output end of the direct current side voltage detection module is connected with the input end of the DSP controller; the input ends of the capacitor voltage detection module, the inductive current detection module and the output current detection module are respectively connected with the BBMC inversion module, and the output ends of the capacitor voltage detection module, the inductive current detection module and the output current detection module are respectively connected with the input end of the DSP controller; the input end of the rectifier IGBT driving module is connected with the output end of the DSP controller, and the output end of the rectifier IGBT driving module is connected with the control signal input end of the BBMC rectifying module; the input end of the inverter IGBT driving module is connected with the output end of the DSP controller, and the output end of the inverter IGBT driving module is connected with the control signal input end of the BBMC inverter module.
CN202210546126.3A 2022-05-18 2022-05-18 400Hz intermediate frequency power supply control method and device based on Buck-Boost matrix converter Pending CN114726189A (en)

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Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115313899A (en) * 2022-08-26 2022-11-08 湖南科技大学 Low-ripple adjustable direct-current stabilized power supply and control method thereof
CN116260343A (en) * 2023-04-04 2023-06-13 湖南科技大学 Low-ripple adjustable direct-current stabilized power supply control method based on Buck-Boost inverter circuit

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115313899A (en) * 2022-08-26 2022-11-08 湖南科技大学 Low-ripple adjustable direct-current stabilized power supply and control method thereof
CN116260343A (en) * 2023-04-04 2023-06-13 湖南科技大学 Low-ripple adjustable direct-current stabilized power supply control method based on Buck-Boost inverter circuit

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