CN115441962A - non-Forster broadband matching control method and control device for electroacoustic transducer - Google Patents
non-Forster broadband matching control method and control device for electroacoustic transducer Download PDFInfo
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B13/00—Transmission systems characterised by the medium used for transmission, not provided for in groups H04B3/00 - H04B11/00
- H04B13/02—Transmission systems in which the medium consists of the earth or a large mass of water thereon, e.g. earth telegraphy
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
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- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/0264—Arrangements for coupling to transmission lines
- H04L25/0278—Arrangements for impedance matching
Abstract
The invention provides a non-Forster broadband matching control method and a non-Forster broadband matching control device for an electroacoustic transducer, wherein the non-Forster broadband matching control method comprises the following steps of: and constructing a closed-loop control system, obtaining a reference current feedforward value after an output current reference value passes through a proportional controller, adding a result obtained by subtracting the output current of the power amplifier from the output current reference value after the subtraction result passes through a PR controller to the reference current feedforward value, and inputting the added result into the single-phase full-bridge inverter to obtain the output voltage of the single-phase full-bridge inverter. In a first lumped parameter model of the electroacoustic transducer, a first static equivalent resistance model, an equivalent inductance model and a first vibration system equivalent circuit structure are mutually connected in series between two driving ends of the electroacoustic transducer; the equivalent inductance model is an eddy current impedance model formed by mutually connecting a nonlinear inductance model and a nonlinear resistance model in series.
Description
Technical Field
The invention relates to the technical field of underwater acoustic communication, in particular to a non-Forster broadband matching control method and a non-Forster broadband matching control device for a high-power electroacoustic transducer.
Background
The electroacoustic transducer is a high-power energy conversion device which is widely applied to the technical field of underwater wireless communication and can transmit information in a long distance, and plays a key role in underwater communication, seabed detection and other work. Giant magnetostrictive transducers often together with power amplifiers constitute an electroacoustic transduction system. The electroacoustic transducer mainly comprises an electromagnetic energy storage element and a mechanical vibration system: the energy storage element is responsible for completing the motor conversion under certain physical effect, and the mechanical vibration system is responsible for outputting the converted energy, namely sound energy. The reactance on most mechanical branches of an electroacoustic transducer is small, and the static reactance dominates the reactive response of the system. In order to improve the energy conversion efficiency and the working bandwidth of the high-power electroacoustic transducer, an impedance matching network is required to be added to offset the reactive loss caused by the static reactance of the transducer, so that the resonance bandwidth of the system is expanded.
The traditional impedance matching network is limited by a gain bandwidth theory, can only offset static reactance under a single frequency, and is dependent on the parameter setting accuracy of a matching element, so that the matching precision is low. The Non-Foster Circuit can synthesize negative impedance, break through the limit of gain bandwidth theory, overcome the assumed limitation of passivity, and realize the broadband matching of the high-power electroacoustic transducer. However, the currently used non-foster circuit is only suitable for broadband matching of a tiny power load due to the limited output capability of the transistors and operational amplifiers used by the non-foster circuit, and cannot be suitable for high-power equipment similar to an electroacoustic transducer. Meanwhile, due to the change of the working condition of the electroacoustic transducer, the disturbance of the environment and the non-linear phenomenon of the transducer, a good self-adaptive control system, a good self-adaptive control method and a good self-adaptive control strategy are needed for providing a broadband matching system with high precision and quick response. Therefore, providing a high-precision broadband matching system capable of adapting to a high-power load is very important for improving the energy conversion efficiency and the output quality of the electroacoustic transducer.
Disclosure of Invention
The invention provides a non-Forster broadband matching control method and a non-Forster broadband matching control device for an electroacoustic transducer by utilizing a switch type non-Forster system, aiming at the problems of low energy transmission efficiency and narrow working bandwidth of the traditional electroacoustic transducer.
In order to solve the technical problems, the technical scheme adopted by the invention is as follows: a non-Forster wideband matching control method, the electroacoustic transducer input impedance is inductive, the electroacoustic transducer driving signal is provided by a power amplifier;
the switch type non-Foster system comprises a single-phase full-bridge inverter connected to the driving end of the electroacoustic transducer, a first capacitor and a first inductor; two switching tubes of the single-phase full-bridge inverter are provided with a first common connecting end, and the other two switching tubes are provided with a second common connecting end; two input ends of the single-phase full-bridge inverter are respectively and correspondingly electrically connected with two output ends of the direct-current power supply module; the first common connecting end is electrically connected with one end of the first inductor, and the second common connecting end, one end of the first capacitor and one driving end of the electroacoustic transducer are electrically connected with each other;
the other end of the first inductor, the other end of the first capacitor and one output end of the power amplifier are electrically connected with a first electric connection point, and the other output end of the power amplifier and the other driving end of the electroacoustic transducer are electrically connected with each other;
the non-Forster broadband matching control method comprises the following steps: constructing a closed-loop control system in which a current reference value I is output ac_ref (s) is
Wherein s represents a variable of an s-domain function; v non (s) is the difference between the voltage at the other end of the first capacitor and the voltage at one end of the first capacitor; output current reference value I ac_ref (s) obtaining a reference current feedforward value I after passing through a proportional controller ac_f (s) output current reference value I ac_f (s) subtracting the power amplifier output current I ac (s) the result obtained by the subtraction result after passing through the PR controller and the reference current feedforward value I ac_f (s) adding, wherein the added result is output to a PWM (pulse-width modulation) module as a signal wave, and the output end of the PWM module is electrically connected with the control end of a single-phase full-bridge inverter switching tube;
(U1) the electroacoustic transducer has a first lumped parameter model composed of a first static equivalent resistance, a first equivalent inductance model, and a first vibration system equivalent circuit structure connected in series with each other between two driving ends of the electroacoustic transducer, the first equivalent inductance model being an eddy current impedance model composed of a nonlinear inductance model and a nonlinear resistance model connected in series with each other; the inductance value of the nonlinear inductance model is L em (ω) the resistance value of the nonlinear resistance model is R em (ω)，L em (s) is L em (ω) in the s-domain, and an angular frequency ω =2 π F s ，F s A frequency of an output voltage signal for the power amplifier; or
(U2) the electroacoustic transducer has a second lumped parameter model, the second lumped parameter model is composed of a second static equivalent resistance, a second equivalent inductance model and a second vibration system equivalent circuit structure which are mutually connected in series between two driving ends of the electroacoustic transducer, the second equivalent inductance model is a static inductance model with a constant inductance value Lem, and L is a static inductance model with a constant inductance value Lem em (s) is the expression Lem in the s domain.
The control method can track the nonlinear impedance (namely the nonlinear inductance part in the inductance model) of the transducer, provide more accurate negative reactance value, and is suitable for broadband matching of the electroacoustic transducer because the equivalent reactance can be prevented from being counteracted only under single frequency. In the invention, the modulation degree feedback quantity is calculated by subtracting the value matched with the target and the value obtained by actual measurement, so that closed-loop control can be realized and the control precision is higher. In one case, the first equivalent inductance model is an eddy current impedance model formed by mutually connecting the nonlinear inductance model and the nonlinear resistance model in series, so that the influence of eddy current factors is considered in the static inductance model, and the model is more accurate.
In the above technical solution, the expression of the transfer function of the PR controller in the s domain is:
wherein k is p1 Is the proportionality coefficient, k, of the PR controller r Is an integral coefficient, c is a cut-off frequency, a resonance angular frequency omega 0 ＝2πF s 。
In the above technical solution, the inductance value L of the nonlinear inductance model em (omega), resistance value R of nonlinear resistance model em The expression of (ω) is:
wherein θ (ω) is a first phase angle value, L ex Is a proportionality coefficient, p is a first coefficient, q is a second coefficient, and p is more than 0 and less than 1,0 and less than q and less than 1.
In the technical scheme, an excitation signal is applied to the driving end of the electroacoustic transducer to obtain an electric input admittance curve/electric input impedance curve of the electroacoustic transducer, and a first lumped parameter model of the electroacoustic transducer is obtained according to the electric input admittance curve/electric input impedance curve fitting.
In the invention, the first lumped parameter model is obtained according to the actual electric input admittance curve/electric input impedance curve of the electroacoustic transducer, so that the established model is consistent with the actual transducer performance, the effect of generating negative impedance by the switch type non-Foster system is better, and the equivalent reactance of the transducer is better counteracted.
In the above technical scheme: the first lumped parameter model of the electroacoustic transducer is obtained through the following steps (M1) and (M2):
(M1) fitting according to the electric input admittance curve/electric input impedance curve to obtain a second lumped parameter model of the electroacoustic transducer, wherein the second lumped parameter model of the electroacoustic transducer is formed by a second static equivalent resistance, a static equivalent inductance and a second vibration system equivalent circuit structure which are mutually connected in series between two driving ends of the electroacoustic transducer; the first vibration system equivalent circuit structure and the second vibration system equivalent circuit structure have the same structure; the first vibration system equivalent circuit structure consists of a first vibration system equivalent resistor, a first vibration system equivalent inductor and a first vibration system equivalent capacitor which are connected in parallel; the second vibration system equivalent circuit structure consists of a second vibration system equivalent resistor, a second vibration system equivalent inductor and a second vibration system equivalent capacitor which are connected in parallel; respectively taking the resistance value of the equivalent resistor of the second vibration system, the inductance value of the equivalent inductor of the second vibration system, the capacitance value of the equivalent capacitor of the second vibration system and the resistance value of the equivalent resistor of the second static state as the resistance value of the equivalent resistor of the first vibration system, the inductance value of the equivalent inductor of the first vibration system, the capacitance value of the equivalent capacitor of the first vibration system and the resistance value of the equivalent resistor of the first static state;
(M2) for the first coefficient p, the second coefficient q, and the scaling coefficient L ex And (3) fitting:
constructing a virtual three-dimensional coordinate system oxyz, wherein the x axis, the y axis and the z axis of the virtual three-dimensional coordinate system respectively represent the fitting value of a first coefficient p, the fitting value of a second coefficient q and a proportionality coefficient L ex The fitting value of (a); in an oxyz coordinate system, coordinate points around a first coordinate point are searched by taking the first coordinate point as a starting point, coordinate points closer to the first coordinate point to coordinate points farther from the first coordinate point are taken as a searching sequence, and the result is obtained until a fitting value of a first coefficient p, a fitting value of a second coefficient q and a proportionality coefficient L which correspond to the searched coordinate points are obtained ex The fitting value of the first vibration system equivalent resistance value, the inductance value of the first vibration system equivalent inductance, the capacitance value of the first vibration system equivalent capacitance and the resistance value of the first static equivalent resistance value obtained in the step (M1) are combined to form a model, the fitting error of the admittance curve/impedance curve corresponding to the model relative to the electric input admittance curve/electric input impedance curve of the electroacoustic transducer is not more than the fitting error set value, and the fitting value of the first coefficient p, the fitting value of the second coefficient q and the proportionality coefficient L corresponding to the searched coordinate point are used for calculating the fitting error of the admittance curve/impedance curve corresponding to the electric input admittance curve/electric input impedance curve of the electroacoustic transducer ex Respectively corresponding to the first coefficient p, the second coefficient q, and the scaling coefficient L ex Thereby obtaining a first lumped parameter model of the electroacoustic transducer;
wherein the first coordinate point is a coordinate point composed of p (0), q (0), lem; p (0) =1,q (0) =0, lem is the inductance value of the static equivalent inductance (56').
The applicant found in the study that if p = arbitrary value, q = arbitrary value, L ex If the fitting is started with an arbitrary value, the fitting speed is slow and the convergence time is long. Since the set of parameters p (0) =1, q (0) =0, lem and the result of step (M1) form a model, i.e. a second lumped parameter model, which at least corresponds to the admittance/impedance value of the electrical input admittance/impedance curve of the electroacoustic transducer (10) at the resonance point. That is, p, q, L can be considered ex The coordinate point corresponding to the true value of (3) is relatively close to the first coordinate point constituted by p (0) =1, q (0) =0, lem. In practice, if the search is started from the first coordinate point and the order from the coordinate point closer to the first coordinate point to the coordinate point farther from the first coordinate point is used as the search order, the search efficiency can be greatly improved compared with arbitrarily taking p, q, and L ex The values of (a) start to fit and the search time can be greatly reduced.
In the above technical solution, the first vibration system equivalent circuit structure is composed of a first vibration system equivalent resistor, a first vibration system equivalent inductor, and a first vibration system equivalent capacitor, which are connected in parallel;
and the resistance value of the equivalent resistor of the first vibration system, the inductance value of the equivalent inductor of the first vibration system and the capacitance value of the equivalent capacitor of the first vibration system are obtained by identification according to the electric input admittance curve/electric input impedance curve.
In the above technical solution, the inductance value L of the first inductor s Capacitance value C of the first capacitor s Satisfies the following formula:
wherein L is s 、C s The inductance value of the first inductor and the capacitance value of the first capacitor are respectively; f n The resonance frequency of the LC filter is formed by the first inductor and the first capacitor; f p The switching frequency of a switching tube of the single-phase full-bridge inverter is set; delta i ac_max The rated output current of the power amplifier is 30% of the effective value of the rated output current of the power amplifier.
In the above technical solution, the dc power supply module is connected in parallel with a second capacitor.
The invention also provides a non-foster broadband matching control apparatus for an electroacoustic transducer using a switch-type non-foster system, characterized by comprising a processor configured for executing the steps of the non-foster broadband matching control method described above.
Compared with the prior art, the invention has the following advantages:
1. the impedance broadband matching of the high-power electroacoustic transmitting equipment is realized by using the non-Foster broadband matching control device, and the problem that the broadband matching cannot be realized due to the limitation of a gain-bandwidth theory in the existing matching technology is solved; compared with a common non-Foster device based on an operational amplifier, the power capacity of the device can be improved by more than 1000 times, the power application magnitude of a non-Foster circuit matching network is improved, and the blank of the related technology is filled;
2. by constructing a nonlinear equivalent circuit model of the electroacoustic transducer under the condition of high power, the device and the system can more accurately track the nonlinear impedance of the transducer and provide more accurate negative reactance value, thereby realizing the broadband matching of the high-power electroacoustic transducer;
3. the non-Foster broadband matching control device and the control system thereof can perform self-adaptive error-free adjustment control according to the working condition change of the transducer, external disturbance and nonlinearity existing in the working process of the transducer, realize broadband automatic impedance matching and improve the output efficiency of electroacoustic emission equipment.
4. The control system of the invention uses a Proportional Resonance (PR) controller to complete feedback control adjustment, the steady-state error of the system is small, and the control precision is high; meanwhile, the reliability and the dynamic response speed of the control system are improved by using a feedforward control method.
Drawings
FIG. 1 is a prior art lumped parameter model of an electroacoustic transducer with inductive input impedance and a simplified diagram thereof;
FIG. 2 is a schematic diagram of the electrical connections of the non-Foster broadband matching control device with the power amplifier and the electroacoustic transducer according to the embodiment of the present invention;
FIG. 3 is a schematic illustration of the principle analysis of FIG. 2;
FIG. 4 is a block diagram of the overall structure of a non-Foster broadband matching device with a power amplifier and an electroacoustic transducer according to an embodiment of the present invention;
FIG. 5 is a block diagram of the control system of an embodiment of the present invention;
FIG. 6 is a schematic diagram illustrating the control effect of the non-Foster broadband matching control device according to the embodiment of the present invention;
FIG. 7 is a diagram of the output voltage of the non-Foster broadband matching control device, the output current of the power amplifier, the matching steady state error, and the port characteristics of the non-Foster broadband matching control device after impedance matching according to the present invention;
FIG. 8 is a schematic diagram of the output voltage of the non-Foster wideband matching control device, the output current of the power amplifier, the matching steady-state error, and the port characteristic waveform of the non-Foster wideband matching control device under the condition of linear frequency conversion of the power amplifier.
Detailed Description
In order to make the objects, technical solutions and advantages of the embodiments of the present invention clearer, embodiments of the present invention will be described below by way of specific embodiments with reference to the accompanying drawings, and the technical solutions of the present invention will be clearly and completely described. It is to be understood that the embodiments described are only a few embodiments of the present invention, and not all embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
Example 1
The existing impedance matching network can only complete matching on a single-point frequency generally, so that the broadband matching of the load cannot be realized, and the non-Foster network is used for completing the broadband matching of the load. The existing non-foster network consists of elements with limited output capacity such as operational amplifiers and the like, and can only realize impedance matching of milliwatt-level low-power loads such as a micro antenna and the like. In the application, the provided switch type nonlinear non-Foster system has stronger output capability, can complete impedance matching of a high-power sound source with the equal power of more than 100W of the energy transducer, and can track the output signal frequency of the power amplifier 20, thereby realizing the matching of the static impedance of the electroacoustic transducer in the whole output signal frequency range and expanding the bandwidth of the electroacoustic transducer.
When the input impedance of the electroacoustic transducer is inductive, a commonly used lumped parameter model of the electroacoustic transducer and a simplified diagram thereof are shown in fig. 1.
Without the addition of a matching network, the equivalent inductance of the transducer shares the power provided by the power amplifier 20, resulting in a lower output power of the transducer at multiple frequencies. The scheme of the invention is that under the condition of maintaining the output voltage of the power amplifier 20 unchanged, the equivalent admittance (impedance) of the input position of the transducer is adjusted in a wider frequency range by using a non-Foster matching network, the output power of the transducer is improved, and the broadband output of the transducer is realized.
Aiming at the defects of more matching limitations, narrow application range, low matching precision, low corresponding speed and the like of the existing impedance matching technology, the invention provides a Switch-mode non-Forster broadband matching control method and a control device for widening the bandwidth of a high-power electroacoustic transducer, solves the problems of low energy transmission efficiency and narrow working bandwidth of the electroacoustic transducer, and realizes the broadband matching of the transducer.
Fig. 2 is a schematic diagram of the circuit connection between the non-foster broadband matching control device for the electroacoustic transducer, the power amplifier and the electroacoustic transducer according to the present invention. Wherein the power amplifier provides an excitation signal of variable amplitude and frequency to the electroacoustic transducer. As shown in fig. 4, the non-foster broadband matching control device specifically includes a nonlinear equivalent circuit model building module, a model identification module, a signal detection module, and a control system, wherein the control system further includes a closed-loop control module, a PWM modulation module, and an inverter module. The nonlinear equivalent circuit model building module is used for deducing a nonlinear equivalent circuit model of the high-power transducer by combining a nonlinear impedance model based on the actual complex working condition of the electroacoustic transducer and a multi-field coupling basic theory; the model identification module is based on the nonlinear model of the transducer, and determines the parameters of each element of the nonlinear model by methods such as theoretical calculation, parameter identification and the like according to high-power impedance test experimental data; the input end of the inversion module is connected with a direct-current voltage source, and the output end of the inversion module is connected with a power amplifier and the high-power sound source in series; the signal detection module is used for detecting the voltage and the output current at two ends of the power amplifier and taking the detected voltage and the output current as the control input quantity of the control system; the closed-loop control module in the control system takes the output voltage frequency of the power amplifier obtained by the signal detection module as a controller parameter and the output current of the power amplifier as a reference quantity, and takes the static inductance of the energy converter obtained by the model identification module as a control target quantity to control the output characteristic of the non-foster broadband matching control device to present negative inductance; the input end of the PWM module is connected with the closed-loop control module, the output end of the PWM module is connected with the inverter module, and the PWM module compares a signal wave (namely a modulation signal) obtained through feedback control with a carrier to generate a proper PWM pulse to control the working state of an internal element of the inverter module. The non-foster broadband matching control means is interconnected in series relationship with the power amplifier and the electroacoustic transducer.
As shown in fig. 6, fig. 6 is a schematic diagram illustrating the control effect of the switch-type non-foster broadband matching control device and the control system according to the present invention. Wherein, the solid line (—) represents the output reactance curve of the power amplifier before matching, and it can be seen from the figure that the output reactance of the power amplifier increases rapidly with the increase of the frequency, which severely limits the broadband output of the high-power transducer; the dotted line (· -) represents the power amplifier output reactance curve after the switch type non-foster broadband matching control device based on the high-power electroacoustic transducer linear concentration parameter model is matched, and as can be seen from the figure, although the matching effect of the linear system is obvious, the static inductance is not completely matched due to the influence of nonlinear factors such as the eddy current effect and the like; the dotted line (—) represents the non-foster broadband matching control device port output reactance curve introduced in the electro-acoustic transducer system, and it can be seen that the negative reactance of the system output is not linear with frequency, and the output target of the system is realized. After the open Guan Xing nonlinear non-foster control system is introduced, the output reactance (namely, the reactance between the point P1 and the negative end of the power amplifier 20) curve of the power amplifier is shown as a dotted line (-), and under the condition that the nonlinear static reactance of the transducer is completely eliminated, the output reactance of the power amplifier can be kept close to zero under the condition of high frequency, so that the output efficiency of the transducer is improved, and the output bandwidth of the high-power transducer is expanded.
The specific steps of the non-foster broadband matching control device for carrying out broadband matching on the electroacoustic transducer are as follows:
the invention also provides a specific control method and a strategy of the control system of the switch type non-foster broadband matching control device, wherein the specific control method comprises the following steps: to cancel static reactance of the electroacoustic transducer, the output characteristic of the switch type non-Foster broadband matching control device is negative inductance, and the nonlinear static reactance, i.e. j omega L, obtained by the nonlinear equivalent circuit model of the transducer is used em I.e. (or j ω L) em (ω)) as a target matching amount with the power amplifier output current
And a PR controller is used as a feedback controller to change along with the sinusoidal reference quantity to realize the adjustment without difference and accurately match the static reactance of the electroacoustic transducer. Meanwhile, the dynamic response speed of the control system is enhanced by using feedforward control, and the accurate and quick control of the broadband matching system is realized.
The first lumped parameter model of the electroacoustic transducer 10 is obtained by the following steps (M1) and (M2):
(M1) fitting according to the electrical input admittance curve/electrical input impedance curve to obtain a second lumped parameter model of the electroacoustic transducer 10, where the second lumped parameter model of the electroacoustic transducer 10 is formed by a second static equivalent resistance 57', a static equivalent inductance 56', and a second vibration system equivalent circuit V2 structure, which are mutually connected in series between two driving ends of the electroacoustic transducer 10; the first vibration system equivalent circuit structure V1 and the second vibration system equivalent circuit structure V2 have the same structure; the first vibration system equivalent circuit structure V1 is composed of a first vibration system equivalent resistor 53, a first vibration system equivalent inductor 54, and a first vibration system equivalent capacitor 55, which are connected in parallel; the second vibration system equivalent circuit structure V2 is composed of a second vibration system equivalent resistor 53', a second vibration system equivalent inductor 54', and a second vibration system equivalent capacitor 55' which are connected in parallel; taking the resistance value of the second vibration system equivalent resistor 53', the inductance value of the second vibration system equivalent inductor 54', the capacitance value of the second vibration system equivalent capacitor 55', and the resistance value of the second static equivalent resistor 57' as the resistance value of the first vibration system equivalent resistor 53, the inductance value of the first vibration system equivalent inductor 54, the capacitance value of the first vibration system equivalent capacitor 55, and the resistance value of the first static equivalent resistor 57, respectively;
(M2) for the first coefficient p, the second coefficient q, the scaling coefficient L ex And (3) fitting:
constructing a virtual three-dimensional coordinate system oxyz, wherein the x axis, the y axis and the z axis of the virtual three-dimensional coordinate system respectively represent the fitting value of a first coefficient p, the fitting value of a second coefficient q and a proportionality coefficient L ex The fitting value of (a); in the oxyz coordinate system, starting from the first coordinate pointSearching coordinate points around the first coordinate point at the initial point, taking a coordinate point closer to the first coordinate point to a coordinate point farther from the first coordinate point as a searching sequence, and obtaining a fitting value of a first coefficient p, a fitting value of a second coefficient q and a proportionality coefficient L corresponding to the searched coordinate points ex A model (i.e., a model based on the fitting value of p, the fitting value of q, and the value of L) is formed by the fitting value of (d) and the resistance value of the first vibration system equivalent resistor 53, the inductance value of the first vibration system equivalent inductor 54, the capacitance value of the first vibration system equivalent capacitor 55, and the resistance value of the first static equivalent resistor 57 obtained in step (M1) ex The fitting value of the first coefficient p, the fitting value of the second coefficient q, and the proportionality coefficient L corresponding to the searched coordinate point are used to obtain a nonlinear inductance model 51 and a nonlinear resistance model 52, and then the model formed by combining the resistance value of the first vibration system equivalent resistor 53, the inductance value of the first vibration system equivalent inductor 54, the capacitance value of the first vibration system equivalent capacitor 55, the resistance value of the first static equivalent resistor 57, which are obtained in the step (M1) is combined with the fitting error of the admittance curve/impedance curve corresponding to the electric input admittance curve/electric input impedance curve of the electroacoustic transducer 10, which is not greater than the fitting error set value, and the fitting value of the first coefficient p, the fitting value of the second coefficient q, and the proportionality coefficient L corresponding to the searched coordinate point are used to obtain the fitting value of the first coefficient p, the fitting value of the second coefficient q, and the proportionality coefficient L ex Respectively corresponding to the first coefficient p, the second coefficient q, and the scaling coefficient L ex Thereby obtaining a first lumped parameter model of said electro-acoustic transducer 10;
wherein the first coordinate point is a coordinate point composed of p (0), q (0), lem; p (0) =1,q (0) =0, lem is the inductance value of the static equivalent inductance 56'.
In this application, in step (M1), the resistance value of the first vibration system equivalent resistor 53, the inductance value of the first vibration system equivalent inductor 54, the capacitance value of the first vibration system equivalent capacitor 55, and the resistance value of the first static equivalent resistor 57 are obtained first, that is, each parameter value of the first vibration system equivalent circuit structure in the first centralized parameter model and the resistance value of the first static equivalent resistor are obtained according to each parameter value of the second vibration system equivalent circuit structure in the second centralized parameter model and the resistance value of the first static equivalent resistor. In step (M2), the fitting value of the first coefficient p and the second coefficient are obtainedFitting value of q, proportionality coefficient L ex The fitting values of (a) and (b) are obtained by the step (M2), and the expressions of the nonlinear inductance model 51 and the nonlinear resistance model 52 are obtained. And (5) combining the step (M1) and the step (M2) to obtain a first lumped parameter model.
The specific operation steps when the switch type non-foster broadband matching control device and the control system thereof are used for realizing the broadband matching of the electroacoustic transducer are as follows:
s1: applying an excitation signal to a high-power electroacoustic transducer by using a power amplifier to obtain an electrical input impedance curve of the transducer;
s2: establishing a nonlinear lumped parameter equivalent circuit model according to the structure of the high-power electroacoustic transducer and a multi-field coupling theory, and determining parameter values of elements in the nonlinear model according to an electric input impedance curve by using a fitting algorithm and parameter identification;
the step S2 specifically includes:
s201: as shown in fig. 4, a linear lumped parameter model of a high power electroacoustic transducer is first constructed based on the coupling characteristics of the electroacoustic multi-physical field and the internal energy transfer principle of the transducer.
As shown in FIG. 1, the linear lumped parameter model of the high power electroacoustic transducer is derived according to a motor analogy method, and comprises a driving system equivalent circuit and a vibration system equivalent circuit, wherein the two systems are connected through a transformer with a transformation ratio being an electromechanical conversion coefficient. Wherein the equivalent circuit of the driving system comprises a driving static DC resistor R connected in series e And a static inductance L em The equivalent circuit of the vibration system is composed of a dynamic inductor L m Dynamic capacitor C m Dynamic resistance R 1 And a load impedance Z L Are connected in series. The high-power emission lumped parameter model can be simplified into a driving static direct current resistor R e And a static inductor L em And equivalent dynamic resistance R of vibration system mes Equivalent dynamic inductance L of vibration system mes Equivalent dynamic capacitance C of vibration system mes Forming a five-parameter element equivalent circuit.
S202: and preliminarily calculating the parameter value of the impedance element of the transducer linear lumped parameter model according to the frequency characteristic of the electroacoustic emission resonance point and the corresponding impedance theoretical calculation method thereof.
The method for calculating the frequency characteristic of the electroacoustic emission resonance point and the corresponding impedance theory mainly comprises the following steps:
(1) When the working frequency F s When the frequency is not less than 0Hz, the starting point of the amplitude of the impedance curve is the high-power electroacoustic transmission driving direct-current resistor R e 。
(2) When the high power electroacoustic emission generates series resonance, the resonance frequency
Only the static equivalent inductor 56' (with an inductance of Lem) remains in the circuit, i.e. when F is s ＝f s Corresponding reactance value of ω s Lem。
(3) Resonant frequency when parallel resonance of high power electroacoustic emission occurs
At this time, the theoretical value of the transmitting reactance is zero, and only the first static equivalent resistor 57 (with the resistance value R) is left in the circuit e ) The first vibration system equivalent resistor 53 (resistance R) mes ) When F is s ＝f p Corresponding resistance value of R e +R mes 。
The initial values of the parameters of the elements in the linear lumped parameter model (i.e. the second lumped parameter model) of the electroacoustic transducer can be obtained by a theoretical calculation method as shown in the following table.
TABLE 2 second lumped parameter model element fitting parameter values
S203: considering the eddy current nonlinear effect in the practical operation of the transducer, a nonlinear impedance model is used to replace the linear impedance model part of the elements of step S201. And (3) taking each parameter of the linear lumped parameter impedance model obtained by the preliminary theoretical calculation in the step (S202) as an initial parameter of a nonlinear impedance model identification algorithm, and accurately simulating the variation trend of the eddy current impedance along with the frequency by using a nonlinear impedance model capable of representing the eddy current nonlinear effect of the transducer. Therefore, in the embodiment, the power-exponent model is selected to fit the eddy current impedance model in the high-power electroacoustic emission model, and the expression of the power-exponent model is as follows:
preferably, the fitting algorithm of the nonlinear impedance model parameters may be a least square algorithm, a particle swarm algorithm, or the like, to fit the electrical input impedance curve, but the fitting algorithm is not limited to these two algorithms.
And fitting the parameter values of the model elements according to the electric input impedance curve by using a fitting algorithm, wherein when the fitting error is smaller than a set value, the fitting parameters of the elements are shown in the following table.
TABLE 2 first lumped parameter model element fitting parameter values
S3: as shown in figure 1, a switch type non-Foster broadband matching control device is connected in series between a power amplifier and an electroacoustic transducer, and a negative inductance value-L required to be simulated by an output port of a given inverter is given according to a nonlinear static equivalent inductance value in a nonlinear equivalent circuit model of the high-power electroacoustic transducer em (ω)；
S4: as shown in fig. 5. Fig. 5 is a schematic diagram of the principle analysis of fig. 1. Port output voltage of non-foster broadband matching control device
Voltage across nonlinear inductance model 51
The relationship between them is:
current flowing from non-foster broadband matching control device port
With the current flowing through the nonlinear inductance model 51
The relationship between them is:
control device output impedance due to non-foster broadband matching
Static reactance
Can therefore obtain
Thereby achieving matching of the static impedance of the transducer.
Nonlinear static reactance j omega L according to target matching quantity em (omega), the output current of the power amplifier is taken as a reference quantity, and the characteristic of the output port of the inverter is kept stable and presented as negative inductance, namely-L, through feedback and feedforward control in a control system em (omega), thus realize the accurate, fast impedance broadband matching to the high-power electroacoustic transducer;
further, a control process of the control system of the non-foster broadband matching control device used in the step S4 is as shown in fig. 5, and fig. 5 is a control block diagram of the control system of the non-foster broadband matching control device proposed by the present invention, and the specific control process includes:
s401: collecting output voltage signal of power amplifier by signal detection module
Obtaining the amplitude of the power amplifier output voltage as E m Frequency of F s And collecting output current signal of power amplifier
Output voltage of non-foster broadband matching control device
S402: from-L obtained in step S3 em (ω) and the output voltage of the non-foster broadband matching control device obtained in step S401
The power amplifier output current reference value obtained via the integrator is:
403: reference value of output current of power amplifier
And the actual output current value
After comparison, the comparison difference value is regulated and controlled by a PR controller, and the output result of the PR controller is compared with the feedforward value of the reference current
Adding the signals to obtain a signal wave, generating PWM (pulse width modulation) pulse by the signal wave through an inverter, controlling the working state of the Guan Xingfei Forster matching system, and keeping the characteristics of the output port of the matching network to be always stable as-L em (ω) to achieve matching of the static reactance of the high power electroacoustic transducer. The inverter bridge outputs a voltage of
The carrier wave is a triangular wave.
The output current of the power amplifier is subjected to error-free tracking of a sinusoidal signal by a PR controller through feedback control, the dynamic response speed of the system is improved by a proportional controller through feedforward control, and the transfer functions of the two controllers are as follows:
wherein k is p1 Is the proportionality coefficient, k, of the PR controller r Is the integral coefficient, ω, of the PR controller 0 For resonant angular frequency, omega c Is the cut-off frequency; k is a radical of f Is the scaling factor of the proportional controller. In order to enable the control system to follow the signal change situation in real time, ensure that the steady-state error of the control effect is small, the response speed is high, and realize the accurate matching of the non-Foster broadband matching control device, the resonance angular frequency of the PR controller is selected to be equal to the frequency F of the real-time output signal of the power amplifier acquired by the detection module in the step S401 s To be consistent, i.e. ω 0 ＝2πF s . When the output frequency F of the power amplifier s When varied, preferably ω c Generally taking the value ω 0 *2 percent. When the output frequency F of the power amplifier s When changed, k can also be adjusted r And k p1 And (6) adjusting. For example, the steady state error σ can be requested (e.g., if the steady state error is a predetermined error σ, then the simulation is performed
And
is not greater than the preset error value sigma), k is obtained according to simulation r And k p1 Then the simulation result is verified in the test or simulation, if the simulation result is obtained in the test or simulation
And
is not greater than the steady state error sigma, the k is obtained r And k p1 The parameter value of (2) meets the requirements.
The PR controller is able to follow the sinusoidal signal well. The PR controller adopted by the application can track the working frequency w0 in real time, and the best effect is achieved.
In the present embodiment, k p1 The value range is 250,k r The value is 40,K f May range from 0.7. And the values of the parameters can be adjusted according to the actual situation.
Coefficient of proportionality K pwm Is the transfer function from the PWM module input to the inverter bridge output of the single-phase full-bridge inverter 30. The scheme is that the driving signal of the control switch tube is adjusted by adjusting the waveform of the signal wave, and then the adjustment of the output waveform of the inverter is realized. In this patent, the nonlinear reactance part that the static equivalent inductance corresponds is matched, that is to say, the nonlinear reactance that static inductance and vortex brought has been matched.
I ac_ref (s)×K f ＝I ac_f (s)
[(I ac_ref (s)-I ac (s))×G PR (s)+I ac_f (s)]×K pwm ＝V ac (s)
V non ×s×C s ＝I non
Wherein s represents a variable of an s-domain function; v non (s) is the voltage across the first capacitor; l is em (s) is L em (ω) expression in the s-Domain, I s (s) is the current flowing through the first inductance in the direction from the first common connection (A) to the first electrical connection point (P1), K f For a first proportional gain, the output voltage of the power amplifier, G PR (s) is the expression of the proportional resonant controller in the s domain, K pwm Proportional gain of inverter, L s 、C s The inductance of the first inductor and the capacitance of the first capacitor are respectively. V ac (s) is a single phaseThe AC output voltage of the full-bridge inverter (30).
S404: in order to filter out higher harmonics near the switching frequency, the non-foster broadband matching control device adopts an LC filter according to the principles shown in the following formulas (4) and (5), and the output voltage of the inverter is V after passing through the LC filter non (s)。
Wherein, F n Is the resonant frequency of the LC filter; f p A carrier frequency of PWM; Δ i ac_max 30% of the effective value of the rated current is output for the power amplifier. Selecting a filter inductor L through theoretical calculation and allowance consideration s Is 2mH; filter capacitor C s 10 μ F.
Referring to fig. 7, fig. 7 is a diagram illustrating the output voltage of the non-foster broadband matching control device, the output current of the power amplifier, the matching steady-state error, and the port characteristic of the non-foster broadband matching control device after the impedance matching according to the present invention when the output voltage of the power amplifier has an effective value of 15V and the output frequency is 100 Hz. Since the non-foster broadband matching control device is connected in series between the power amplifier and the electroacoustic transducer, the output current of the power amplifier is the input current of the non-foster broadband matching control device. As can be seen from the results in fig. 7, after the electroacoustic transducer system is connected to the control device, after about one cycle, the system enters a stable state, the phase of the output current of the power amplifier stably leads the output voltage of the non-foster broadband matching control device by about 90 degrees, and the port characteristic of the non-foster broadband matching control device presents a negative inductance; under the action of a control system, a non-Forster broadband matching control device has a steady-state error sigma of no more than 0.08 after the system is stabilized; comparing actual output equivalent inductance value | Z of non-foster broadband matching control device port non I/omega andstatic inductance L to be matched em Theoretical, the relative error e after system stabilization is about% 0.24. The results prove that the control system of the non-foster broadband matching control device can completely meet the requirement that the port characteristic is negative inductance, and the control system has high matching precision and high response speed. In the embodiment shown in FIG. 7, k is the frequency of the power amplifier output at 100Hz p1 The value is 250,k r A first proportional gain K of 40 f Is 0.7.
Where the steady state error σ is defined as:
the actual output equivalent inductance value of the port of the non-foster broadband matching control device and the relative error epsilon of the static inductance theoretical value to be matched are defined as follows:
referring to fig. 8, fig. 8 is a schematic diagram of the output voltage of the non-foster broadband matching control device, the output current of the power amplifier, the matching steady-state error, and the port characteristic waveform of the non-foster broadband matching control device under the condition of the linear frequency conversion of the power amplifier when the effective value of the output voltage of the power amplifier is 15V and the output frequency range is 200Hz-500 Hz. From the results in fig. 8, it can be seen that the control system of the non-foster broadband matching control device can adapt to the change of the matching condition under the variable frequency working condition, when the system works at each frequency, the phase of the output current of the power amplifier can stably lead the output voltage of the non-foster broadband matching control device by about 90 degrees, and the port characteristic of the non-foster broadband matching control device presents negative inductance, thereby meeting the matching requirement. Under the action of the control system, the steady-state error sigma of frequency conversion matching does not exceed 0.05, and the equivalent inductance value | Z of the actual output of the port of the non-foster broadband matching control device is compared non I/omega (i.e. the absolute value of the equivalent inductance between the point P1 and the point P2) and the static state of the desired matchTheoretical value of inductance (the theoretical value of static inductance to be matched is based on L corresponding to the output frequency of the power amplifier em The expression of (omega) is calculated), the relative error epsilon after the system is stabilized does not exceed 2.3 percent. The results show that the control system of the non-foster broadband matching control device can completely meet the requirement that the port characteristic of the device is negative inductance under the condition of linear frequency conversion, can accurately and quickly control and respond in real time according to the change condition of the working condition of the system, and achieves the output target.
In the embodiment shown in fig. 8, when the output frequencies of the power amplifiers are 200Hz, 300Hz, 400Hz, and 500Hz, it is obvious that the inductance values of the nonlinear inductance model 51 are different, so that the static inductances (i.e., the inductance values of the nonlinear inductance model 51) to be matched are different.
In the embodiment shown in fig. 8: k is a radical of p1 The value is 250,k r Value of 40, proportional coefficient K of proportional controller f Is 0.7.
Example 2
This embodiment 2 differs from embodiment 1 in that the electroacoustic transducer is characterized using a second lumped parameter model (i.e., the model in fig. 1).
The electroacoustic transducer 10 is provided with a second lumped parameter model which is composed of a second static equivalent resistance 57', a second equivalent inductance model 56' and a second vibration system equivalent circuit structure V2 which are mutually connected in series between two driving ends of the electroacoustic transducer (10). The inductance value of the second equivalent inductance model 56' is a constant inductance value Lem, L em (s) is the expression Lem in the s domain. I.e. L in example 1 em (ω) is replaced by Lem. Other contents can be referred to embodiment 1.
It should be noted that, in this specification, each embodiment is described in a progressive manner, and each embodiment focuses on differences from other embodiments, and portions that are the same as and similar to each other in each embodiment may be referred to.
The embodiments of the present invention have been described in detail, but the description is only for the preferred embodiments of the present invention and should not be construed as limiting the scope of the present invention. All equivalent changes and modifications made within the scope of the present invention should be covered by the present patent. After reading this disclosure, modifications of various equivalent forms of the present invention by those skilled in the art will fall within the scope of the present application, as defined in the appended claims. The embodiments and features of the embodiments of the invention/inventions may be combined with each other without conflict.
Claims (9)
1. A non-foster broadband matching control method for an electroacoustic transducer, the electroacoustic transducer (10) input impedance being inductive, an electroacoustic transducer (10) drive signal being provided by a power amplifier (20);
the switching type non-Foster system is characterized by comprising a single-phase full-bridge inverter (30) connected to the driving end of the electroacoustic transducer (10), a first capacitor (1) and a first inductor (2); two switching tubes of the single-phase full-bridge inverter (30) are provided with a first common connection end (A), and the other two switching tubes are provided with a second common connection end (B); two input ends of the single-phase full-bridge inverter (30) are respectively and correspondingly electrically connected with two output ends of the direct-current power supply module (4); the first common connecting end (A) is electrically connected with one end of the first inductor (2), and the second common connecting end (B), one end of the first capacitor (1) and one driving end of the electroacoustic transducer (10) are electrically connected with each other;
the other end of the first inductor (2), the other end of the first capacitor (1) and one output end of the power amplifier (20) are electrically connected with a first electric connection point (P1), and the other output end of the power amplifier (20) and the other driving end of the electroacoustic transducer (10) are electrically connected with each other;
the non-Forster broadband matching control method comprises the following steps: constructing a closed loop control system wherein
Output current reference value I ac_ref (s) is
Wherein s represents a variable of an s-domain function; v non (s) is an expression of the difference between the voltage at the other end of the first capacitor (1) and the voltage at one end of the first capacitor (1) obtained by measurement in the s domain;
output current reference value I ac_ref (s) obtaining a reference current feedforward value I after passing through a proportional controller ac_f (s)；
Output current reference value I ac_ref (s) subtracting the power amplifier output current measurement I ac (s) the result obtained by the subtraction result after passing through the PR controller and the reference current feedforward value I ac_f (s) adding, wherein the added result is output to a PWM (pulse-Width modulation) module as a signal wave, and the output end of the PWM module is electrically connected with the control end of a switching tube of the single-phase full-bridge inverter (30);
(U1) the electroacoustic transducer (10) has a first lumped parameter model consisting of a first static equivalent resistance (57), a first equivalent inductance model (56) and a first vibration system equivalent circuit structure (V1) connected in series with each other between the two drive ends of the electroacoustic transducer (10), the first equivalent inductance model (56) being an eddy current impedance model consisting of a nonlinear inductance model (51) and a nonlinear resistance model (52) connected in series with each other; the inductance value of the nonlinear inductance model (51) is L em (ω) the resistance value of the nonlinear resistance model (52) is R em (ω)，L em (s) is L em (ω) an expression in the s domain, where the angular frequency ω is expressed as ω =2 π F s ，F s A frequency of an output voltage signal for the power amplifier (20); or
(U2) the electroacoustic transducer (10) has a second lumped parameter model consisting of a second static equivalent resistance (57 '), a second equivalent inductance model (56 '), and a second vibration system equivalent circuit structure (V2) connected in series with each other between the two drive ends of the electroacoustic transducer (10), the second equivalent inductance model (56 ') being a static inductance model of constant inductance value Lem, L em (s) is the expression of Lem in the s domain.
2. The non-foster broadband matching control method of claim 1 wherein: the expression of the PR controller transfer function in the s-domain is:
wherein k is p1 、k r Proportional coefficient, integral coefficient, omega, of the PR controller c 、ω 0 Cut-off frequency, resonance frequency, omega, respectively, of the PR controller 0 ＝2πF s 。
3. The non-foster broadband matching control method of claim 1 wherein: the inductance value Lem (ω) of the nonlinear inductance model (51) and the resistance value Rem (ω) of the nonlinear resistance model (52) are expressed as follows:
wherein θ (ω) is a first phase angle value, L ex Is a proportionality coefficient, p is a first coefficient, q is a second coefficient, and p is more than 0 and less than 1,0 and less than q and less than 1.
4. The non-foster broadband matching control method of claim 3 wherein: an excitation signal is applied to the driving end of the electroacoustic transducer (10), an electric input admittance curve/electric input impedance curve of the electroacoustic transducer (10) is obtained, and a first lumped parameter model of the electroacoustic transducer (10) is obtained according to the electric input admittance curve/electric input impedance curve fitting.
5. The non-Forster wideband matching control method of claim 4, wherein: the first lumped parameter model of the electroacoustic transducer (10) is obtained by the following steps (M1) and (M2):
(M1) fitting according to the electric input admittance curve/electric input impedance curve to obtain a second lumped parameter model of the electroacoustic transducer (10), wherein the first vibration system equivalent circuit structure (V1) and the second vibration system equivalent circuit structure (V2) have the same structure; the first vibration system equivalent circuit structure (V1) is composed of a first vibration system equivalent resistor (53), a first vibration system equivalent inductor (54) and a first vibration system equivalent capacitor (55) which are connected in parallel; the second vibration system equivalent circuit structure (V2) is composed of a second vibration system equivalent resistor (53 '), a second vibration system equivalent inductor (54 ') and a second vibration system equivalent capacitor (55 ') which are connected in parallel; respectively taking the resistance value of the second vibration system equivalent resistor (53 '), the inductance value of the second vibration system equivalent inductor (54'), the capacitance value of the second vibration system equivalent capacitor (55 '), and the resistance value of the second static equivalent resistor (57') as the resistance value of the first vibration system equivalent resistor (53), the inductance value of the first vibration system equivalent inductor (54), the capacitance value of the first vibration system equivalent capacitor (55), and the resistance value of the first static equivalent resistor (57);
(M2) for the first coefficient p, the second coefficient q, the scaling coefficient L ex And (3) fitting:
constructing a virtual three-dimensional coordinate system oxyz, wherein the x axis, the y axis and the z axis of the virtual three-dimensional coordinate system respectively represent the fitting value of a first coefficient p, the fitting value of a second coefficient q and a proportionality coefficient L ex The fitting value of (a); in an oxyz coordinate system, coordinate points around a first coordinate point are searched by taking the first coordinate point as a starting point, coordinate points closer to the first coordinate point to coordinate points farther from the first coordinate point are taken as a searching sequence, and the result is obtained until a fitting value of a first coefficient p, a fitting value of a second coefficient q and a proportionality coefficient L which correspond to the searched coordinate points are obtained ex The fitting error of the admittance curve/impedance curve corresponding to the model consisting of the fitting value of (1), the resistance value of the first vibration system equivalent resistor (53), the inductance value of the first vibration system equivalent inductor (54), the capacitance value of the first vibration system equivalent capacitor (55) and the resistance value of the first static equivalent resistor (57) relative to the electric input admittance curve/electric input impedance curve of the electroacoustic transducer (10) is not more than the fitting error set value, and the fitting value of the first coefficient p, the fitting value of the second coefficient q and the proportionality coefficient L corresponding to the searched coordinate points are used ex Corresponding to a value of a first coefficient p and a value of a second coefficient qValue, proportionality coefficient L ex Thereby obtaining a first lumped parameter model of the electroacoustic transducer (10);
wherein the first coordinate point is a coordinate point consisting of p (0), q (0), lem; p (0) =1,q (0) =0, lem is the inductance value of the static equivalent inductance (56').
6. The non-Forster broadband matching control method of any one of claims 1-5, wherein: the first vibration system equivalent circuit structure (V1) is composed of a first vibration system equivalent resistor (53), a first vibration system equivalent inductor (54) and a first vibration system equivalent capacitor (55) which are connected in parallel;
and the resistance value of the first vibration system equivalent resistor (53), the inductance value of the first vibration system equivalent inductor (54) and the capacitance value of the first vibration system equivalent capacitor (55) are obtained by identification according to the electric input admittance curve/electric input impedance curve.
7. The non-Forster broadband matching control method of any one of claims 1-5, wherein: inductance L of the first inductor (2) s A capacitance value C of the first capacitor (1) s Satisfies the following formula:
wherein L is s 、C s The inductance value of the first inductor and the capacitance value of the first capacitor are respectively; f n The resonance frequency of an LC filter formed by a first inductor (2) and a first capacitor (1); f p The switching frequency of a switching tube of the single-phase full-bridge inverter (30); Δ i ac_max The rated output current of the power amplifier (20) is 30% of the rated output current effective value.
8. The non-Forster wideband matching control method of any of claims 1-6, characterized in that: and the direct current power supply module (4) is connected with a second capacitor (3) in parallel.
9. A non-foster broadband matching control apparatus for an electroacoustic transducer, comprising a processor configured to perform the steps of the non-foster broadband matching control method of any one of claims 1-8.
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