CN115276503A - System for eliminating output ripple of small-capacitance frequency converter with permanent magnet synchronous motor load and control method - Google Patents
System for eliminating output ripple of small-capacitance frequency converter with permanent magnet synchronous motor load and control method Download PDFInfo
- Publication number
- CN115276503A CN115276503A CN202210879351.9A CN202210879351A CN115276503A CN 115276503 A CN115276503 A CN 115276503A CN 202210879351 A CN202210879351 A CN 202210879351A CN 115276503 A CN115276503 A CN 115276503A
- Authority
- CN
- China
- Prior art keywords
- small
- capacitor
- permanent magnet
- magnet synchronous
- synchronous motor
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
- 230000001360 synchronised effect Effects 0.000 title claims abstract description 48
- 238000000034 method Methods 0.000 title claims abstract description 28
- 239000003990 capacitor Substances 0.000 claims abstract description 66
- 238000004146 energy storage Methods 0.000 claims description 53
- 239000003985 ceramic capacitor Substances 0.000 claims description 23
- 239000010409 thin film Substances 0.000 claims description 13
- 239000010408 film Substances 0.000 claims description 10
- 238000010521 absorption reaction Methods 0.000 claims description 5
- 238000004590 computer program Methods 0.000 claims description 5
- 238000011217 control strategy Methods 0.000 claims description 3
- 238000004804 winding Methods 0.000 claims description 3
- 230000006870 function Effects 0.000 claims 3
- XOFYZVNMUHMLCC-ZPOLXVRWSA-N prednisone Chemical compound O=C1C=C[C@]2(C)[C@H]3C(=O)C[C@](C)([C@@](CC4)(O)C(=O)CO)[C@@H]4[C@@H]3CCC2=C1 XOFYZVNMUHMLCC-ZPOLXVRWSA-N 0.000 claims 1
- 238000005070 sampling Methods 0.000 abstract description 4
- 230000002829 reductive effect Effects 0.000 description 6
- 238000010586 diagram Methods 0.000 description 3
- 230000000694 effects Effects 0.000 description 3
- 238000012937 correction Methods 0.000 description 2
- 230000008030 elimination Effects 0.000 description 2
- 238000003379 elimination reaction Methods 0.000 description 2
- 238000005516 engineering process Methods 0.000 description 2
- 238000011160 research Methods 0.000 description 2
- 238000004088 simulation Methods 0.000 description 2
- NTSBMKIZRSBFTA-AIDOXSFESA-N Digoxigenin bisdigitoxoside Chemical compound C1[C@H](O)[C@H](O)[C@@H](C)O[C@H]1O[C@@H]1[C@@H](C)O[C@@H](O[C@@H]2C[C@@H]3[C@]([C@@H]4[C@H]([C@]5(CC[C@@H]([C@@]5(C)[C@H](O)C4)C=4COC(=O)C=4)O)CC3)(C)CC2)C[C@@H]1O NTSBMKIZRSBFTA-AIDOXSFESA-N 0.000 description 1
- 230000009286 beneficial effect Effects 0.000 description 1
- 238000013016 damping Methods 0.000 description 1
- 238000013461 design Methods 0.000 description 1
- 238000011161 development Methods 0.000 description 1
- 230000009977 dual effect Effects 0.000 description 1
- 230000002401 inhibitory effect Effects 0.000 description 1
- 230000000670 limiting effect Effects 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 239000004576 sand Substances 0.000 description 1
- 239000004065 semiconductor Substances 0.000 description 1
- 230000003068 static effect Effects 0.000 description 1
Images
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
- H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
- H02P25/022—Synchronous motors
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4233—Arrangements for improving power factor of AC input using a bridge converter comprising active switches
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
- H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
- H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
- H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M5/4585—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only having a rectifier with controlled elements
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
- H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
- H02P27/085—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation wherein the PWM mode is adapted on the running conditions of the motor, e.g. the switching frequency
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P2207/00—Indexing scheme relating to controlling arrangements characterised by the type of motor
- H02P2207/05—Synchronous machines, e.g. with permanent magnets or DC excitation
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Rectifiers (AREA)
Abstract
The invention discloses a small-capacitance frequency converter output ripple wave eliminating system with a permanent magnet synchronous motor load and a control method thereof. The control method is that the real-time impedance control function value is automatically calculated by sampling the input voltage, the input current and the bus voltage, and a capacitance multiplier is realized in a current mode, so that the two-port split virtual capacitor is equivalent to a large capacitor capable of balancing instantaneous input power and output power. The invention improves the power density and the service life of the system, ensures the good working performance of the motor, and has simple and feasible realization method, strong applicability and easy digital realization.
Description
Technical Field
The invention relates to a power electronic control technology, in particular to a system and a control method for eliminating output ripples of a small-capacitance frequency converter with a permanent magnet synchronous motor load.
Background
In recent years, with the rapid development of power electronics technology, permanent Magnet Synchronous Motors (PMSM) are widely used in various fields such as household appliances, electric vehicles, numerical control machines and the like due to the advantages of high efficiency, easy control, high power density and the like. At present, a traditional variable frequency driving system of a permanent magnet synchronous motor mainly comprises a rectifier, a power factor correction circuit, an electrolytic capacitor, an inverter and a PMSM. In the case of single-phase ac power supply, the dc bus voltage will fluctuate greatly due to the difference in input and output power, and a large-capacity energy storage capacitor is usually used to eliminate output ripples. The existing electrolytic capacitor is the only energy storage capacitor with enough energy density to adapt to high-power application, but the electrolytic capacitor has the advantages of large volume, high cost, short service life, easy leakage at high temperature, and limited service life of the whole electrolytic capacitor, and seriously influences the miniaturization and reliability of the system.
In order to effectively reduce the volume of the system and improve the reliability of the system, a small-capacity thin film capacitor/ceramic capacitor with long service life is adopted to replace a large-capacity electrolytic capacitor. However, the film/ceramic capacitor is generally only dozens of microfarads at most, and when the small capacitor absorbs the pulsating power of the power grid, the direct-current bus voltage inevitably has large output ripples. The voltage fluctuation of double grid frequency of the direct current bus voltage can directly influence the torque and the rotating speed of the permanent magnet synchronous motor, and further the running performance of the motor is reduced. Therefore, how to make a small-capacitance frequency converter with a motor load simultaneously take high power density and motor output performance into consideration becomes a research hotspot, and has great research value.
Disclosure of Invention
The invention aims to provide a system for eliminating output ripples of a small-capacitance frequency converter with a permanent magnet synchronous motor load and a control method.
The technical solution for realizing the purpose of the invention is as follows: a small-capacitance frequency converter output ripple wave eliminating system with a permanent magnet synchronous motor load comprises a single-phase alternating current input, a single-phase uncontrolled diode rectifier, a PFC converter, a two-port split virtual capacitor, an inverter and a permanent magnet synchronous motor, wherein the input end of an uncontrolled rectifier circuit unit is connected with the single-phase alternating current input, the anode of the output end of the uncontrolled rectifier circuit is connected with the anode of the input end of the PFC converter, and the cathode of the output end of the uncontrolled rectifier circuit is connected with the cathode of the input end of the PFC converter; the positive electrode of the output end of the PFC converter is connected with the positive electrode of the input end of the two-port split virtual capacitor, and the negative electrode of the output end of the PFC converter is connected with the negative electrode of the input end of the two-port split virtual capacitor; the positive electrode of the output end of the two-port split virtual capacitor is connected with the positive electrode of the direct current bus, and the negative electrode of the output end of the two-port split virtual capacitor is connected with the negative electrode of the direct current bus; the positive pole of the input end of the inverter is connected with the positive pole of the direct current bus, the negative pole of the input end of the inverter is connected with the negative pole of the direct current bus, and the output end of the inverter is connected with the three-phase winding of the permanent magnet synchronous motor;
the two-port split virtual capacitor is formed by connecting a small-capacity film/ceramic capacitor and an H-bridge power converter consisting of an inductor, an energy storage capacitor and first to fourth power switch tubes in parallel, wherein the positive output end of the small-capacity film/ceramic capacitor is connected with the cathode of a main power diode in a PFC converter and one end of the inductor, the other end of the inductor is connected with the source electrode of the first power switch tube and the drain electrode of the second power switch tube, the negative output end of the small-capacity film/ceramic capacitor is connected with the source electrode of the third power switch tube and the drain electrode of the fourth power switch tube, the drain electrode of the first power switch tube, the drain electrode of the third power switch tube and one end of the energy storage capacitor are connected, and the source electrode of the second power switch tube, the source electrode of the fourth power switch tube and the other end of the energy storage capacitor are connected.
Furthermore, the single-phase uncontrolled diode rectifying circuit is composed of a first rectifying diode, a second rectifying diode and a fourth rectifying diode, wherein the first rectifying diode and the third rectifying diode are connected in series to form a bridge arm, and the second rectifying diode and the fourth rectifying diode form another bridge arm.
Furthermore, the PFC converter comprises a Boost PFC circuit consisting of a Boost inductor, a main power diode and a main power switch tube, wherein the positive output end of the direct current side of the single-phase uncontrolled diode rectifying circuit is connected with one end of the Boost inductor, the other end of the Boost inductor is simultaneously connected with the drain electrode of the main power switch tube and the anode of the main power diode, the source electrode of the main power switch tube is connected with the negative output end of the direct current side of the single-phase uncontrolled diode rectifying circuit and the negative output end of the small-capacity thin film/ceramic capacitor, and the cathode of the main power diode is connected with the positive output end of the small-capacity thin film/ceramic capacitor.
Furthermore, the value of the energy storage capacitor and the energy storage capacitor CsThe voltage variation range is related to the type of the adopted power converter, and the specific relationship is as follows:
wherein Vm、ImAmplitude of AC input voltage and current, omega =2 pi fline，flineFor single-phase input frequency, V, of AC mainsc_maxAnd Vc_minAre respectively an energy storage capacitor CsThe maximum and minimum values of the instantaneous voltage.
Furthermore, the three-phase inverter circuit is composed of first to sixth inverter switch tubes, wherein a drain electrode of the first inverter switch tube, a drain electrode of the third inverter switch tube, and a drain electrode of the fifth inverter switch tube are connected with a positive output end of the small-capacity thin film/ceramic capacitor, a source electrode of the second inverter switch tube, a source electrode of the fourth inverter switch tube, and a source electrode of the sixth inverter switch tube are connected with a negative output end of the small-capacity thin film/ceramic capacitor, a source electrode of the first inverter switch tube is simultaneously connected with a drain electrode of the second inverter switch tube and one end of the permanent magnet synchronous motor load, a source electrode of the third inverter switch tube is simultaneously connected with a drain electrode of the fourth inverter switch tube and one end of the permanent magnet synchronous motor load, and a source electrode of the fifth inverter switch tube is simultaneously connected with a drain electrode of the sixth inverter switch tube and one end of the permanent magnet synchronous motor load.
The method for eliminating and controlling the output ripple of the small-capacitance frequency converter with the permanent magnet synchronous motor load is based on the small-capacitance frequency converter output ripple eliminating and controlling system with the permanent magnet synchronous motor load, so that the small-capacitance frequency converter output ripple eliminating and controlling with the permanent magnet synchronous motor load is realized, and the method comprises the following steps of:
the method comprises the following steps: detecting the whole circuit state of the two-port split virtual capacitor, and calculating the total energy storage capacitance value C of the direct current bus required by the ripple absorption according to the circuit state and the expected voltage ripple presettingallThe specific expression is as follows:
wherein, Pin(t) is input instantaneous power, PoFor output power, ω =2 π fline，flineFor single-phase input frequency of AC network, integral interval [ Tline/8,3Tline/8]Charging time for the total energy storage capacitor of the DC bus, CallIs the total energy storage capacitance value of the DC bus, Δ E is the energy required to be stored by the total energy storage capacitance of the DC bus, Vdc_maxAnd Vdc_minRespectively, a maximum voltage value charged and a minimum voltage value discharged, Vdc_aveIs the average voltage, Δ V, across the total energy storage capacitor of the DC busdc＝Vdc_max-Vdc_minThe ripple voltage on the total energy storage capacitor of the direct current bus;
comprehensively obtaining the total energy storage capacitance value of the direct current bus:
wherein, Vm、ImThe amplitudes of the alternating input voltage and the alternating input current are respectively;
step two: based on a current control current source method, the equivalent power impedance of the two-port split virtual capacitor is solved in an s domain, and a specific expression is as follows:
wherein, CdcThe capacitance value of the small-capacity passive capacitor is N, the impedance control function value is N, and the frequency domain is s; the two-port split type virtual capacitor can be equivalent to CdcAnd equivalent virtual capacitance N.CdcParallel connection, namely:
Call＝(N+1)Cdc
step three: and (3) calculating a real-time impedance control function value N by combining the first step and the second step, wherein a specific expression is as follows:
step four: the method adopts a voltage and current double closed-loop control strategy to split the two ports into a virtual capacitor equivalent capacitance value and an energy storage capacitor CsThe voltage at two ends is controlled, which specifically comprises the following steps:
calculating the error between the average voltage of the small energy-storage capacitor and the given reference value of the average voltage of the small energy-storage capacitor, and comparing the error with i after passing through a voltage compensator*After addition, the desired split current i is generated2Wherein i is*Controlling the function value N and the flowing current i for the small-capacity passive capacitor in real time1The product of (a); calculating a split current i2Actual value and split current i2After passing through the current compensator, the error generates a PWM square wave modulation signal to control a switching tube of an H bridge in the two-port split virtual capacitor in real time, thereby achieving the purpose of eliminating output ripples.
When the processor executes the computer program, based on the small-capacitance frequency converter output ripple wave elimination control method with the permanent magnet synchronous motor load, the small-capacitance frequency converter output ripple wave elimination control with the permanent magnet synchronous motor load is realized.
A computer-readable storage medium, on which a computer program is stored, which, when executed by a processor, implements a small-capacitance frequency converter output ripple cancellation control with a permanent magnet synchronous motor load based on the small-capacitance frequency converter output ripple cancellation control method with a permanent magnet synchronous motor load.
Compared with the prior art, the invention has the remarkable advantages that: 1) The method has the advantages that the method can effectively restrain the voltage fluctuation of the bus, meanwhile, the characteristics of high power factor, high efficiency, long service life and excellent driving performance are also met, and the problems of serious fluctuation of the direct-current bus voltage and poor running performance of the motor in the existing small-capacitance frequency converter scheme with the permanent magnet synchronous motor load can be effectively solved. 2) The two-port split virtual capacitor and the control method thereof replace the original high-capacity electrolytic capacitor to absorb ripple power, effectively reduce the volume of the required energy storage element, avoid the use of the electrolytic capacitor, improve the power density of the system, simultaneously consider good operation performance of the motor, prolong the service life of the whole system and increase the stability of the system. 3) The two-port split type virtual capacitor and the control method thereof are mutually independent from motor control, do not need to change the original connection mode of a load, have simple structure, low device cost and simple and feasible control and are beneficial to digital design.
Drawings
FIG. 1 is a block diagram of the general structure of the output ripple cancellation system of a small-capacitance frequency converter with a permanent magnet synchronous motor load according to the present invention;
FIG. 2 is a graph of the voltage, current and power waveforms of the power converter in the two-port split virtual capacitor of the present invention;
FIG. 3 is a block diagram of the voltage-current dual closed loop control of the power converter in the two-port split virtual capacitor of the present invention;
FIG. 4 is a circuit diagram of the output ripple cancellation of a small-capacitance frequency converter with a PMSM load according to an embodiment of the present invention;
fig. 5 is a comparison graph of simulation effects before and after the small-capacitance frequency converter with the permanent magnet synchronous motor load according to the embodiment of the invention uses a two-port split virtual capacitor.
Detailed Description
In order to make the objects, technical solutions and advantages of the present application more apparent, the present application is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the present application and are not intended to limit the present application.
Referring to the attached figure 1, the small-capacitance frequency converter output ripple wave eliminating system with the permanent magnet synchronous motor load is composed of a single-phase alternating current input, a single-phase uncontrolled diode rectifying circuit 1, a PFC converter 2, a two-port split type virtual capacitor 3, an inverter 4 and a permanent magnet synchronous motor load 5 which are sequentially connected in series. The input end of the single-phase uncontrolled diode rectifying circuit 1 is connected with a single-phase alternating current input, the positive pole of the output end of the single-phase uncontrolled diode rectifying circuit 1 is connected with the positive pole of the input end of the PFC converter 2, and the negative pole of the output end of the single-phase uncontrolled diode rectifying circuit 1 is connected with the negative pole of the input end of the PFC converter 2; the positive electrode of the output end of the PFC converter 2 is connected with the positive electrode of the input end of the two-port split type virtual capacitor 3, and the negative electrode of the output end of the PFC converter 2 is connected with the negative electrode of the input end of the two-port split type virtual capacitor 3; the positive electrode of the output end of the two-port split virtual capacitor 3 is connected with the positive electrode of the direct current bus, and the negative electrode of the output end of the two-port split virtual capacitor 3 is connected with the negative electrode of the direct current bus; the positive pole of the input end of the inverter 4 is connected with the positive pole of the direct current bus, the negative pole of the input end of the inverter 4 is connected with the negative pole of the direct current bus, and the output end of the inverter 4 is connected with the three-phase winding 5 of the permanent magnet synchronous motor.
Referring to fig. 4, the single-phase uncontrolled diode rectifier circuit 1 consists of a rectifier diode D1-D4Is composed of a first rectifying diode D1And a third rectifying diode D3Serially connected to form a bridge arm and a second rectifier diode D2And a fourth rectifying diode D4Forming another bridge arm.
The PFC circuit 2 consists of a boost inductor LbMain power diode DbMain power switch tube SbA boost PFC circuit is formed to realize the function of power factor correction, wherein the positive output end of the direct current side of the single-phase uncontrolled diode rectifying circuit 1 and the boost inductor LbIs connected to a boost inductor LbThe other end of the primary power switch tube S is connected with the primary power switch tube S simultaneouslybDrain electrode, main power twoPolar tube DbIs connected with the anode of the main power switch tube SbThe source electrode of the single-phase uncontrolled diode rectifying circuit 1, the direct current side negative output end of the single-phase uncontrolled diode rectifying circuit and the small-capacity film/ceramic capacitor CdcNegative output terminal connected, main power diode DbCathode and small-capacity film/ceramic capacitor CdcThe positive output end is connected.
The two-port split virtual capacitor 3 is realized by a power semiconductor switch and a passive element and is composed of a small-capacity film/ceramic capacitor CdcAnd by an inductance L2And an energy storage capacitor CsAnd a power switch tube S1-S4The H-bridge power converters are connected in parallel, wherein the small-capacity film/ceramic capacitor CdcPositive output terminal and main power diode DbCathode and inductor L of2Is connected to one end of an inductor L2And the other end of the first power switch tube S1Source electrode of the first power switch tube S2Is connected with the drain electrode of the thin film/ceramic capacitor CdcNegative output end and third power switch tube S3Source electrode of, fourth power switch tube S4Is connected with the drain electrode of the first power switch tube S1Drain electrode of the third power switch tube S3Drain electrode of (1), and energy storage capacitor CsIs connected with one end of the second power switch tube S2Source electrode of, fourth power switch tube S4Source electrode and energy storage capacitor CsThe other ends of the two are connected. CsValue and energy storage capacitor CsThe voltage variation range is related to the kind of power converter used.
The three-phase inverter circuit 4 is composed of an inverter switch tube Si1-Si6Is composed of a first inverter switch tube Si1Drain electrode of (1), third inverter switching tube Si3Drain electrode of (1), fifth inverter switching tube Si5Drain electrode and small-capacity thin film/ceramic capacitor CdcThe positive output end is connected with the second inverter switch tube Si2Source electrode, fourth inverter switching tubeSi4Source electrode of (1), sixth inverter switching tube Si6Source electrode and small-capacity thin film/ceramic capacitor CdcNegative output end connected to the first inverter switching tube Si1Is connected with the second inverter switch tube Si2Drain electrode of (1), one end of a permanent magnet synchronous motor load 5, and a third inverter switching tube Si3The source electrode of the first inverter is simultaneously connected with the fourth inverter switching tube Si4Drain electrode of (1), one end of a permanent magnet synchronous motor load 5, and a fifth inverter switching tube Si5Source electrodes of the first and second inverter switching tubes S are connected with the sixth inverter switching tube S simultaneouslyi6And one end of the permanent magnet synchronous motor load 5.
The controller 6 of the two-port split virtual capacitor comprises a sampling circuit, and is used for sampling input voltage and input current from an alternating current power grid and voltage at two ends of a direct current bus; and a real-time impedance control function value N calculating unit for realizing a capacitance multiplier in a current mode to make the two-port split virtual capacitor equivalent to a large capacitor (1 + N) C capable of balancing instantaneous input power and output powerdc. The method comprises the following specific steps:
the method comprises the following steps: the sampling circuit in the two-port split virtual capacitor controller detects the current overall circuit state, and the total energy storage capacitance value C of the direct current bus required by ripple absorption is calculated according to the circuit state and the expected voltage ripple presettingallThe specific expression is as follows:
wherein, Pin(t) is input instantaneous power, PoFor output power, ω =2 π fline，flineFor single-phase input frequency of AC network, integral interval [ Tline/8,3Tline/8]Charging time for the total energy storage capacitor of the DC bus, CallIs the total energy storage capacitance value of the DC bus, Δ E is the energy required to be stored by the total energy storage capacitance of the DC bus, Vdc_maxAnd Vdc_minRespectively, a maximum voltage value charged and a minimum voltage value discharged, Vdc_aveFor the total energy-storage capacitor of the DC busAverage voltage of, Δ Vdc＝Vdc_max-Vdc_minThe ripple voltage on the total energy storage capacitor of the direct current bus;
according to the above equation system, it can be obtained:
wherein, Vm、ImThe amplitudes of the ac input voltage and current are provided.
Step two: based on a current control current source method, the equivalent power impedance of the two-port split virtual capacitor is solved in an s domain, and a specific expression is as follows:
wherein, CdcThe capacitance value of the small-capacity passive capacitor, N is an impedance control function value, and s is a frequency domain;
it can be shown that the two-port split virtual capacitor can be equivalent to CdcAnd equivalent virtual capacitance N.CdcParallel connection, namely:
Call＝(N+1)Cdc
step three: and (3) calculating a real-time impedance control function value N by combining the first step and the second step, wherein a specific expression is as follows:
at this time, from the energy absorption angle, the secondary ripple energy on the bus voltage is absorbed by two parts of the two-port split virtual capacitor, a small part of the secondary ripple energy is absorbed by the small-capacity passive capacitor, and the rest of the secondary ripple energy is absorbed by the energy storage capacitor in the power converter, wherein the specific expression is as follows:
wherein, Δ E is the energy required to be absorbed by the total energy storage capacitor of the direct current bus; delta ECdcIs a small-capacity passive capacitor CdcThe energy absorbed; delta ECsFor energy-storage capacitor C in power convertersThe energy absorbed. The voltage, current and power waveforms of the power converter in the two-port split virtual capacitor in the embodiment are shown in fig. 2.
Step four: the method adopts a voltage and current double closed-loop control strategy to split the two ports into a virtual capacitor equivalent capacitance value and an energy storage capacitor CsControlling the voltage at two ends; calculating the error between the average voltage of the small energy-storage capacitor and the given reference value of the average voltage of the small energy-storage capacitor, and comparing the error with i after passing through a voltage compensator*After addition, the desired split current i is generated2Wherein i is*Controlling a function value N and a small-capacity passive capacitor C for real-time impedancedcThrough which a current i flows1The product of (a). Calculating a split current i2Actual value and split current i2After passing through the current compensator, the error generates a PWM square wave modulation signal to control a switching tube S of an H bridge in the two-port split virtual capacitor in real time1-S4Thereby achieving the purpose of eliminating output ripples.
From the electromagnetic torque equation:
Tc＝1.5p(ψfiq+(Ld-Lq)idiq)
it can be seen that the motor electromagnetic torque is determined by the q-axis current component, the voltage fluctuation of the dc bus voltage is reduced, and the frequency fluctuation in the q-axis current is reduced, so that the motor electromagnetic torque fluctuation is significantly reduced.
By the equation of motion:
wherein id、iqD and q axis stator currents respectively; l isd、LqD-axis and q-axis inductors respectively; psifIs a permanent magnetic linkage; p is the number of pole pairs of the motor; t is a unit ofeIs the motor electromagnetic torque; t isLIs the load torque; r isΩThe damping coefficient of the motor; j is the rotational inertia of the motor rotor; omegarIs the mechanical angular velocity of the motor. From this equation, the motor speed is determined by the electromagnetic torque of the motor, with the motor load torque unchanged. Therefore, the fluctuation of the rotating speed of the motor during the operation of the motor is reduced.
In conclusion, the circuit control parts of the invention are mutually independent and are simultaneously carried out, so that the invention has the advantages of high input power factor, long service life and excellent driving performance while effectively inhibiting the voltage fluctuation of the direct current bus, and can effectively solve the problems of serious voltage fluctuation of the direct current bus and poor static and dynamic performance of the motor of the existing small-capacitance frequency converter with the motor load driving system.
Examples
To verify the validity of the inventive scheme, the following simulation experiment was performed.
The specific implementation parameters of this embodiment are as follows: single-phase AC input voltage 220Vac/50Hz, DC bus voltage 400V, and small-capacity capacitor C on DC busdc150uF, energy storage capacitor C in power converters265uF, where N is 22. The effect of using a small electrolytic capacitor and a two-port split dummy capacitor under the same circuit conditions is shown in fig. 5.
It can be seen that through the control, the two-port split virtual capacitor has the same effect as the passive large-capacity electrolytic capacitor, plays the same role of ripple power absorption, and uses the active switch to enable the small-capacity capacitor C on the direct current bus to have the same effectdcEnergy storage capacitor C for transferring power incapable of being absorbed to power convertersIn (1). Due to the energy storage capacitor CsThe large voltage fluctuation is allowed, so that the capacitance value can be obviously reduced, the power density of the whole machine is improved, the original PFC function is ensured, and the voltage fluctuation of the bus is effectively inhibited.
The technical features of the above embodiments can be arbitrarily combined, and for the sake of brevity, all possible combinations of the technical features in the above embodiments are not described, but should be considered as the scope of the present specification as long as there is no contradiction between the combinations of the technical features.
The above-mentioned embodiments only express several embodiments of the present application, and the description thereof is more specific and detailed, but not construed as limiting the scope of the present application. It should be noted that, for a person skilled in the art, several variations and modifications can be made without departing from the concept of the present application, which falls within the scope of protection of the present application. Therefore, the protection scope of the present application shall be subject to the appended claims.
Claims (8)
1. The utility model provides a take permanent magnet synchronous motor load's little electric capacity converter output ripple eliminating system which characterized in that: the permanent magnet synchronous motor comprises a single-phase alternating current input, a single-phase uncontrolled diode rectifier, a PFC converter, a two-port split type virtual capacitor, an inverter and a permanent magnet synchronous motor, wherein the input end of an uncontrolled rectifier circuit unit is connected with the single-phase alternating current input, the anode of the output end of the uncontrolled rectifier circuit is connected with the anode of the input end of the PFC converter, and the cathode of the output end of the uncontrolled rectifier circuit is connected with the cathode of the input end of the PFC converter; the positive electrode of the output end of the PFC converter is connected with the positive electrode of the input end of the two-port split virtual capacitor, and the negative electrode of the output end of the PFC converter is connected with the negative electrode of the input end of the two-port split virtual capacitor; the positive electrode of the output end of the two-port split virtual capacitor is connected with the positive electrode of the direct current bus, and the negative electrode of the output end of the two-port split virtual capacitor is connected with the negative electrode of the direct current bus; the positive pole of the input end of the inverter is connected with the positive pole of the direct current bus, the negative pole of the input end of the inverter is connected with the negative pole of the direct current bus, and the output end of the inverter is connected with the three-phase winding of the permanent magnet synchronous motor;
the two-port split virtual capacitor is composed of a small-capacity film/ceramic capacitor (C)dc) And an inductor (L)2) Energy storage capacitor (C)s) And first to fourth power switching tubes (S)1-S4) The H-bridge power converters are formed in parallel, wherein the thin film/ceramic capacitor (C) with small capacitydc) The positive output terminal and the main power diode (D) in the PFC converterb) Cathode, inductance (L)2) Is connected to one end of an inductor (L)2) The other end of the first power switch tube (S)1) Source electrode of (1), second power switch tube (S)2) Is connected with the drain electrode of the thin film/ceramic capacitor (C)dc) Negative output end and third power switch tube (S)3) Source electrode of (1), fourth power switch tube (S)4) Is connected to the drain of the first power switch tube (S)1) Drain electrode of (1), third power switch tube (S)3) Drain electrode of (1), and energy storage capacitor (C)s) Is connected to one end of the second power switch tube (S)2) Source electrode of (1), fourth power switch tube (S)4) Source electrode, storage capacitor (C)s) The other ends of the two are connected.
2. The system for eliminating the output ripple of the small-capacitance frequency converter with the permanent magnet synchronous motor load according to claim 1, is characterized in that: the single-phase uncontrolled diode rectification circuit is composed of a first to a fourth rectifying diode (D)1-D4) Is composed of a first rectifying diode (D)1) And a third rectifying diode (D)3) Are connected in series to form a bridge arm and a second rectifier diode (D)2) And a fourth rectifying diode (D)4) Forming another bridge arm.
3. The small-capacitance frequency converter output ripple eliminating system with the permanent magnet synchronous motor load according to claim 1, is characterized in that: PFC converter with boost inductor (L)b) Main power diode (D)b) Main power switch tube (S)b) A Boost PFC circuit is formed, wherein the direct current side positive output end of the single-phase uncontrolled diode rectifying circuit and a Boost inductor (L)b) Is connected to a boost inductor (L)b) The other end of the main power switch tube (S) and the main power switch tube (S) simultaneouslyb) Drain electrode of (D), main power diode (D)b) Is connected with the anode of the main power switch tube (S)b) The source electrode of the single-phase uncontrolled diode rectifying circuit, the direct current side negative output end of the single-phase uncontrolled diode rectifying circuit and a small-capacity film/ceramic capacitor (C)dc) Negative output terminal connected to the main power diode (D)b) Cathode and small capacity thin film/ceramic capacitor (C)dc) The positive output end is connected.
4. The system for eliminating the output ripple of the small-capacitance frequency converter with the permanent magnet synchronous motor load according to claim 1, is characterized in that: energy storage capacitor (C)s) Value and energy storage capacitor CsThe voltage variation range is related to the type of the adopted power converter, and the specific relationship is as follows:
wherein Vm、ImThe amplitudes of the AC input voltage and current are respectively, omega =2 pi fline，flineFor single-phase input frequency, V, of AC mainsc_maxAnd Vc_minAre respectively an energy storage capacitor CsThe maximum and minimum values of the instantaneous voltage.
5. The system for eliminating the output ripple of the small-capacitance frequency converter with the permanent magnet synchronous motor load according to claim 1, is characterized in that: the three-phase inverter circuit comprises first to sixth inverter switching tubes (S)i1-Si6) Is composed of a first inverter switching tube (S)i1) Drain electrode of (1), third inverter switching tube (S)i3) Drain electrode of (1), and fifth inverter switching tube (S)i5) Drain electrode of (2) and small-capacity thin film/ceramic capacitor (C)dc) The positive output end is connected with the second inverter switch tube (S)i2) Source electrode of (1), fourth inverter switching tube (S)i4) Source electrode of (1), sixth inverter switching tube (S)i6) Source electrode and small capacity thin film/ceramic capacitor (C)dc) Negative output end connected, first inverter switching tube (S)i1) Is connected with the second inverter switch tube (S)i2) Drain electrode of (1), one end of the load of the permanent magnet synchronous motor, and a third inverter switching tube (S)i3) Is connected to the fourth inverter switching tube (S)i4) Drain electrode of (2), one end of the permanent magnet synchronous motor load, and a fifth inverter switching tube (S)i5) Is connected with the sixth inverter switch tube (S)i6) Drain electrode of and permanent magnet synchronous motor loadTo one end of (a).
6. A small-capacitance frequency converter output ripple eliminating control method with a permanent magnet synchronous motor load is characterized by comprising the following steps: the control system for eliminating the output ripple of the small-capacitance frequency converter with the permanent magnet synchronous motor load according to any one of claims 1 to 5, so as to realize the control for eliminating the output ripple of the small-capacitance frequency converter with the permanent magnet synchronous motor load, comprises the following steps:
the method comprises the following steps: detecting the whole circuit state of the two-port split virtual capacitor, and calculating the total energy storage capacitance value C of the direct current bus required by the ripple absorption according to the circuit state and the expected voltage ripple presettingallThe specific expression is as follows:
wherein, Pin(t) is input instantaneous power, PoFor output power, ω =2 π fline，flineFor single-phase input frequency of AC network, integral interval [ Tline/8,3Tline/8]Charging time for the total energy storage capacitor of the DC bus, CallIs the total energy storage capacitance value of the DC bus, delta E is the energy required to be stored by the total energy storage capacitance of the DC bus, Vdc_maxAnd Vdc_minRespectively, the maximum voltage value charged and the minimum voltage value discharged, Vdc_aveIs the average voltage, deltaV, across the total energy storage capacitor of the DC busdc＝Vdc_max-Vdc_minThe ripple voltage on the total energy storage capacitor of the direct current bus;
comprehensively obtaining the total energy storage capacitance value of the direct current bus:
wherein, Vm、ImThe amplitudes of the alternating input voltage and the alternating input current are respectively;
step two: based on a current control current source method, the equivalent power impedance of the two-port split virtual capacitor is solved in an s domain, and a specific expression is as follows:
wherein, CdcThe capacitance value of the small-capacity passive capacitor is N, the impedance control function value is N, and the frequency domain is s;
the two-port split type virtual capacitor can be equivalent to CdcAnd equivalent virtual capacitance N.CdcParallel connection, namely:
Call＝(N+1)Cdc
step three: and (3) calculating a real-time impedance control function value N by combining the first step and the second step, wherein a specific expression is as follows:
step four: the method adopts a voltage and current double closed-loop control strategy to split the two ports into a virtual capacitor equivalent capacitance value and an energy storage capacitor CsThe voltage at two ends is controlled, which specifically comprises the following steps:
calculating the error between the average voltage of the small energy-storage capacitor and the given reference value of the average voltage of the small energy-storage capacitor, and comparing the error with i after passing through a voltage compensator*After addition, the desired split current i is generated2Wherein i is*Controlling the function value N and the small-capacity passive capacitor (C) for real-time impedancedc) Through which a current i flows1The product of (a); calculating a split current i2Actual value and split current i2After passing through the current compensator, the error generates a PWM square wave modulation signal to control a switching tube (S) of an H bridge in the two-port split virtual capacitor in real time1-S4) Thereby achieving the purpose of eliminating output ripples.
7. A computer device comprising a memory, a processor and a computer program stored in the memory and executable on the processor, wherein when the processor executes the computer program, the method for controlling the output ripple cancellation of the small-capacitance frequency converter with the load of the permanent magnet synchronous motor according to claim 6 is used for controlling the output ripple cancellation of the small-capacitance frequency converter with the load of the permanent magnet synchronous motor.
8. A computer-readable storage medium, on which a computer program is stored, which, when being executed by a processor, implements a small-capacitance inverter output ripple cancellation control with a permanent magnet synchronous motor load based on the small-capacitance inverter output ripple cancellation control method with a permanent magnet synchronous motor load according to claim 6.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202210879351.9A CN115276503B (en) | 2022-07-25 | 2022-07-25 | Output ripple eliminating system of small-capacitance frequency converter with permanent magnet synchronous motor load and control method |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202210879351.9A CN115276503B (en) | 2022-07-25 | 2022-07-25 | Output ripple eliminating system of small-capacitance frequency converter with permanent magnet synchronous motor load and control method |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN115276503A true CN115276503A (en) | 2022-11-01 |
| CN115276503B CN115276503B (en) | 2024-05-14 |
Family
ID=83769349
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202210879351.9A Active CN115276503B (en) | 2022-07-25 | 2022-07-25 | Output ripple eliminating system of small-capacitance frequency converter with permanent magnet synchronous motor load and control method |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN115276503B (en) |
Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN106803721A (en) * | 2017-02-17 | 2017-06-06 | 江苏大学 | PMSM Drive System no electrolytic capacitor power inverter and control method |
| CN111082646A (en) * | 2019-12-25 | 2020-04-28 | 广州金升阳科技有限公司 | Current ripple eliminating circuit and power converter using same |
| CN113258795A (en) * | 2021-04-13 | 2021-08-13 | 江苏大学 | Small-capacitance power converter, power grid side power quality control working method thereof and bus voltage suppression control method |
-
2022
- 2022-07-25 CN CN202210879351.9A patent/CN115276503B/en active Active
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN106803721A (en) * | 2017-02-17 | 2017-06-06 | 江苏大学 | PMSM Drive System no electrolytic capacitor power inverter and control method |
| WO2018149041A1 (en) * | 2017-02-17 | 2018-08-23 | 江苏大学 | Permanent magnet synchronous motor drive system power converter not employing electrolytic capacitor, and control method thereof |
| CN111082646A (en) * | 2019-12-25 | 2020-04-28 | 广州金升阳科技有限公司 | Current ripple eliminating circuit and power converter using same |
| CN113258795A (en) * | 2021-04-13 | 2021-08-13 | 江苏大学 | Small-capacitance power converter, power grid side power quality control working method thereof and bus voltage suppression control method |
Non-Patent Citations (1)
| Title |
|---|
| 李研达;苗风东;高相铭;: "基于重复控制的单相整流驱动系统高功率因数实现方法", 电力电容器与无功补偿, no. 03, 25 June 2017 (2017-06-25) * |
Also Published As
| Publication number | Publication date |
|---|---|
| CN115276503B (en) | 2024-05-14 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN103248261B (en) | Loop current inhibition method of modularized multi-level converter | |
| CN101106338A (en) | Bidirectional power flow efficient energy saving converter | |
| CN107453395B (en) | Volage current transformer grid-connected current low-frequency harmonics suppressing method in cascaded H-bridges | |
| GB2610545A (en) | Small-capacitance power converter, and grid-side electrical-energy quality control working method and bus voltage suppression control method therefor | |
| CN108880209B (en) | Active damping control method of active third harmonic injection matrix converter | |
| CN108233403B (en) | MMC double-loop circulating current restraining method based on quasi-proportional resonant regulator | |
| CN111464103B (en) | Electrolytic capacitor network-free side current harmonic suppression method and system | |
| CN110460291A (en) | A kind of back-to-back current source type motor driven systems DC bus current Ripple Suppression method | |
| CN112003463A (en) | Single-phase PWM rectification DC side voltage secondary ripple suppression method | |
| CN113162505A (en) | Permanent magnet motor torque control method and system | |
| CN104253549A (en) | LCL filtering-based circuit topology structure of high-power PWM (pulse-width modulation) rectifier | |
| CN114435163B (en) | Double-battery integrated charging topology circuit of electric automobile and staggered control strategy method thereof | |
| CN109004849A (en) | A kind of Electric Servo Loading System PWM rectifier FAST RESPONSE | |
| CN108539779A (en) | Total power variable-ratio pumped storage based on MMC | |
| Haruna et al. | Behavior of a matrix converter with a feed back control in an input side | |
| CN105939121A (en) | Wind generator current-adjustment and phase-modulation control-based parallel DCM Boost PFC converter | |
| Feng et al. | An improved current control strategy of PWM rectifier under unbalanced grid voltage condition | |
| CN115276503B (en) | Output ripple eliminating system of small-capacitance frequency converter with permanent magnet synchronous motor load and control method | |
| Haruna et al. | Control Strategy for a Matrix Converter with a Generator and a Motor | |
| CN114465515A (en) | Energy storage type MMC topology capable of avoiding battery microcirculation and control method thereof | |
| CN204190641U (en) | Based on the high-power PWM rectifier circuit topological structure of LCL filtering | |
| Babadi et al. | Improved source-end current Power Quality performance of a BLDC motor drive using a novel DC-DC converter | |
| Zhou et al. | Secondary ripple suppression Strategy for a single-phase PWM rectifier based on constant frequency current predictive control | |
| CN114696630B (en) | Bootstrap-type compensated three-port converter and control method and system thereof | |
| Zhu et al. | DC-Link current optimal control of current source PWM converter |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |