CN101106338A - Bidirectional power flow efficient energy saving converter - Google Patents
Bidirectional power flow efficient energy saving converter Download PDFInfo
- Publication number
- CN101106338A CN101106338A CNA2006100289943A CN200610028994A CN101106338A CN 101106338 A CN101106338 A CN 101106338A CN A2006100289943 A CNA2006100289943 A CN A2006100289943A CN 200610028994 A CN200610028994 A CN 200610028994A CN 101106338 A CN101106338 A CN 101106338A
- Authority
- CN
- China
- Prior art keywords
- signal
- pwm
- resistor
- phase
- current
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Images
Landscapes
- Inverter Devices (AREA)
- Control Of Ac Motors In General (AREA)
Abstract
The invention relates to an energy-efficient bidirectional power flow transducer provided with a topological structure for dual PWM frequency conversion main circuit, combining three-phase PWM rectifying with three-phase PWM inverting to achieve a four-quadrant controlled transducer and realize bidirectional energy transmission between the power network and the motor. The power network can directly get electric energy feedback and braking torque can be adjusted automatically when power generation is delivered so that environmental protection and power saving can be realized. The great improvement of power factor both can effectively inhibit electromagnetic interference, harmonic pollution and can reduce switching loss. The entire systemis provided with double closed loop vector controlled scheme and adaptive function, is characterized in good static and dynamic performance and low frequency starting.
Description
Technical Field
The invention relates to a frequency converter, in particular to a frequency converter which can realize energy bidirectional transmission between a power grid and a motor, has high power factor and is efficient and energy-saving.
Background
The existing frequency converter is a general frequency converter which is mainly structurally characterized by uncontrollable rectification, direct current and inversion, and the control method is a space voltage vector.
However, such a frequency converter has some disadvantages. Firstly, when the motor is decelerated or the transmitted potential energy load is lowered, the motor is in a power generation state, six feedback diodes of the inverter of the frequency converter feed back the electric energy to the direct current side, and the electric energy cannot return to a power grid due to the one-way fluidity of the uncontrollable rectifier, so that the voltage of a direct current bus of the frequency converter is increased and the frequency converter cannot work normally. This energy must be handled to maintain the inverter dc bus voltage within a normal operating range.
As can be seen from fig. 1: the three-phase alternating current provides direct current voltage through the uncontrollable rectifier, the uncontrollable rectifier adopts a common diode, and due to the unidirectionality of the diode, when the motor is in a power generation state, and the electric energy enables the direct current bus voltage to rise by a certain value through the PWM inverter, the electric energy on the direct current bus is consumed by controlling the conduction of the insulated gate bipolar transistor Q1 to enable the brake resistor R to be conducted, so that the direct current voltage is reduced to an allowable value. This method not only wastes energy, but also pollutes the environment. In addition, since the input current of the rectifier is the charging current for the electrolytic capacitor E1, the current waveform is not a sine wave, the higher harmonic content is quite large, and the power factor of the frequency converter is low, which causes many adverse effects, such as: the capacity of the power grid is occupied; polluting the power grid, causing the voltage waveform of the power grid to be distorted, causing other equipment on the line to be incapable of working normally, and the like. Thirdly, the space voltage vector control mode for driving the PWM inverter is based on the steady-state mathematical model of the asynchronous motor, and the dynamic performance is not high.
Disclosure of Invention
The invention aims to solve the technical problem of providing a bidirectional power flow high-efficiency energy-saving frequency converter and aims to solve the defects.
In order to solve the technical problems, the invention is realized by the following technical scheme:
the invention comprises the following steps: PWM inverter, electrolytic capacitor, contactor, asynchronous motor, keyboard control display unit; further comprising: a phase, B phase and C phase of three-phase alternating current are respectively connected with R, S and T ends of a PWM rectifier through a first inductor, a second inductor and a third inductor, a P1 end of the PWM rectifier is connected with three input contacts of a contactor, three output contacts of the contactor are connected with a P end of a PWM inverter, a resistor is connected with the contactor in parallel, an N end of the PWM rectifier is connected with an N end of the PWM inverter, an anode of an electrolytic capacitor is connected with the P end of the PWM inverter, a cathode of the electrolytic capacitor is connected with the N end of the PWM inverter, and U, V and W ends of the PWM inverter are respectively connected with three phases of an asynchronous motor; the power grid voltage sampling signal, the input current sampling signal and the direct current voltage sampling signal are connected with the SPWM signal generation and open-phase protection unit, six driving output signals of the SPWM signal generation and open-phase protection unit are connected with the PWM rectifier, the SPWM signal generation and open-phase protection unit is connected with the flux linkage closed-loop vector control code parameter processing unit, the output voltage sampling signal, the output current sampling signal and the direct current voltage sampling signal are connected with the flux linkage closed-loop vector control code parameter processing unit, the driving signal of the flux linkage closed-loop vector control code parameter processing unit is connected with the PWM inverter, and the flux linkage closed-loop vector control code parameter processing unit is connected with the keyboard control display unit.
Compared with the prior art, the invention has the beneficial effects that: the double-PWM frequency conversion main circuit topological structure is adopted, three-phase PWM rectification and three-phase PWM inversion are combined together, a four-quadrant controlled frequency converter is realized, energy between a power grid and a motor is transmitted in two directions, electric energy can be directly fed back to the power grid when the motor generates electricity, braking torque can be automatically adjusted, the environment is protected, and electric energy is saved; the power factor is greatly improved, so that the electromagnetic interference and harmonic pollution can be effectively inhibited, and the switching loss is reduced; the whole system adopts a double closed-loop vector control scheme and a self-adaptive function, and has good static and dynamic characteristics and low-frequency starting characteristics.
Drawings
FIG. 1 is a block diagram of a prior art frequency converter;
FIG. 2 is a block diagram of the present invention;
FIG. 3 is a block diagram of a flux linkage closed loop vector control code parameter processing unit of FIG. 2;
FIG. 4 is a block diagram of the SPWM signal generation and open-phase protection unit of FIG. 2;
Detailed Description
The invention is described in further detail below with reference to the following figures and embodiments:
as can be seen from fig. 2, the present invention comprises: the system comprises a PWM inverter 2, an electrolytic capacitor E1, a contactor KM1, an asynchronous motor 3 and a keyboard control display unit 6; further comprising: a phase, B phase and C phase of three-phase alternating current are respectively connected with R, S and T ends of a PWM rectifier 1 through a first inductor L1, a second inductor L2 and a third inductor L3, a P1 end of the PWM rectifier 1 is connected with three input contacts of a contactor KM1, three output contacts of the contactor KM1 are connected with a P end of the PWM inverter 2, a resistor R1 is connected with the contactor KM1 in parallel, an N end of the PWM rectifier 1 is connected with an N end of the PWM inverter 2, an anode of an electrolytic capacitor E1 is connected with the P end of the PWM inverter 2, a cathode of the electrolytic capacitor E1 is connected with the N end of the PWM inverter 2, and U, V and W ends of the PWM inverter 2 are connected with three phases of an asynchronous motor 3; the power grid voltage sampling signal, the input current sampling signal and the direct current voltage sampling signal are connected with an SPWM signal generation and open-phase protection unit 4, six driving output signals of the SPWM signal generation and open-phase protection unit 4 are connected with a PWM rectifier 1, the SPWM signal generation and open-phase protection unit 4 is connected with a flux linkage closed-loop vector control code parameter processing unit 5, the output voltage sampling signal, the output current sampling signal and the direct current voltage sampling signal are connected with the flux linkage closed-loop vector control code parameter processing unit 5, a driving signal of the flux linkage closed-loop vector control code parameter processing unit 5 is connected with a PWM inverter 2, and the flux linkage closed-loop vector control code parameter processing unit 5 is connected with a keyboard control display unit 6.
The PWM rectifier 1 and the PWM inverter 2 are the same: all are composed of 6 IGBTs (insulated gate bipolar transistors);
1. the double-PWM mode is adopted, namely the rectifying part is also controlled by PWM waves, when the motor generates electricity, energy is directly fed back to a power grid through an SPWM rectifier, feedback current is sine wave, and the voltage phase of the power grid is automatically tracked, so that the frequency converter controlled by four quadrants is really realized.
2. And a vector control mode is adopted. The asynchronous motor is equivalent to a direct current motor through coordinate transformation, a magnetic field component and a torque component of stator current are decoupled and respectively controlled, and the torque can be quickly adjusted, so that ideal dynamic performance is obtained.
As can be seen from fig. 3, the flux linkage closed-loop vector control code parameter processing unit includes: rotor speed given signal omega * r With the speed feedback signal omega r After comparison, a torque set signal T is obtained via the speed regulator 7 * ；T * With rotor flux linkage Ψ 2 After division, a torque current given signal I is generated * t1 ，I * t1 And a torque current feedback signal I t1 After comparison, I is obtained via the torque current regulator 10 * t (ii) a Speed feedback signal omega r After passing through a flux weakening controller 20, the signal is used as a rotor flux linkage given signal psi * 2 ，Ψ * 2 With rotor linkage Ψ 2 After comparison, an exciting current given signal I is obtained through a flux linkage regulator 8 * m1 ，I * m1 And an excitation current feedback signal I m1 After comparison, I is obtained through the excitation current regulator 9 * m (ii) a Said I * t 、I * m 、ω r Obtaining an excitation voltage given signal U after current-voltage conversion 11 * m1 And torque voltage given signal U * t1 (ii) a The U is * m1 、U * t1 、sinθ 1 、cosθ 1 Obtaining U after inverse rotation transformation 12 * α1 、U * β1 ，U * α1 、U * β1 Obtaining three-phase voltage given signals U after 2/3 conversion 13 * u1 、U * v1 、U * w1 (ii) a The U is * u1 、U * v1 、U * w1 Generating a driving signal of the PWM inverter 2 through the gate control 14; output voltage sampling signal U UVW Obtaining U through 3/2 conversion 16 α1 、U β1 (ii) a Output current sampling signal I UVW Obtaining I by 3/2 conversion 17 α1 、I β1 (ii) a The Uα1 、U β1 、I α1 、I β1 Psi is obtained by observing 15 through flux linkage 2 、sinθ 1 、cosθ 1 (ii) a Said I α1 、I β1 、sinθ 1 、cosθ 1 After rotating and transforming 18, I is obtained m1 。I t1 (ii) a The U UVW 、I UVW After a speed estimation of 19, ω r 。
As can be seen from fig. 4, the SPWM signal generation and open-phase protection unit includes: the A phase voltage signal is connected with a first resistor R21 through a first rectifier 21, the first resistor R21 is connected with the anode of a first operational amplifier 22 through a second resistor R22, the anode and the output of the first operational amplifier 22 are connected through a third resistor R23, the anode of the first operational amplifier 22 is connected with the ground through a first capacitor C21, the output of the first operational amplifier 22 is connected with a polarity discriminator 25, the A phase voltage signal is also connected with the polarity discriminator 25, the A phase current signal is connected with the cathode of the first operational amplifier 22 through a second rectifier 31, the DC bus voltage signal is connected with a PWM (pulse width modulation) signal generating unit 24, the output of the PWM signal generating unit is connected with the input ends of the first inverter 23, a second inverter 36 and a third inverter 37, and the output end of the first inverter 23 is connected with the node of the first resistor R21 and the second resistor R22; the B phase voltage signal is connected with a fourth resistor R24 through a third rectifier 32, the fourth resistor R24 is connected with the anode of a second operational amplifier 38 through a fifth resistor R25, the anode and the output of the second operational amplifier 38 are connected through a sixth resistor R26, the anode of the second operational amplifier 38 is connected with the ground through a second capacitor C22, the output of the second operational amplifier 38 is connected with a polarity discriminator 25, the B phase voltage signal is also connected with the polarity discriminator 25, the B phase current signal is connected with the cathode of the second operational amplifier 38 through a fourth rectifier 33, and the output end of a second inverter 36 is connected with the node of the fourth resistor R24 and the fifth resistor R25; the phase-C voltage signal is connected with a seventh resistor R27 through a fifth rectifier 34, the seventh resistor R27 is connected with the anode of a third operational amplifier 39 through an eighth resistor R28, the anode and the output of the third operational amplifier 39 are connected through a ninth resistor R29, the anode of the third operational amplifier 39 is connected with the ground through a third capacitor C23, the output of the third operational amplifier 39 is connected with a polarity discriminator 25, the phase-C voltage signal is also connected with the polarity discriminator 25, the phase-C current signal is connected with the cathode of the third operational amplifier 39 through a sixth rectifier 35, and the output end of a third inverter 37 is connected with the nodes of the seventh resistor R27 and the eighth resistor R28; the six groups of outputs of the polarity discriminator 25 are respectively isolated by a first optical coupler 26, a second optical coupler 40, a third optical coupler 41, a fourth optical coupler 42, a fifth optical coupler 43 and a sixth optical coupler 44 and then used as a first driving signal G1, a second driving signal G2, a third driving signal G3, a fourth driving signal G4, a fifth driving signal G5 and a sixth driving signal G6 of the PWM rectifier 1; A. the three-phase current signals of B and C are connected with one input end of an AND gate 28 through a zero-current detection 27, the other input end of the AND gate 28 is connected with a PWM signal generating unit 24, and the output end of the AND gate 28 is also connected with the PWM signal generating unit 24; the direct current bus voltage signal is connected with the PWM signal generating unit 24; A. the voltage signals of the three phases B and C are connected with the negative input of a comparator 29 through a rectifier 30, the reference voltage is connected with the positive input of the comparator 29, the output end of the comparator 29 is connected with a PWM signal generating unit 24, and the PWM signal generating unit 24 is connected with a flux linkage closed-loop vector control code parameter processing unit.
The main properties of the invention are:
1. the input current is sine wave, and the phase of the network voltage is automatically tracked, and the power factor is larger than 0.95.
2. The optimal braking torque can be automatically adjusted according to the quantity of the regenerated electric energy.
3. Compared with the traditional frequency converter, the interference is reduced by more than half.
4. Full digital vector control mode, speed and current double-loop speed regulating system. Within the speed range of 1: 10, the speed precision is less than 0.5 percent, and the rising time of the rotating speed is less than or equal to 100ms; low speed overload capability up to 150% (5 hz); the carrier frequency is continuously adjustable from 1.0 KHz to 16.0 KHz; the output frequency resolution is 0.01Hz; the device has the functions of automatic starting, fault test recovery, dynamic parameter modification, overvoltage, overcurrent, overload, overheat and undervoltage protection, input undervoltage and open-phase protection, no-tripping function and the like.
A PWM rectifier, namely a chopping control type rectifier is adopted, the rectifier consists of 6 IGBTs, and when the voltage of a direct current bus rises to a certain value, the direct current bus works in an active inversion state. The specific process is that a phase voltage detection signal is charged and discharged to a capacitor at a frequency of tens of KHz, so that a waveform of a triangular wave of tens of KHz is superposed on a 50Hz sine wave, the waveform is used as a reference signal to be compared with an actual phase current detection signal, the deviation of the waveform passes through a high-gain amplifier with hysteresis characteristics, the on-off of the IGBT of the upper bridge arm and the lower bridge arm of the phase of the rectifier is controlled, the actual current is forced to continuously track the waveform of the given reference signal, and the feedback current is forced to be a sine wave, and the phase of the voltage of a power grid is automatically tracked. The unipolar type is adopted, and only the on-off of an upper bridge arm is controlled when the voltage is positive for a half cycle; and when the voltage is in a negative half cycle, only the on-off of the lower bridge arm is controlled.
Using a PWM signal generating unit: the IO port of the DSP chip TMS320F2407 of the flux linkage closed-loop vector control code parameter processing unit 5 generates a three-phase shared switching signal with a certain duty ratio and a frequency of tens of KHz. The duty ratio of the output switching signal of the PWM signal generation unit is adjusted according to the voltage value of the direct current bus: when the voltage value is higher, the duty ratio is increased, namely the charging time of the capacitor is increased, the discharging time of the capacitor is reduced, the effective value of the sine wave is increased, the effective value of the actual feedback current is also increased, and the brake torque is increased; when the voltage value is lower, the duty ratio is reduced, namely the charging time of the capacitor is reduced, the discharging time of the capacitor is increased, the effective value of the sine wave is reduced, the effective value of the actual feedback current is also reduced, and the reduction of the braking torque is realized.
And a double closed-loop vector control mode of a speed outer ring and a current inner ring is adopted. As shown in FIG. 3, the AC current I in the three-phase coordinate system UVW Can be equivalent to alternating current I under a two-phase static coordinate system through three/two conversion α1 、I β1 。
U α1 、U β1 This three/two transformation equation can be used as well.
Then converted into direct current I under a synchronous rotating coordinate system through rotation oriented according to the rotor m1 、 I t1 。
Magnetic linkage Ψ 2 The observation of (2) is carried out by a voltage model method,
note: l is r Is the inductance of the rotor and is,
L m is the mutual inductance between the stator and the rotor,
L s is the inductance of the stator and is,
σ is the leakage inductance coefficient and the inductance is,
u in voltage-current conversion * m1 、U * t1 、I * t 、I * m 、ω r The relationship of (1) is:
note: t is a unit of 1 Is the time constant of the stator and is,
T 2 is the time constant of the rotor and is,
counter-rotating converter VR -1 Middle U * m1 、U * t1 And U * α1 、U * β1 The relationship of (c) is:
the two/three transformation is the inverse process of the above three/two transformation, and the specific formula is as follows:
the flux weakening control is to keep the magnetic flux unchanged when the frequency is below the base frequency, and belongs to constant torque speed regulation; when the frequency is above the base frequency, a constant power region is entered where the magnetic flux decreases inversely with the frequency.
The speed estimation is due to the fact that the speed sensor is not used, and the rotating speed is estimated through sampling signals of output voltage and current.
Claims (4)
1. A bi-directional power flow high efficiency energy saving frequency converter comprising: the device comprises a PWM inverter (2), an electrolytic capacitor (E1), a contactor (KM 1), an asynchronous motor (3) and a keyboard control display unit (6); the method is characterized in that: further comprising: a phase, B phase and C phase of three-phase alternating current are respectively connected with R, S and T ends of a PWM rectifier (1) through a first inductor (L1), a second inductor (L2) and a third inductor (L3), a P1 end of the PWM rectifier (1) is connected with three input contacts of a contactor (KM 1), three output contacts of the contactor (KM 1) are connected with a P end of the PWM inverter (2), a resistor (R1) is connected with the contactor (KM 1) in parallel, an N end of the PWM rectifier (1) is connected with an N end of the PWM inverter (2), an anode of an electrolytic capacitor (E1) is connected with the P end of the PWM inverter (2), a cathode of the electrolytic capacitor (E1) is connected with the N end of the PWM inverter (2), and U, V and W ends of the PWM inverter (2) are connected with three phases of an asynchronous motor (3); the power grid voltage sampling signal, the input current sampling signal and the direct current voltage sampling signal are connected with an SPWM signal generation and open-phase protection unit (4), six driving output signals of the SPWM signal generation and open-phase protection unit (4) are connected with a PWM rectifier (1), the SPWM signal generation and open-phase protection unit (4) is connected with a flux linkage closed-loop vector control code parameter processing unit (5), the output voltage sampling signal, the output current sampling signal and the direct current voltage sampling signal are connected with the flux linkage closed-loop vector control code parameter processing unit (5), a driving signal of the flux linkage closed-loop vector control code parameter processing unit (5) is connected with a PWM inverter (2), and the flux linkage closed-loop vector control code parameter processing unit (5) is connected with a keyboard control display unit (6).
2. The bi-directional power flow energy efficient converter according to claim 1, wherein: the PWM rectifier (1) and the PWM inverter (2) are the same: are composed of 6 insulated gate bipolar transistors.
3. The bi-directional power flow energy efficient frequency converter according to claim 1 or 2, characterized in that: the flux linkage closed-loop vector control code parameter processing unit comprises: rotor speed given signal omega * r With the speed feedback signal omega r After comparison, a torque setting signal is obtained via a speed regulator (7)Number T * ；T * With rotor flux linkage Ψ 2 After division, a torque current given signal I is generated * t1 ，I * t1 With torque current feedback signal I t1 After comparison, I is obtained via the torque current regulator (10) * t (ii) a Speed feedback signal omega r After passing through a flux-weakening controller (20), the signal is used as a rotor flux linkage given signal psi * 2 ，Ψ * 2 With rotor flux linkage Ψ 2 After comparison, an exciting current given signal I is obtained through a flux linkage regulator (8) * m1 ，I * m1 And an excitation current feedback signal I m1 After comparison, I is obtained by exciting a current regulator (9) * m; said I * t 、I * m 、ω r Obtaining an excitation voltage given signal U after current-voltage conversion (11) * m1 And torque voltage given signal U * t1 (ii) a The U * m1 、U * t1 、sinθ 1 、cosθ 1 Obtaining U after inverse rotation transformation (12) * α1 、U * β1 ，U * α1 、U * β1 Obtaining a three-phase voltage given signal U after 2/3 conversion (13) * u1 、U * v1 、U * w1 (ii) a The U is * u1 、U * v1 、U * w1 Generating a driving signal of the PWM inverter (2) through gate control (14); output voltage sampling signal U UVW Through 3/2 conversion (16) to obtainTo U α1 、U β1 (ii) a Output current sampling signal I UVW Obtaining I by 3/2 conversion (17) α1 、I β1 (ii) a The U is α1 、U β1 、I α1 、I β1 Via flux linkage observation (15) to obtain psi 2 、 sinθ 1 、cosθ 1 (ii) a Said I α1 、I β1 、sinθ 1 、cosθ 1 After rotational transformation (18) I is obtained m1 。I t1 (ii) a The U is UVW 、I UVW After a speed estimation (19) omega is obtained r 。
4. The bi-directional power flow energy efficient frequency converter according to claim 1 or 2, characterized in that: SPWM signal generation and open-phase protection unit includes: the A phase voltage signal is connected with a first resistor (R21) through a first rectifier (21), the first resistor (R21) is connected with the anode of a first operational amplifier (22) through a second resistor (R22), the anode and the output of the first operational amplifier (22) are connected through a third resistor (R23), the anode of the first operational amplifier (22) is connected with the ground through a first capacitor (C21), the output of the first operational amplifier (22) is connected with a polarity discriminator (25), the A phase voltage signal is also connected with the polarity discriminator (25), the A phase current signal is connected with the cathode of the first operational amplifier (22) through a second rectifier (31), the direct current bus voltage signal is connected with a PWM signal generating unit (24), the output of the PWM signal generating unit is connected with the input ends of a first inverter (23), a second inverter (36) and a third inverter (37), and the output end of the first inverter (23) is connected with the node of the first resistor (R21) and the resistor (R22); the B phase voltage signal is connected with a fourth resistor (R24) through a third rectifier (32), the fourth resistor (R24) is connected with the anode of a second operational amplifier (38) through a fifth resistor (R25), the anode and the output of the second operational amplifier (38) are connected through a sixth resistor (R26), the anode of the second operational amplifier (38) is connected with the ground through a second capacitor (C22), the output of the second operational amplifier (38) is connected with a polarity discriminator (25), the B phase voltage signal is also connected with the polarity discriminator (25), the B phase current signal is connected with the cathode of the second operational amplifier (38) through a fourth rectifier (33), and the output end of a second inverter (36) is connected with the node of the fourth resistor (R24) and the fifth resistor (R25); the C phase voltage signal is connected with a seventh resistor (R27) through a fifth rectifier (34), the seventh resistor (R27) is connected with the anode of a third operational amplifier (39) through an eighth resistor (R28), the anode and the output of the third operational amplifier (39) are connected through a ninth resistor (R29), the anode of the third operational amplifier (39) is connected with the ground through a third capacitor (C23), the output of the third operational amplifier (39) is connected with a polarity discriminator (25), the C phase voltage signal is also connected with the polarity discriminator (25), the C phase current signal is connected with the negative pole of the third operational amplifier (39) through a sixth rectifier (35), and the output end of a third inverter (37) is connected with the node of the seventh resistor (R27) and the eighth resistor (R28); the six groups of outputs of the polarity discriminator (25) are respectively isolated by a first optical coupler (26), a second optical coupler (40), a third optical coupler (41), a fourth optical coupler (42), a fifth optical coupler (43) and a sixth optical coupler (44) and then serve as a first driving signal (G1), a second driving signal (G2), a third driving signal (G3), a fourth driving signal (G4), a fifth driving signal (G5) and a sixth driving signal (G6) of the PWM rectifier (1); A. the three-phase current signals of B and C are connected with one input end of an AND gate (28) through a zero-crossing current detection (27), the other input end of the AND gate (28) is connected with a PWM signal generation unit (24), and the output end of the AND gate (28) is also connected with the PWM signal generation unit (24); the direct current bus voltage signal is connected with a PWM signal generating unit (24); A. the voltage signals of the three phases B and C are connected with the negative input of a comparator (29) through a rectifier (30), the reference voltage is connected with the positive input of the comparator (29), the output end of the comparator (29) is connected with a PWM signal generating unit (24), and the PWM signal generating unit (24) is connected with a flux linkage closed-loop vector control code parameter processing unit.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNA2006100289943A CN101106338A (en) | 2006-07-14 | 2006-07-14 | Bidirectional power flow efficient energy saving converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNA2006100289943A CN101106338A (en) | 2006-07-14 | 2006-07-14 | Bidirectional power flow efficient energy saving converter |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN101106338A true CN101106338A (en) | 2008-01-16 |
Family
ID=39000075
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CNA2006100289943A Pending CN101106338A (en) | 2006-07-14 | 2006-07-14 | Bidirectional power flow efficient energy saving converter |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN101106338A (en) |
Cited By (26)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101854065A (en) * | 2010-06-02 | 2010-10-06 | 天津大学 | Control method of cascade boost chopper |
| CN101951222A (en) * | 2010-08-03 | 2011-01-19 | 天津大学 | Control method of brushless double-fed motor and application thereof |
| CN101976954A (en) * | 2010-09-30 | 2011-02-16 | 中国矿业大学 | Frequency converter and method for eliminating harmonic and compensating reactive power |
| CN102055345A (en) * | 2011-01-12 | 2011-05-11 | 芜湖瑞科技术有限公司 | Frequency converter for digital generator set |
| CN102182630A (en) * | 2011-03-30 | 2011-09-14 | 清华大学深圳研究生院 | Method for braking in series for frequency-conversion speed-regulating wind power generation water pumping system |
| CN102412735A (en) * | 2011-12-06 | 2012-04-11 | 中国煤炭科工集团太原研究院 | Control method used four-quadrant transducer |
| WO2012097529A1 (en) * | 2011-01-18 | 2012-07-26 | 江苏省电力公司常州供电公司 | Fully controlled rectifier device |
| CN103193116A (en) * | 2012-01-05 | 2013-07-10 | 苏州远志科技有限公司 | Integrated control system of elevator |
| CN103326600A (en) * | 2012-03-19 | 2013-09-25 | 上海利思电气有限公司 | Non-harmonic rectifying device for frequency converter |
| CN103560681A (en) * | 2013-11-11 | 2014-02-05 | 上海电气自动化设计研究所有限公司 | Four-quadrant frequency converter control device for AC drive system |
| CN103921669A (en) * | 2013-04-17 | 2014-07-16 | 济南田中工贸有限公司 | Electric slippage type chassis of engineering machinery |
| CN103956952A (en) * | 2013-04-17 | 2014-07-30 | 济南田中工贸有限公司 | Vector frequency conversion controller of synchronization frequency conversion type alternating current motor |
| CN104218820A (en) * | 2014-08-15 | 2014-12-17 | 广州日滨科技发展有限公司 | Four-quadrant frequency converter |
| CN105515487A (en) * | 2015-12-30 | 2016-04-20 | 武汉港迪电气传动技术有限公司 | Rotating speed tracking system of rotary mechanism |
| CN106329569A (en) * | 2016-08-31 | 2017-01-11 | 杭州威衡科技有限公司 | Variable frequency motor driving energy feedback closed-loop device |
| CN106953360A (en) * | 2017-04-25 | 2017-07-14 | 石狮市酷瑞电气有限责任公司 | A kind of powered recoverable frequency converter |
| CN107425756A (en) * | 2017-06-07 | 2017-12-01 | 深圳市新科瑞电气技术有限公司 | A kind of raise scaffold intelligent driving system |
| CN109185191A (en) * | 2018-09-25 | 2019-01-11 | 广东美的制冷设备有限公司 | The starting control method and device of DC fan, outdoor unit, air conditioner |
| CN109525121A (en) * | 2018-10-25 | 2019-03-26 | 明阳智慧能源集团股份公司 | The braking energy feeding control method of fan motor pitch-controlled system power conversion circuit |
| CN109525122A (en) * | 2018-10-25 | 2019-03-26 | 明阳智慧能源集团股份公司 | A kind of full-controlled rectifier control method of fan motor pitch-controlled system power conversion circuit |
| CN109923779A (en) * | 2016-10-19 | 2019-06-21 | 伊玛罗格股份有限公司 | Mixed-rectification device |
| CN110034690A (en) * | 2019-03-29 | 2019-07-19 | 南通大学 | A kind of Vienna rectifier model prediction Virtual shipyard control method |
| CN110463010A (en) * | 2017-04-12 | 2019-11-15 | 三菱电机株式会社 | Power inverter and contactless power supply system |
| CN110572048A (en) * | 2019-10-17 | 2019-12-13 | 中国人民解放军海军工程大学 | marine static frequency converter |
| CN111769747A (en) * | 2020-06-15 | 2020-10-13 | 珠海格力电器股份有限公司 | Control device and method of frequency converter and frequency converter |
| CN112557744A (en) * | 2020-12-11 | 2021-03-26 | 上海新时达电气股份有限公司 | Three-phase current detection method and circuit |
-
2006
- 2006-07-14 CN CNA2006100289943A patent/CN101106338A/en active Pending
Cited By (34)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101854065A (en) * | 2010-06-02 | 2010-10-06 | 天津大学 | Control method of cascade boost chopper |
| CN101951222A (en) * | 2010-08-03 | 2011-01-19 | 天津大学 | Control method of brushless double-fed motor and application thereof |
| CN101976954A (en) * | 2010-09-30 | 2011-02-16 | 中国矿业大学 | Frequency converter and method for eliminating harmonic and compensating reactive power |
| CN102055345A (en) * | 2011-01-12 | 2011-05-11 | 芜湖瑞科技术有限公司 | Frequency converter for digital generator set |
| WO2012097529A1 (en) * | 2011-01-18 | 2012-07-26 | 江苏省电力公司常州供电公司 | Fully controlled rectifier device |
| CN102182630A (en) * | 2011-03-30 | 2011-09-14 | 清华大学深圳研究生院 | Method for braking in series for frequency-conversion speed-regulating wind power generation water pumping system |
| CN102412735A (en) * | 2011-12-06 | 2012-04-11 | 中国煤炭科工集团太原研究院 | Control method used four-quadrant transducer |
| CN103193116A (en) * | 2012-01-05 | 2013-07-10 | 苏州远志科技有限公司 | Integrated control system of elevator |
| CN103326600A (en) * | 2012-03-19 | 2013-09-25 | 上海利思电气有限公司 | Non-harmonic rectifying device for frequency converter |
| CN103326600B (en) * | 2012-03-19 | 2015-10-21 | 利思电气（上海）有限公司 | A kind of frequency converter is used without harmonic wave rectification device |
| CN103921669A (en) * | 2013-04-17 | 2014-07-16 | 济南田中工贸有限公司 | Electric slippage type chassis of engineering machinery |
| CN103956952A (en) * | 2013-04-17 | 2014-07-30 | 济南田中工贸有限公司 | Vector frequency conversion controller of synchronization frequency conversion type alternating current motor |
| CN103921669B (en) * | 2013-04-17 | 2018-03-09 | 山东田中机械设备有限公司 | Electrically slipping formula engineering machinery chassis |
| CN103560681A (en) * | 2013-11-11 | 2014-02-05 | 上海电气自动化设计研究所有限公司 | Four-quadrant frequency converter control device for AC drive system |
| CN104218820A (en) * | 2014-08-15 | 2014-12-17 | 广州日滨科技发展有限公司 | Four-quadrant frequency converter |
| CN105515487A (en) * | 2015-12-30 | 2016-04-20 | 武汉港迪电气传动技术有限公司 | Rotating speed tracking system of rotary mechanism |
| CN105515487B (en) * | 2015-12-30 | 2018-02-23 | 武汉港迪电气传动技术有限公司 | A kind of rotating-speed tracking system of rotating mechanism |
| CN106329569A (en) * | 2016-08-31 | 2017-01-11 | 杭州威衡科技有限公司 | Variable frequency motor driving energy feedback closed-loop device |
| CN106329569B (en) * | 2016-08-31 | 2019-05-14 | 杭州威衡科技有限公司 | A kind of variable-frequency motor driving energy feedback closed-loop device |
| CN109923779A (en) * | 2016-10-19 | 2019-06-21 | 伊玛罗格股份有限公司 | Mixed-rectification device |
| CN109923779B (en) * | 2016-10-19 | 2021-07-27 | 伊玛罗格股份有限公司 | Hybrid rectifier |
| CN110463010B (en) * | 2017-04-12 | 2021-04-20 | 三菱电机株式会社 | Power conversion device and non-contact power supply system |
| CN110463010A (en) * | 2017-04-12 | 2019-11-15 | 三菱电机株式会社 | Power inverter and contactless power supply system |
| CN106953360A (en) * | 2017-04-25 | 2017-07-14 | 石狮市酷瑞电气有限责任公司 | A kind of powered recoverable frequency converter |
| CN107425756A (en) * | 2017-06-07 | 2017-12-01 | 深圳市新科瑞电气技术有限公司 | A kind of raise scaffold intelligent driving system |
| CN109185191A (en) * | 2018-09-25 | 2019-01-11 | 广东美的制冷设备有限公司 | The starting control method and device of DC fan, outdoor unit, air conditioner |
| CN109185191B (en) * | 2018-09-25 | 2023-12-01 | 广东美的制冷设备有限公司 | Start control method and device of direct current fan, outdoor unit and air conditioner |
| CN109525122A (en) * | 2018-10-25 | 2019-03-26 | 明阳智慧能源集团股份公司 | A kind of full-controlled rectifier control method of fan motor pitch-controlled system power conversion circuit |
| CN109525121A (en) * | 2018-10-25 | 2019-03-26 | 明阳智慧能源集团股份公司 | The braking energy feeding control method of fan motor pitch-controlled system power conversion circuit |
| CN110034690A (en) * | 2019-03-29 | 2019-07-19 | 南通大学 | A kind of Vienna rectifier model prediction Virtual shipyard control method |
| CN110572048A (en) * | 2019-10-17 | 2019-12-13 | 中国人民解放军海军工程大学 | marine static frequency converter |
| CN111769747A (en) * | 2020-06-15 | 2020-10-13 | 珠海格力电器股份有限公司 | Control device and method of frequency converter and frequency converter |
| CN111769747B (en) * | 2020-06-15 | 2021-08-31 | 珠海格力电器股份有限公司 | Control device and method of frequency converter and frequency converter |
| CN112557744A (en) * | 2020-12-11 | 2021-03-26 | 上海新时达电气股份有限公司 | Three-phase current detection method and circuit |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN101106338A (en) | Bidirectional power flow efficient energy saving converter | |
| Hu et al. | Incorporated operation control of DC microgrid and electric vehicle | |
| US9871462B2 (en) | Regenerative variable frequency drive with auxiliary power supply | |
| CN111628660B (en) | Compressor variable frequency speed regulating system and control method of direct current bus voltage | |
| CN105119536B (en) | A kind of motor driver topology and its control method | |
| CN110920422B (en) | High-power electric vehicle charging device based on current source and control method | |
| CN108418493B (en) | Common bus opens winding permanent magnet synchronous motor collaboration spaces vector modulation method | |
| CN106385214B (en) | High-speed permanent magnetic synchronous motor control method based on Modular multilevel converter | |
| CN204190636U (en) | PWM rectifier circuit topological structure | |
| CN104253549A (en) | LCL filtering-based circuit topology structure of high-power PWM (pulse-width modulation) rectifier | |
| CN112217238B (en) | Brushless doubly-fed generator system and control method thereof | |
| Zhang et al. | Three-Level PWM rectifier based high efficiency batteries charger for EV | |
| CN105958525B (en) | PWM grid-connected inverter control method of permanent magnet wind power generation system | |
| CN202841050U (en) | Cascaded high-voltage inverter speed regulating system with energy feedback function | |
| CN104378034B (en) | The operation control system of brushless ac compound rectifier excitation brshless DC motor | |
| CN204334399U (en) | The operation control system of brushless ac compound rectifier excitation brshless DC motor | |
| Wang et al. | DC-link current optimal control of current source converter in DFIG | |
| Chen et al. | On the PFC AC-DC converter fed SRM drives with reversible and regenerative braking capabilities | |
| Yu et al. | A Multi-energy Interface Electric-drive-reconstructed Onboard Charger for EVs with Integrated Control Strategy | |
| CN204190641U (en) | Based on the high-power PWM rectifier circuit topological structure of LCL filtering | |
| Zhou et al. | Research of electric vehicle on-board controller based on inverter time division multiplexing | |
| Zhu et al. | DC-Link current optimal control of current source PWM converter | |
| Miura et al. | Efficiency improvement of a gas engine cogeneration system by power factor control with an IGBT rectifier | |
| CN214591224U (en) | Drive circuit and drive device | |
| Ohnuma et al. | Control strategy for a three-phase to single-phase power converter using an active buffer with a small capacitor |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| C02 | Deemed withdrawal of patent application after publication (patent law 2001) | ||
| WD01 | Invention patent application deemed withdrawn after publication |
Open date: 20080116 |