CN114697941A - Low-power consumption Bluetooth baseband receiving method - Google Patents
Low-power consumption Bluetooth baseband receiving method Download PDFInfo
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Abstract
The invention provides a low-power-consumption Bluetooth baseband receiving method, and belongs to the technical field of wireless communication. Firstly, carrying out low-pass filtering processing on a digital baseband signal, and carrying out initial fixed gain adjustment on the filtered signal; then detecting the initial position of the GFSK signal by calculating the average power estimation value of the digital baseband signal after fixed gain adjustment; calculating and adjusting dynamic digital gain based on the average power estimated value; after demodulation of the GFSK signal, carrying out moving average filtering and down-sampling merging; and finally, correcting the phase error of the next GFSK signal by using the phase error estimation value demodulated by the current GFSK. Through the digital gain adjustment process, accurate and efficient receiving of digital baseband signals can be realized, and the stability and reliability of data transmission are enhanced; in addition, the reception performance can be improved.
Description
Technical Field
The invention provides a low-power consumption Bluetooth baseband receiving method, and belongs to the technical field of wireless communication.
Background
The low-power-consumption Bluetooth technology is one of the most popular short-distance wireless communication technologies in the world at present, and has good market application prospect. Although bluetooth low energy has the advantages of low power consumption, low delay, low cost and the like, the further development of bluetooth low energy is restricted by the defects of weaker noise immunity, sensitivity to external interference, shorter transmission distance and the like of bluetooth low energy, and the communication effect of bluetooth low energy is greatly influenced when the bluetooth low energy is applied and popularized in a scene with a severe communication environment.
The low power consumption Bluetooth mainly adopts GFSK as a modulation mode, and the design of a receiver is carried out based on the GFSK modulation. Gaussian Frequency Shift keying gfsk (gauss Frequency Shift keying) is widely applied in the field of wireless mobile communication due to its characteristics of concentrated power spectrum, capability of suppressing out-of-band radiation, compressed signal power, easy implementation and the like. When receiving, a receiver based on GFSK modulation converts an analog high-frequency signal into a digital baseband signal through analog-to-digital conversion and down-conversion, and the stability and reliability of data transmission are poor due to the fact that the low-power Bluetooth technology is sensitive to noise interference; in addition, the receiving performance of the receiver is greatly influenced by noise interference, so that less useful information is received. The current solution is to perform filtering processing and fixed gain adjustment on the digital baseband signal, but the adjustment of the digital baseband signal by using the fixed gain may cause errors in the demodulation process of the signal after the gain adjustment, which are inconsistent with the signal of the sender, and affect the stability of transmission.
Disclosure of Invention
The invention aims to provide a low-power-consumption Bluetooth baseband receiving method to solve the problems that signals are wrong in a demodulation process and transmission reliability is influenced due to the fact that fixed gain adjustment is carried out on baseband signals.
In order to achieve the above object, the present invention provides a low power consumption bluetooth baseband receiving method, which comprises the following steps: 1) preprocessing the received digital baseband signal to obtain a preprocessed signal and an initial fixed digital gain of the preprocessed signal;
2) according to the first set window length, carrying out sliding window average processing on the preprocessed signals, calculating the average power of each sliding window, comparing the average power with a target power representing the upper limit of the received power, and determining the digital gain of the corresponding sliding window:
if the average power of the current sliding window is lower than the target power and the ratio of the average power of the current sliding window to the target power is lower than the square of the ratio of the minimum digital gain to the initial fixed digital gain, the dynamic digital gain corresponding to the sliding window is the minimum digital gain; if the average power of the current sliding window is lower than the target power and the ratio of the average power of the current sliding window to the average power of the last sliding window is greater than 2 or less than 1/2, the dynamic digital gain coefficient of the current sliding window is the reciprocal of the result obtained by further extracting the ratio of the average power of the current sliding window to the target power, and the dynamic digital gain of the current sliding window is the product of the dynamic digital gain coefficient of the current sliding window and the initial fixed digital gain;
3) performing gain adjustment on the signals in the corresponding sliding windows according to the dynamic digital gain of each sliding window to obtain gain-adjusted signals;
4) and demodulating the gain-adjusted signal to obtain a demodulated signal.
The maximum power allowed by the receiver is the target power due to the limitation of the analog-to-digital conversion bit width of the receiver, so that for the case that the average power of the sliding window is smaller than the target power, the signal in the sliding window needs to be adjusted according to the specific values of the average power and the target power of the sliding window to enhance the receiving effect and ensure that the maximum receiving capability of the receiver is not exceeded. The ratio of the average power of the current sliding window to the target power is a power adjustment amount, the ratio of the minimum digital gain to the initial fixed digital gain is a single minimum amplitude gain adjustment amount, and if the power adjustment amount is lower than the square of the single minimum amplitude gain adjustment amount, it is indicated that the digital gain should be the minimum value at the moment, namely the minimum digital gain. The dynamic digital gain adjustment process of the invention can realize accurate and high-efficiency reception of digital baseband signals and enhance the stability and reliability of data transmission.
Further, in the bluetooth low energy baseband receiving method, if the average power of the current sliding window exceeds the target power in step 2), the dynamic digital gain of the current sliding window is the initial fixed digital gain.
The average power of the current sliding window exceeds the maximum received power of the receiver, which indicates that the signal in the sliding window should be adjusted to reduce the average power of the sliding window, and then the dynamic digital gain is the initial fixed digital gain obtained by preprocessing.
Further, in the bluetooth low energy baseband receiving method, if the average power of the current sliding window is equal to the average power of the previous sliding window in step 2), the dynamic digital gain of the current sliding window is the same as the dynamic digital gain of the previous sliding window.
The dynamic digital gain needs to be calculated by gains of a plurality of sliding windows to converge to a stable state, so if the average power of the sliding window is equal to the average power of the previous sliding window, it indicates that the corresponding dynamic digital gain should be the same and not changed.
Further, in the bluetooth low energy baseband receiving method, in step 1), the pre-processed signal is further subjected to sliding window averaging processing according to a second set window length, an average power of each sliding window is calculated, useful signal detection is performed according to the average power of the sliding window, and dynamic gain adjustment is performed on the detected useful signal:
and if the average power of the current sliding window is greater than the average power threshold value and the average power of the previous sliding window is less than the average power threshold value, judging that the signal of the current sliding window is a useful signal.
If the average power of the sliding window is smaller than the average power threshold, it indicates that the noise signal with low power in the window is more, and the useful signal with high power is less; if the average power of the sliding window is larger than the average power threshold value, the window is indicated to contain more useful signals; in addition, the starting position of the useful signal can be judged through the relation between the average power of two continuous sliding windows and the average power threshold value, and the useful signal can be accurately detected. Only the sliding window with more useful signals is selected for gain adjustment processing, so that the processing amount can be reduced, and the signal processing efficiency can be improved.
Further, in the bluetooth low energy baseband receiving method, after the useful signal is detected, if the sum of the average power increments of a continuously set number of sliding windows is greater than the average power increment threshold, the currently detected useful signal is not processed, and the useful signal detection is performed again.
The useful signal usually changes slowly, and if the average power increment of the useful signal is larger than the average power increment threshold, it indicates that the useful signal changes too fast, and a judgment error occurs, and it may be that a special noise signal is regarded as the useful signal, so the useful signal needs to be judged again. Through the useful signal checking process, the judgment accuracy of the useful signal can be further improved.
Further, in the bluetooth low energy baseband receiving method, if the digital baseband signal adopts a GFSK modulation method, the phase difference demodulation is performed on the signal after the gain adjustment in step 4) to obtain a demodulated signal.
Further, in the bluetooth low energy baseband receiving method, the demodulated signal is further re-modulated to obtain a re-modulated signal, a difference between phase information of the re-modulated signal and phase information of a corresponding digital baseband signal is calculated as a phase error, and a phase of a subsequently demodulated signal is adjusted according to the phase error.
Since the noise interference of the wireless channel affects the demodulation performance and the phase error changes little when a plurality of data packets are continuously received, the influence of the noise interference on the phase of the demodulated signal can be eliminated to a certain extent by calculating and correcting the phase error, and the demodulation performance of the signal is improved.
Further, in the bluetooth low energy baseband receiving method, the second set window length is related to a preamble sequence length of the digital baseband signal.
Further, in the bluetooth low energy baseband receiving method, the preprocessing includes performing low-pass filtering on the digital baseband signal through an FIR filter, and performing initial fixed digital gain adjustment on the filtered digital baseband signal.
In the low-power-consumption Bluetooth system, because the wireless channel environment is complex and changeable and the noise interference is serious, the low-pass filtering processing is carried out on the digital baseband signal so as to filter out the out-of-band noise interference and avoid the noise interference from influencing the receiving performance. In addition, in order to avoid the situation that the signal is subjected to low-pass filtering to generate large gain and the output signal of the filter is subjected to amplitude limiting, digital gain adjustment is carried out on the filtered digital baseband signal before the output of the low-pass filter.
Further, in the bluetooth low energy baseband receiving method, the average power of each sliding window is calculated for the preprocessed signal in step 2) by a two-stage averaging method.
The two-stage average estimation method is adopted, firstly, sampling points in each sliding window are divided into a group according to set time, average power of each group is calculated, then, average power of all groups in a single sliding window is calculated, and average power calculation is completed. The influence of the power abrupt change point on the average power value can be eliminated by calculating the average power in a grouping and grading mode.
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Fig. 1 is a flow chart of a baseband receiving method of the present invention;
FIG. 2 is a flow chart of average power estimation and GFSK signal detection according to the invention;
fig. 3 is a flow chart of dynamic digital gain adjustment of the GFSK signal according to the present invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to the accompanying drawings and embodiments.
The method comprises the following steps:
as shown in fig. 1, the method for receiving bluetooth low energy baseband according to the present invention comprises the following steps:
1) the baseband signal is received and pre-processed.
At the receiver side, it is generally necessary to down-convert and analog-to-digital convert the received modulated baseband signal to obtain a corresponding digital baseband signal. Because a large amount of noise interference exists in the digital baseband signal, low-pass filtering processing needs to be performed on the digital baseband signal to filter out-of-band noise influence, initial fixed gain adjustment is performed on the filtered signal, and the condition that the amplitude of the output signal of the filter is limited due to large gain of the filtered signal is avoided. Specifically, in the physical layer of the bluetooth low energy system, the system architecture refers to the physical layer part of the bluetooth 5.0 protocol, the bluetooth low energy mode used is an encoding mode S ═ 8(LE Coded S ═ 8PHY), and the digital baseband signal is z (k), then the digital baseband signal r (k) after passing through the low-pass FIR filter can be represented as:
wherein k is 0,1,2, …; h (n) is a tap coefficient of the FIR filter; n is the number of tap coefficients.
The tap coefficients of the FIR filter can be generated by a Taylor window by a window function method according to different sampling frequencies and cut-off frequencies, wherein the cut-off frequency is 650kHz and the sampling frequency is 12 MHz. r (k) through an initial fixed digital gain GfixedObtaining a digital baseband signal y '(k) used for calculating the average power estimation value after adjustment, wherein the expression of y' (k) is as follows:
y′(k)＝r(k)·Gfixed
2) and carrying out useful signal detection on the preprocessed digital baseband signal.
The preprocessed digital baseband signal still contains a lot of noise, and if the preprocessed digital signal is directly adjusted, the noise signal in the preprocessed digital baseband signal is also adjusted, so that the processing amount is increased. Therefore, when the receiver receives the digital baseband signal, the receiver needs to perform useful signal detection to reduce the processing amount of subsequent gain adjustment. As shown in fig. 2, the gain-adjusted digital baseband signal is subjected to average power estimation and signal detection to determine the start position of the useful signal. Specifically, the following two-stage averaging method is adopted to calculate an average power estimation value according to the digital baseband signal after fixed gain adjustment:
first sampling frequency FsCorresponding to the number of sampling points within 1 mu s being FsThe sampling point within 1 mu s can be knownThe number is 12, and the power average value of the sampling point number in 1 mu s is calculated
I.e. the first order average power value.
The expression of (a) is:
wherein, FsIs the sampling frequency in MHz; n is 0,1,2, …; [. the]*The complex conjugate is taken.
Then selecting proper sliding window length according to the length of the preamble sequence of the data packet of the low-power-consumption Bluetooth system, and calculating the average power of all 1 mu s packets in the sliding window by a sliding window averaging method
I.e., the second order average power value. Since bluetooth low energy has two broad classes of data transmission modes: the method comprises an LE Uncoded PHY mode and an LE Coded PHY mode, wherein leader sequences of data packets in the two data transmission modes have different lengths, the length of the leader sequence in the LE Uncoded PHY mode is 8 mu s, and the length of the leader sequence in the LE Coded PHY mode is 80 mu s. Therefore, the lengths of the divided sliding windows are different corresponding to different preamble sequences in different transmission modes, the window length in LE unused PHY mode is 2 mus, and the window length in LE Coded PHY mode is 8 mus. In this embodiment, the low power consumption bluetooth uses an LE Coded PHY mode, so that the length of the preamble sequence of the data packet is 80 μ s, and the length of the sliding window is set to 8 μ s.
The expression of (a) is:
wherein m is 0,1,2, …; w is the sliding window length. The two-stage average power value thus obtained is an average power estimation value (the same as the average power of the sliding window below), and the average power estimation value is used for detecting the initial position of the GFSK signal. The average power is calculated in a grouping and grading mode, the influence of the power abrupt change point on the average power value can be eliminated, and the calculation complexity is low.
The step of detecting the start position of the GFSK signal based on the average power estimate is as follows (in the embodiment, the average power threshold pow _ thr is 2)8The average power increment threshold value pow _ raise _ thr is 25Initial fixed digital gain Gfixed＝27Minimum digital gain Gmin＝22)：
a) Calculating the average power of the current sliding window
And determines its relationship to the average power threshold pow _ thr:
if the average power of the current sliding window
Below the average power threshold pow _ thr, the condition is satisfied:
the GFSK signal is deemed not to be detected, no signal is received at that time, and the calculation of the next sliding window average power continues
If the average power of the current sliding window
Exceeds the average power threshold pow _ thr and the average power of the last sliding window
Below the average power threshold pow _ thr, the condition is satisfied:
the GFSK signal is considered to be detected, and the GFSK signal begins to be received at the moment, and the average power of the next sliding window is continuously calculated
And the average power increment of two adjacent sliding windows
b) After the GFSK signal is detected, if the average power increment of four continuous sliding windows exists
If the sum exceeds the average power increment threshold value pow _ raise _ thr, the condition is satisfied:
where T is the sliding window time at which the GFSK signal is detected. If the above conditions are met, the change of the average power is considered to be too fast, and the GFSK signal does not exist, at the moment, the receiving state is reset to be a non-receiving signal, and the step a) is returned to detect the GFSK signal again.
c) After the GFSK signal is detected, if the window slides to the end of the preamble sequence of the GFSK signal, the average power increment of four continuous sliding windows
If the sum is lower than the average power increment threshold value pow _ raise _ thr, the average power estimation and the detection of the GFSK signal are finished.
3) The sliding windows are subdivided for the useful signal and the dynamic digital gain is calculated within each sliding window.
As shown in fig. 3, dynamic digital gain calculations and adjustments are made based on the average power estimate. Setting the target power as PtarIn the embodiment, the output bit width of the analog-to-digital converter is 14 bits, wherein 1 bit is a sign bit, and the rest 13-bit digital bits represent quantization precision, so that the target power Ptar＝213×2＝226The calculation method of the dynamic digital gain is as follows:
a) if the average power of the current sliding window
Not equal to the average power of the last sliding window
Namely:
when the above formula condition is satisfied, the calculation of the dynamic digital gain of the current sliding window is started, specifically as follows:
if the current sliding window
Exceeding the target power PtarNamely, the condition is satisfied:
dynamic digital gain GdynFor maximum digital gain, i.e. initially fixed digital gain Gfixed；
If the current sliding window
Below target power PtarAnd simultaneously satisfies the following conditions:
i.e. the average power of the current sliding window
To the target power PtarIs less than the single minimum amplitude gain adjustment Gmin/GfixedSquare of (d), then dynamic digital gain GdynIs a minimum digital gain Gmin；
If the current sliding window
Below target power PtarAnd simultaneously satisfies the following conditions:
I.e. the average power of the current sliding window
Is the average power of the last sliding window
2 times or 1/2, then the dynamic digital gain GdynCan be expressed as:
b) if the average power of the current sliding window
Equal to the average power of the last sliding window
Namely, the conditions are satisfied:
the dynamic digital gain G of the current sliding windowdynDigital gain G 'with a top sliding window'dynThe same is true.
c) For GFSK signal r in current sliding windoww(k) Y obtained after gain adjustmentw(k) Can be expressed as:
yw(k)＝rw(k)·Gdyn
d) after several sliding window dynamic gain calculations, the GFSK signal y (k) after dynamic gain adjustment can be represented as:
y(k)＝r(k)·Gdyn_last
wherein G isdyn_lastThe resulting gain value is calculated for the last sliding window.
As another embodiment, the dynamic gain adjustment may be directly performed on the output result of the filter. In addition, the sliding window is divided in the step 2) to detect useful signals by taking the window as a unit, the length of the sliding window is related to the length of the preamble sequence, the sliding window is divided in the step 3) to adjust the dynamic gain by taking the window as a unit, the length of the sliding window is only related to the adjustment precision, if the adjustment precision is higher, the length of the sliding window can be set to be smaller, otherwise, the length of the sliding window can be set to be larger. However, for the purpose of simplifying the processing flow, the window lengths of the two divided windows may take the same value.
4) And demodulating the signal after the dynamic digital gain adjustment.
Since the signal in this embodiment adopts the GFSK signal modulation method, it is necessary to perform phase difference demodulation on the signal after the dynamic digital gain adjustment. And after the amplitude angle of the GFSK signal after the dynamic digital gain adjustment is obtained, GFSK phase information is obtained, and differential processing is performed on the phase information to obtain GFSK soft bit information. In addition, smooth filtering and accumulation can be adoptedThe combining process is averaged to eliminate amplitude jitter. Specifically, the moving average filter adopts an FIR filter with all 1 tap coefficients, and the filter order is the sampling frequency F in MHzs. The down-sampling is performed by means of accumulation and combination, and F is usedsThe points are grouped and accumulated for averaging. Phase of GFSK signal after phase detection
Can be expressed as:
to pair
The oversampled soft bit information b' (k) after GFSK demodulation can be obtained by performing differential processing, and can be expressed as:
smoothing b '(k) by using a moving average filter to obtain curve-smoothed oversampled soft bit information b'avg(k) Can be expressed as:
where g (m) is a tap coefficient of the moving average filter, g (m) is 1, m is 0,1,2, …, and Fs. To b'avg(k) The soft bit information b (n) after the downsampling is obtained by performing cumulative average combining can be expressed as:
wherein n is 0,1,2, …, L/FsL is the GFSK signal length, FsIn MHz, is the sampling frequency. For accumulationAveraging the combined soft bit information b (n) to perform demodulation decision, and obtaining bit information x (n) as:
5) phase error estimation and correction is performed.
The information obtained after demodulation has a certain phase error, and the phase error of the subsequent data packet can be eliminated by calculating the phase error of the first data packet because the change of the phase error is small when a plurality of data packets are continuously received. Specifically, according to the bit information x (n) after the current demodulation decision, the GFSK modulation is performed again to obtain the phase information
The estimate of the phase error epsilon can be expressed as:
the phase error correction is performed at the next GFSK signal reception demodulation. The phase of the next GFSK signal is set to be psi (k), and the corrected phase psi can be obtained according to the estimated value epsilon of the phase errorc(k) Can be expressed as:
ψc(k)＝ψ(k)+ε
therefore, the receiving of the GFSK digital baseband signal is realized. For a low-power-consumption Bluetooth system, the GFSK modulation baseband receiving method is simple to implement, low in circuit complexity and capable of improving the anti-interference capability of the system, effectively improving the receiving performance and saving the cost of a receiver on the basis of meeting the requirements of low power consumption and low delay.
Claims (10)
1. A low power consumption Bluetooth baseband receiving method is characterized by comprising the following steps:
1) preprocessing the received digital baseband signal to obtain a preprocessed signal and an initial fixed digital gain of the preprocessed signal;
2) according to the first set window length, carrying out sliding window average processing on the preprocessed signals, calculating the average power of each sliding window, comparing the average power with a target power representing the upper limit of the received power, and determining the dynamic digital gain of the corresponding sliding window:
if the average power of the current sliding window is lower than the target power and the ratio of the average power of the current sliding window to the target power is lower than the square of the ratio of the minimum digital gain to the initial fixed digital gain, the dynamic digital gain corresponding to the sliding window is the minimum digital gain; if the average power of the current sliding window is lower than the target power and the ratio of the average power of the current sliding window to the average power of the previous sliding window is greater than 2 or less than 1/2, the dynamic digital gain coefficient of the current sliding window is the reciprocal of the result obtained after the ratio of the average power of the current sliding window to the target power is further processed, and the product of the dynamic digital gain coefficient of the current sliding window and the initial fixed digital gain is taken as the dynamic digital gain of the current sliding window;
3) performing gain adjustment on the signals in the corresponding sliding windows according to the dynamic digital gain of each sliding window to obtain gain-adjusted signals;
4) and demodulating the gain-adjusted signal to obtain a demodulated signal.
2. The bluetooth low energy baseband receiving method according to claim 1, wherein in step 2), if the average power of the current sliding window exceeds the target power, the dynamic digital gain of the current sliding window is an initial fixed digital gain.
3. The bluetooth low energy baseband receiving method according to claim 1 or 2, wherein in step 2), if the average power of the current sliding window is equal to the average power of the previous sliding window, the dynamic digital gain of the current sliding window is the same as the dynamic digital gain of the previous sliding window.
4. The bluetooth low energy baseband receiving method according to claim 1, wherein in step 1), the pre-processed signal is further subjected to sliding window averaging according to a second set window length, the average power of each sliding window is calculated, useful signal detection is performed according to the average power of the sliding window, and dynamic gain adjustment is performed on the detected useful signal:
and if the average power of the current sliding window is greater than the average power threshold value and the average power of the previous sliding window is less than the average power threshold value, judging that the signal of the current sliding window is a useful signal.
5. The bluetooth low energy baseband receiving method according to claim 4, wherein after the useful signal is detected, if the sum of the average power increments of a continuously set number of sliding windows is greater than the average power increment threshold, the currently detected useful signal is not processed any more, and the useful signal detection is performed again.
6. The bluetooth low energy baseband receiving method according to claim 1, wherein if the digital baseband signal adopts a GFSK modulation method, the gain-adjusted signal is subjected to phase difference demodulation in step 4) to obtain a demodulated signal.
7. The bluetooth low energy baseband receiving method according to claim 6, further performing signal modulation on the demodulated signal again to obtain a remodulated signal, calculating a difference between phase information of the remodulated signal and phase information of a corresponding digital baseband signal as a phase error, and adjusting a phase of a subsequently demodulated signal according to the phase error.
8. The bluetooth low energy baseband receiving method according to claim 4, wherein the second set window length is related to a preamble sequence length of the digital baseband signal.
9. The bluetooth low energy baseband receiving method according to claim 1, wherein the preprocessing comprises low pass filtering the digital baseband signal with a FIR filter and performing an initial fixed digital gain adjustment on the filtered digital baseband signal.
10. The bluetooth low energy baseband receiving method according to claim 1 or 9, wherein the average power of each sliding window is calculated in step 2) by a two-stage averaging method for the preprocessed signals.
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| CN117394928A (en) * | 2023-12-13 | 2024-01-12 | 苏州赛迈测控技术有限公司 | Bluetooth in-band spurious testing method |
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| CN115276921A (en) * | 2022-07-26 | 2022-11-01 | 深圳市极致汇仪科技有限公司 | Bluetooth frame type automatic detection method and system for tester and storage medium |
| CN117072155A (en) * | 2023-10-16 | 2023-11-17 | 克拉玛依市红都有限责任公司 | Temperature monitoring method, system, equipment and medium applied to petroleum exploitation |
| CN117394928A (en) * | 2023-12-13 | 2024-01-12 | 苏州赛迈测控技术有限公司 | Bluetooth in-band spurious testing method |
| CN117394928B (en) * | 2023-12-13 | 2024-02-27 | 苏州赛迈测控技术有限公司 | Bluetooth in-band spurious testing method |
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