CN114337249A - Three-port DC-DC converter based on quasi-Z source and switch capacitor and competition control method - Google Patents

Three-port DC-DC converter based on quasi-Z source and switch capacitor and competition control method Download PDF

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CN114337249A
CN114337249A CN202111388788.4A CN202111388788A CN114337249A CN 114337249 A CN114337249 A CN 114337249A CN 202111388788 A CN202111388788 A CN 202111388788A CN 114337249 A CN114337249 A CN 114337249A
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capacitor
diode
switch tube
power switch
inductor
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CN114337249B (en
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戚志东
张扬
周礼锋
沈致远
徐胜元
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Nanjing University of Science and Technology
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Abstract

The invention discloses a three-port DC-DC converter based on a quasi Z source and a switched capacitor and a competition control method. On the basis of a Boost circuit, the converter combines a switch capacitor unit consisting of a switch tube, a diode and a capacitor with a charge-discharge unit consisting of the switch tube, the diode and an inductor, and changes the connection mode of the capacitor inductor and the on-off condition of the diode in the circuit by controlling the on-off of 3 switch tubes, thereby achieving the effects of improving the voltage gain and charging and discharging of a second input source. The invention has higher voltage gain, the duty ratio D is within 0 to 0.5, the condition of limit duty ratio can be avoided, and meanwhile, the switched capacitor structure can reduce the voltage stress of a switching device, thus being suitable for new energy hybrid power generation systems such as fuel cells, photovoltaic cells and the like.

Description

Three-port DC-DC converter based on quasi-Z source and switch capacitor and competition control method
Technical Field
The invention belongs to the field of power electronic converters, and particularly relates to a three-port DC-DC converter based on a quasi-Z source and a switched capacitor and a competition control method.
Background
With the development of economy, the problems of energy shortage and environmental pollution become more serious. At present, the solar energy and wind energy power generation technology is mature in China and commercialized, but due to the defects of uneven distribution, high climate requirement and the like, the large-scale popularization and utilization are difficult to achieve, and the development is gradually weak. The hydrogen energy has the advantages of high efficiency, zero pollution, regeneration and the like, focuses on the development of various countries in the world, and becomes a hot spot for research and application of new energy. The proton exchange membrane fuel cell is a novel power generation device which directly converts hydrogen energy into electric energy, only generates water and heat in the reaction process, has the advantages of high efficiency, no pollution and high reliability, is widely applied to the fields of new energy automobiles, distributed power generation and the like, has great application prospect, and therefore a PEMFC hybrid power supply system becomes a research hotspot.
The output voltage of the PEMFC varies greatly, and only the step-up or step-down voltage cannot meet the requirement of practical application, so it is very important to select and design a suitable DC-DC converter. The existing PEMFC hybrid power supply system topology structure mainly includes two major types, one is to use a discrete power conversion unit to realize energy transfer between each port, and the other is to use an integrated multi-port DC-DC converter to realize energy transfer between each port. The multi-port DC-DC converter may be classified into a non-isolated type, a partially isolated type, and a fully isolated type. The ports of the full-isolation type and partial-isolation type converters are electrically isolated through a transformer, direct current is inverted into high-frequency alternating current, energy transmission among the ports is achieved through magnetic coupling, and the problems that a plurality of switching devices are needed, the size of the converter is large, and a control strategy is complex exist generally.
Disclosure of Invention
The invention aims to provide a three-port DC-DC converter based on a quasi Z source and a switched capacitor
The technical solution for realizing the purpose of the invention is as follows: a three-port DC-DC converter based on a quasi Z source and a switch capacitor is characterized by comprising a first input source VpeA second input source VbA first inductor L1A second inductor L2A third inductor L3Shunt diode D0First diode D1A second diode D2A third diode D3A fourth diode D4A fifth diode D5A sixth diode D6The seventh diode D7A first power switch tube S1A second power switch tube S2The third power switch tube S3A first capacitor C1A second capacitor C2A third capacitor C3A fourth capacitor C4A fifth capacitor C5A load R; wherein the first input source VpeAnode of the first diode D1Of a first input source VpeNegative pole of the first power supply is connected with a second input source VbNegative electrode of (1), first diode D1The cathode of the first power switch tube is connected with the second power switch tube S2Source electrode of the second power switch tube S2Drain electrode of the first transistor is connected with a second input source VbThe positive pole of (1), the first inductance L1One end of the first power switch tube S is connected with the second power switch tube S2Source electrode of, first inductor L1The other end of the first diode D is connected with a second diode D2And a shunt diode D0While being connected to a second capacitor C2Negative pole of (2), a second diode D2Cathode of the first capacitor C1Positive electrode and second inductor L2One end of (1), a first power switch tube S1Drain electrode of (D), shunt diode0Negative pole of (2) and second capacitor C2Anode of the first inductor is connected with the second inductor L2The other end of (1), a third inductance L3One end of the first power switch tube S is connected with the second power switch tube S2Drain electrode of (1), third inductance L3The other end of the second diode D is connected with a third diode D3Cathode and third power switch tube S3Source electrode of, a third diode D3Anode of the second power supply is connected with a second input source VbNegative pole of (1), third power switch tube S3Is connected with a seventh diode D7Cathode of (1), seventh diode D7Anode of the first power switch tube S1The fourth diode D4Anode and third capacitor C3Negative pole of the first power switch tube S1The drain electrode of (D), the fourth diode D4Cathode of the first diode is connected with a fifth diode D5Anode of, fourth capacitor C4Negative pole of (1) and a fifth capacitor C5Positive electrode of (2), third capacitor C3And a fifth diode D5Cathode of the first diode is connected with a sixth diode D6Anode of (2), sixth diode D6Cathode of the first capacitor is connected with a fourth capacitor C4And one end of the load R, a fifth capacitor C5The negative pole of the first power switch tube S is connected with the other end of the load R1A source electrode of (a); the first inductor L1A second inductor L2A first capacitor C1A second capacitor C2A second diode D2Shunt diode D0And a first power switch tube S1Form a quasi-Z source structure and further comprise a fourth diode D4A fifth diode D5A sixth diode D6A third capacitor C3A fourth capacitor C4And a fifth capacitance C5A capacitor unit constituting a switch, and a third inductor L3A third diode D3The seventh diode D7And a third power switch tube S3Forming a second input source V of continuous output currentbAnd a charging loop.
Compared with the prior art, the invention has the following remarkable advantages:
(1) according to the invention, the connection mode of the inductance and the capacitance in the circuit and the on-off condition of the diode are changed by controlling the on-off of the three switching tubes, so that the effects of improving the voltage gain and charging and discharging are achieved.
(2) The invention realizes the energy flow of two power supplies and a load through an integrated three-port DC-DC converter, reduces the number of used devices and reduces the cost.
(3) The duty ratio range of the power switching tube is 0-0.5, so that the condition of limit duty ratio is avoided.
(4) The invention adopts competitive control to eliminate the negative influence of artificially set parameters in rule control.
Drawings
FIG. 1 is a circuit diagram of a three-port DC-DC converter based on a quasi-Z source and a switched capacitor according to the present invention.
Fig. 2 is a single-input single-output mode equivalent circuit diagram of a three-port DC-DC converter based on a quasi-Z source and a switched capacitor according to the present invention. FIG. 2(a) shows a first power switch tube S1And (b) is an equivalent circuit diagram of all the power switch tubes being turned off.
Fig. 3 is a single-input dual-output mode equivalent circuit diagram of a three-port DC-DC converter based on a quasi-Z source and a switched capacitor according to the present invention. FIG. 3(a) shows a first power switch tube S1An equivalent circuit diagram of the other power switch tubes being turned on and off, and fig. 3(b) shows a third power switch tube S3The equivalent circuit diagram of the other power switch tubes being turned off when the power switch tube is turned on, and FIG. 3(c) shows the first power switch tube S1And a third power switch tube S3Equivalent circuit diagram of the shutdown.
Fig. 4 is an equivalent circuit diagram of the three-port DC-DC converter based on the quasi-Z source and the switched capacitor in different modes with double inputs and single output modes. FIG. 4(a) shows a first power switch tube S1And a second power switch tube S2Conducting, third power switch tube S3The equivalent circuit diagram of turn-off, FIG. 4(b) is the second power switch tube S2And (c) is an equivalent circuit diagram of all the power switch tubes being turned off.
Fig. 5 is a main waveform diagram of a three-port DC-DC converter based on a quasi-Z source and a switched capacitor according to the present invention in three operating modes. Wherein, fig. 5(a) is a waveform diagram of operating in a single-input single-output mode; FIG. 5(b) is a waveform diagram for operating in a single-input dual-output mode; fig. 5(c) is a waveform diagram for operating in a dual-input single-output mode.
FIG. 6 is a schematic diagram of a contention control strategy according to the present invention.
Detailed Description
The invention is further illustrated by the following examples in conjunction with the accompanying drawings.
As shown in FIG. 1, a three-port DC-DC converter based on a quasi-Z source and a switched capacitor comprises a first input source VpeA second input source VbA first inductor L1A second inductor L2A third inductor L3Shunt diode D0First diode D1A second diode D2A third diode D3A fourth diode D4A fifth diode D5A sixth diode D6The seventh diode D7A first power switch tube S1A second power switch tube S2The third power switch tube S3A first capacitor C1A second capacitor C2A third capacitor C3A fourth capacitor C4A fifth capacitor C5A load R; wherein the first input source VpeAnode of the first diode D1Of a first input source VpeNegative pole of the first input source is connected with a second input source VbNegative electrode of (1), first diode D1The cathode of the first power switch tube is connected with the second power switch tube S2Source electrode of the second power switch tube S2Drain electrode of the first transistor is connected with a second input source VbThe positive pole of (1), the first inductance L1One end of the first power switch tube S is connected with the second power switch tube S2Source electrode of, first inductor L1The other end of the second diode D is connected with a second diode D2And a shunt diode D0While being connected to a second capacitor C2Negative pole of (2), a second diode D2Cathode of the first capacitor C1Positive pole and second inductance L2One end of (1), a first power switch tube S1Drain electrode of (D), and shunt diode (D)0Negative pole of (2) and second capacitor C2Anode of the first inductor is connected with the second inductor L2The other end of (1), a third inductance L3One end of the first power switch tube S is connected with the second power switch tube S2Drain electrode of (1), third inductance L3One end of which is connected with a third diode D3Cathode and third power switch tube S3Source electrode of, a third diode D3Anode of the second power supply is connected with a second input source VbNegative pole of (1), third power switch tube S3Drain electrode of the diode is connected with a seventh diode D7Cathode of (1), seventh diode D7Anode of the first power switch tube S1The drain electrode of (D), the fourth diode D4Anode and third capacitor C3Is connected with the negative electrodeA power switch tube S1The drain electrode of (D), the fourth diode D4Cathode of the first diode is connected with a fifth diode D5Anode of, fourth capacitor C4Negative pole of (1) and a fifth capacitor C5Positive electrode of (1), third capacitor C3And a fifth diode D5Cathode of the first diode is connected with a sixth diode D6Anode of (2), sixth diode D6Cathode of the first capacitor is connected with a fourth capacitor C4And one end of the load R, a fifth capacitor C5The negative pole of the first power switch tube S is connected with the other end of the load R1A source electrode of (a); first inductance L1A second inductor L2A first capacitor C1A second capacitor C2A second diode D2Shunt diode D0And a first power switch tube S1Form a quasi-Z source structure and further comprise a fourth diode D4A fifth diode D5A sixth diode D6A third capacitor C3A fourth capacitor C4And a fifth capacitance C5A capacitor unit constituting a switch, and a third inductor L3A third diode D3The seventh diode D7And a third power switch tube S3Second input source V forming a continuation of the output currentbAnd the charging loop respectively establishes a state space model of the converter under each working mode on the basis of the TPC (three ports converter), so as to obtain the PEMFC hybrid power supply system controller. In single-input single-output mode, a first input source VpeOr a second input source VbSupplying power to a load through the quasi-Z source structure and the switched capacitor unit; in a dual-input single-output mode, the first input source VpeAnd a second input source VbThe power supply is combined, and the power is supplied to the load through the quasi Z source structure and the switch capacitor boosting unit; in single-input and double-output mode, the first input source VpeSupplying power to a load, and simultaneously supplying power to a second input source V through a quasi Z source structure cascade Buck structurebThe end is charged, and the reason for cascading the Buck structure is as follows: one is in single-input double-output mode, because of the first capacitor C1A second capacitor C2And a second input source VbInfluence of the relationship of (1), second input source VbWhen charging, an inductance unit is added to avoid clamping the output voltage; and the Buck structure comprising the inductance unit has the advantage of constant output current while reducing voltage, and just meets the charging requirement.
The invention can be divided into three working modes of single input and single output, double input and single output and single input and double output according to the number of the input and output ports. Suppose a first input source VpeVoltage at both ends is VpeA second input source VbThe voltage at both ends is VbThe voltage across the load R is VoA first inductor L1Has a current of IL1A second inductor L2Current is IL2A third inductor L3Current is IL3A first capacitor C1Voltage at both ends is VC1A second capacitor C2Voltage at both ends is VC2A third capacitor C3Voltage at both ends is VC3A fourth capacitor C4Voltage at both ends is VC4The voltage at two ends of the fifth capacitor is VC5A first power switch tube S1Duty ratio of D1A second power switch tube S2Duty ratio of D2The third power switch tube S3Duty ratio of D3Equivalent series resistance r, r of capacitor1With a switching period of TsThe three operating modes are described in detail:
the control waveform for the single input single output mode, in which the converter has two modes of operation, at t, is shown in FIG. 5(a)0～t1The equivalent circuit diagram of the phase is shown in fig. 2(a), in this mode, the first power switch tube is turned on S1On, the first input source VpeAnd a second capacitor C2For the first inductor L1Charging, first capacitor C1For the second inductor L2Charging, fifth capacitor C5To a third capacitor C3Charging while the fourth capacitor C4The power is supplied to the load R together; t is t1～t2The phase is a second mode, the equivalent circuit diagram of the second mode is shown in fig. 2(b), and the first power switch tube S1Off, first input source VpeAssociated with the first inductor L1A second inductor L2And a third capacitance C3Are jointly a first capacitor C1A second capacitor C2A fourth capacitor C4A fifth capacitor C5Charging and supplying power to the load R.
In this mode, the following relationships can be listed:
Figure BDA0003367959830000051
Figure BDA0003367959830000052
Figure BDA0003367959830000053
Figure BDA0003367959830000054
Figure BDA0003367959830000055
Figure BDA0003367959830000056
Figure BDA0003367959830000057
the output voltage is shown as formula (8)
Figure BDA0003367959830000058
Solving other direct current quantities as shown in formula (9)
Figure BDA0003367959830000061
Therefore, the voltage stress of the power switch tube and the diode device can be calculated, as shown in the formula (10)
Figure BDA0003367959830000062
The device current stress is as shown in equation (11)
Figure BDA0003367959830000063
Single input dual output mode the main waveform diagram is shown in fig. 5(b), and there are three modes of operation in one switching cycle. t is t0～t1The phase equivalent circuit is shown in fig. 3(a), and in the first mode, the first power switch tube S1Conducting, third power switch tube S3Is turned off when the first input source V ispeAnd a second capacitor C2For the first inductor L1Charging, first capacitor C1For the second inductor L2Charging, fifth capacitor C5To a third capacitor C3Charging while the fourth capacitor C4A third inductor L for supplying power to the load R3Is a second input source VbCharging; t is t1～t2The phase equivalent circuit is shown in fig. 3(b), and in the second mode, the first power switch tube S1Turn-off, third power switch tube S3Is turned on when the first input source V ispeAssociated with the first inductor L1A second inductor L2And a third capacitor C3Together being a third inductance L3A first capacitor C1A second capacitor C2A fourth capacitor C4A fifth capacitor C5Charged and is a second input source VbAnd a load R; t is t2～t3The phase equivalent circuit is shown in fig. 3(c), and in the third mode, the first power switch tube S1And a third power switch tube S3Off, first input source VpeAssociated with the first inductor L1A second inductor L2And a third capacitance C3Are jointly a first capacitor C1A second capacitor C2A fourth capacitor C4A fifth capacitor C5Charging and supplying power to load R, third inductor L3Is a second input source VbAnd (6) charging. The pattern satisfies relational expressions (1) to (11) and expressions (12) and (13):
Figure BDA0003367959830000071
Figure BDA0003367959830000072
knowing the output voltage VoThe expression is the same as the expression (8), and the power switch tube S3Diode D3、 D7The voltage stress and current stress of (a) are:
Figure BDA0003367959830000073
Figure BDA0003367959830000074
two-input single-output mode the main waveform diagram is shown in fig. 5(c), and there are three modes of operation in this mode during one switching cycle. t is t0～t1The equivalent circuit of the stage is shown in FIG. 4(a), the first power switch tube S of this stage1And a second power switch tube S2Are all conducted, and the second input source VbAnd a second capacitor C2For the first inductor L1Charging, first capacitor C1For the second inductor L2Charging, fifth capacitor C5To a third capacitor C3Charging while a fourth capacitor C4The power is supplied to the load R together; t is t1～t2The phase equivalent circuit is shown in fig. 4(b), and in the second mode, the first power switch tube S1Off, secondPower switch tube S2On, the second input source VbAssociated with the first inductor L1A second inductor L2And a third capacitance C3Are jointly a first capacitor C1A second capacitor C2A fourth capacitor C4A fifth capacitor C5Charging and supplying power to a load R; t is t2～t3The phase equivalent circuit is shown in fig. 4(c), and in the third mode, the first power switch tube S1And a second power switch tube S2Off, first input source VpeAssociated with the first inductor L1A second inductor L2And a third capacitance C3Are jointly a first capacitor C1A second capacitor C2A fourth capacitor C4A fifth capacitor C5And charging and supplying power to the load R. The relationships that can be listed in this mode are:
Figure BDA0003367959830000075
Figure BDA0003367959830000081
Figure BDA0003367959830000082
Figure BDA0003367959830000083
Figure BDA0003367959830000084
Figure BDA0003367959830000085
Figure BDA0003367959830000086
the output voltage obtained by the solution is shown as the formula (23)
Figure BDA0003367959830000087
Other dc-quantities in this mode are as follows:
Figure BDA0003367959830000088
in this mode, the voltage stress of the power switching tube and the diode is as follows:
Figure BDA0003367959830000089
the current stress of the power switch tube and the diode is as follows:
Figure BDA0003367959830000091
after the variable transfer function required to be controlled in each mode is obtained, the controller can be designed, after the variable transfer function is completed, mode switching is realized by adopting competitive control, and the first power switch tube S is used for competitive control1The third power switch tube S3Of the second input source VbAnd the load voltage as a basis for the determination. Compared with a regular control method, the method has the advantages that the problem that parameters are artificially set and parameter drift caused by battery aging is inconsistent is solved, so that at any time, the converter judges whether the mode needs to be switched according to the current maximum output power of the fuel battery, and the conditions that the battery is damaged due to overload and the like caused by parameter drift after the battery is aged are avoided.
The analysis of three working modes shows that the invention realizes the second input source V by an integrated three-port DC-DC converterbCharging and discharging, reducing devices usedThe number of the parts reduces the cost, the duty ratio is between 0 and 0.5, the condition of limit duty ratio can be avoided, and the reliability is improved. The converter adopts competition control, and 3 PI controllers in total are adopted, namely BDCR (Battery discharge current controller) for controlling the discharge current of the second input source, BCR (Battery discharge current controller) for controlling the charge current of the second input source and OVR (output voltage controller) for controlling the output voltage. The input of the 3 controllers is respectively a second input source discharge current ib,disSecond input source charging current ib,chaAnd an output voltage voRespectively with its reference value ib,disref，ib,charef，vo,refThe difference between the two, the output of 3 PI controllers is db,dis，db,chaAnd dvWherein d isb,cha，dvPlus a second input source SOC and a reference value SOCrefThe difference value of the first and second values is used as an input signal of the competition control, and further a judgment condition of the mode switching is obtained. From db,disAnd db,chaDecision switch tube S2Or a switching tube S3Working state of db,disIs the second power switch tube S2Duty ratio d of2，db,chaIs the third power switch tube S3Duty ratio d of3I.e. output duty cycle of d2/d3The output voltage is provided by a switch tube S1Control of duty cycle d1Is dv. The end result is: in the single-input single-output mode, the first power switch tube S1Working; under the single-input double-output mode, the first power switch tube S1And a third power switch tube S3Working; under the double-input single-output mode, the first power switch tube S1And a second power switch tube S2And (6) working.
In summary, a competitive control method for a three-port DC-DC converter based on a quasi-Z source and a switched capacitor adopts a competitive control strategy to realize automatic switching among various modes of the converter, which specifically includes:
if the current mode is in the single-input single-output mode, the basis for switching to the double-input single-output mode is the secondA power switch tube S1Whether the duty ratio of the first input source V reaches the upper limit value or not is judged, and the basis for switching to the single-input double-output mode is the second input source VbWhether a state of charge (SOC) is less than a lower limit;
if the current mode is in the single-input double-output mode, the basis for switching to the single-input single-output mode is the second input source VbWhether the SOC reaches the maximum value or not is judged, and the basis for switching to the double-input single-output mode is that the third power switch tube S3Whether the duty ratio of (b) reaches an upper limit value;
if the current mode is in a double-input single-output mode, the basis for switching to the single-input single-output mode is whether the second input source SOC is in a given interval, and the basis for switching to the single-input double-output mode is the second input source VbIs less than the lower limit value.
Compared with a rule-based control strategy, the competitive control eliminates the negative influence caused by parameter setting depending on human experience and has stronger adaptability. Even if the output characteristic of the battery is changed, the mode switching can be normally realized by the competitive control, and the reliability of the converter in operation is improved.
The invention adopts a non-isolated three-port DC-DC converter combining a quasi-Z source circuit and a switch capacitor boosting unit and a competition control method thereof. The connection mode of an inductance capacitor and the on-off condition of a diode in the circuit are changed by controlling the on-off of the three switching tubes, so that the effects of improving voltage gain and charging and discharging are achieved.
The invention designs a three-port DC-DC converter based on a quasi Z source and a switch capacitor, designs a competitive control strategy aiming at the converter, and has higher voltage gain, reduced voltage stress of devices and reduced converter cost compared with the traditional non-isolated DC-DC converter. Secondly, a Buck structure is introduced into the energy storage port, and the problem of output voltage clamping is solved. In addition, the duty ratio of the converter is 0-0.5, and the condition of limit duty ratio does not exist. The invention combs the on-off state and the topological power flow direction of the power switch tube in each mode, and deduces performance indexes such as voltage gain of the converter and voltage/current stress of the switch device in each mode. The invention designs a competitive control strategy to ensure that the converter automatically switches modes under different load powers. The strategy takes the duty ratio of a power switch tube and the SOC of a second input source as a judgment basis, compared with a control strategy based on a rule, the negative influence caused by parameter setting depending on human experience is eliminated by competitive control, along with the time lapse, the competitive control strategy based on the duty ratio and the SOC of the second input source can adapt to the current state of a battery, and even if the output characteristic of the battery is changed due to battery aging or external force factors, the mode switching can be normally realized by the competitive control.

Claims (6)

1. A three-port DC-DC converter based on a quasi Z source and a switch capacitor is characterized by comprising a first input source VpeA second input source VbA first inductor L1A second inductor L2A third inductor L3Shunt diode D0First diode D1A second diode D2A third diode D3A fourth diode D4A fifth diode D5A sixth diode D6The seventh diode D7A first power switch tube S1A second power switch tube S2The third power switch tube S3A first capacitor C1A second capacitor C2A third capacitor C3A fourth capacitor C4A fifth capacitor C5A load R; wherein the first input source VpeAnode of the first diode D1Of a first input source VpeNegative pole of the first input source is connected with a second input source VbNegative electrode of (1), first diode D1The cathode of the first power switch tube is connected with the second power switch tube S2Source electrode of the second power switch tube S2Drain electrode of the first transistor is connected with a second input source VbThe positive pole of (1), the first inductance L1One end of the first power switch tube S is connected with the second power switch tube S2Source electrode of, first inductor L1The other end of the first diode D is connected with a second diode D2And a shunt diode D0While being connected to a second capacitor C2Negative pole of (2), a second diode D2Cathode of the first capacitor C1Positive electrode and second electrode ofFeeling L2One end of (1), a first power switch tube S1Drain electrode of (D), shunt diode0Negative pole of (2) and second capacitor C2Anode of the first inductor is connected with the second inductor L2The other end of (1), a third inductance L3One end of the first power switch tube S is connected with the second power switch tube S2Drain electrode of (1), third inductance L3The other end of the second diode D is connected with a third diode D3Cathode and third power switch tube S3Source electrode of, a third diode D3Anode of the second power supply is connected with a second input source VbNegative pole of (1), third power switch tube S3Drain electrode of the diode is connected with a seventh diode D7Cathode of (1), seventh diode D7Anode of the first power switch tube S1The drain electrode of (D), the fourth diode D4Anode and third capacitor C3Negative pole of the first power switch tube S1The drain electrode of (D), the fourth diode D4Cathode of the first diode is connected with a fifth diode D5Anode of, fourth capacitor C4Negative pole of (1) and a fifth capacitor C5Positive electrode of (1), third capacitor C3And a fifth diode D5Cathode of the first diode is connected with a sixth diode D6Anode of (2), sixth diode D6Cathode of the first capacitor is connected with a fourth capacitor C4And one end of the load R, a fifth capacitor C5The negative pole of the first power switch tube S is connected with the other end of the load R1A source electrode of (a); the first inductor L1A second inductor L2A first capacitor C1A second capacitor C2A second diode D2Shunt diode D0And a first power switch tube S1Form a quasi-Z source structure and further comprise a fourth diode D4A fifth diode D5A sixth diode D6A third capacitor C3A fourth capacitor C4And a fifth capacitance C5A capacitor unit constituting a switch, and a third inductor L3A third diode D3The seventh diode D7And a third power switch tube S3Second input source V forming a continuation of the output currentbAnd a charging loop.
2. The quasi-Z source and switched capacitor of claim 1The three-port DC-DC converter is characterized by comprising three modes, namely a single-input single-output mode, a single-input double-output mode and a double-input single-output mode, wherein in the single-input single-output mode, the first power switch tube S1Working; under the single-input double-output mode, the first power switch tube S1And a third power switch tube S3Working; under the double-input single-output mode, the first power switch tube S1And a second power switch tube S2And (6) working.
3. The quasi-Z source and switched capacitor based three-port DC-DC converter according to claim 2, wherein the converter has two operating modes in a single-input single-output mode in one switching cycle, and in the first mode, the first power switch tube S1On, the first input source VpeAnd a second capacitor C2For the first inductor L1Charging, first capacitor C1For the second inductor L2Charging, fifth capacitor C5To a third capacitor C3Charging while the fourth capacitor C4The first power switch tube S supplies power to the load R together, and under the second mode1Off, first input source VpeAssociated with the first inductor L1A second inductor L2And a third capacitance C3Are jointly a first capacitor C1A second capacitor C2A fourth capacitor C4A fifth capacitor C5And charging and supplying power to the load R.
4. The quasi-Z-source and switched capacitor based three-port DC-DC converter according to claim 2, wherein the converter has three operation modes in a single-input and dual-output mode in one switching period, and in the first mode, the first power switch tube S1Conducting, third power switch tube S3Is turned off when the first input source V ispeAnd a second capacitor C2For the first inductor L1Charging, first capacitor C1For the second inductor L2Charging, fifth capacitor C5To a third capacitor C3Charging while the fourth capacitor C4Co-feedingA load R for power supply, a third inductor L3Is a second input source VbCharging, in the second mode, the first power switch tube S1Turn-off, third power switch tube S3Is turned on when the first input source V ispeAssociated with the first inductor L1A second inductor L2And a third capacitance C3Together being a third inductance L3A first capacitor C1A second capacitor C2A fourth capacitor C4A fifth capacitor C5Charged and is a second input source VbAnd a load R for supplying power, and a first power switch tube S in a third mode1And a third power switch tube S3Off, first input source VpeAssociated with the first inductor L1A second inductor L2And a third capacitance C3Are jointly a first capacitor C1A second capacitor C2A fourth capacitor C4A fifth capacitor C5Charging and supplying power to load R, third inductor L3Is a second input source VbAnd (6) charging.
5. The quasi-Z-source and switched-capacitor based three-port DC-DC converter according to claim 2, wherein the converter has three operation modes in a dual-input single-output mode in one switching period, and in the first mode, the first power switch tube S1And a second power switch tube S2On, the second input source VbAnd a second capacitor C2For the first inductor L1Charging, first capacitor C1For the second inductor L2Charging, fifth capacitor C5To a third capacitor C3Charging while the fourth capacitor C4The first power switch tube S supplies power to the load R together, and under the second mode1Turn-off, second power switch tube S2On, the second input source VbAssociated with the first inductor L1A second inductor L2And a third capacitance C3Are jointly a first capacitor C1A second capacitor C2A fourth capacitor C4A fifth capacitor C5Charging and supplying power to the load R, and in the third mode, the first power switch tube S1And a second power switchClosing pipe S2Off, first input source VpeAssociated with the first inductor L1A second inductor L2And a third capacitance C3Are jointly a first capacitor C1A second capacitor C2A fourth capacitor C4A fifth capacitor C5And charging and supplying power to the load R.
6. A competition control method for the three-port DC-DC converter according to claim 1, characterized in that it comprises:
if the current mode is in single-input single-output mode, the first power switch tube S1When the duty ratio reaches the upper limit value, switching to a double-input single-output mode; when the second input source VbThe SOC is smaller than the lower limit value, and the single-input double-output mode is switched;
if the current mode is in single-input double-output mode, when the second input source VbThe SOC reaches the maximum value and is switched to a single-input single-output mode; when the third power switch tube S3When the duty ratio reaches the upper limit value, switching to a double-input single-output mode;
if the current mode is in a double-input single-output mode, the current mode is the second input source VbThe SOC of (1) is in a given interval and is switched to a single-input single-output mode; when the second input source VbIs less than the lower limit value, and switches to the single-input dual-output mode.
CN202111388788.4A 2021-11-22 2021-11-22 Three-port DC-DC converter based on quasi-Z source and switched capacitor and competition control method Active CN114337249B (en)

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Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106787692A (en) * 2017-01-16 2017-05-31 华南理工大学 A kind of quasi- Z source converters of type switching capacity altogether
CN107565811A (en) * 2017-08-10 2018-01-09 燕山大学 High-gain Double-input direct-current converter and modulator approach based on switched capacitor network
CN107612332A (en) * 2017-09-29 2018-01-19 天津大学 The three Port Translation device systems applied to independent photovoltaic generating occasion
CN112467974A (en) * 2020-11-18 2021-03-09 哈尔滨理工大学 High-gain low-stress DC/DC converter for fuel cell
CN112803768A (en) * 2021-01-18 2021-05-14 福州大学 Three-port high-gain direct current converter
CN113098271A (en) * 2021-04-23 2021-07-09 南京理工大学 High-gain three-port DC-DC converter based on switch capacitor

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106787692A (en) * 2017-01-16 2017-05-31 华南理工大学 A kind of quasi- Z source converters of type switching capacity altogether
CN107565811A (en) * 2017-08-10 2018-01-09 燕山大学 High-gain Double-input direct-current converter and modulator approach based on switched capacitor network
CN107612332A (en) * 2017-09-29 2018-01-19 天津大学 The three Port Translation device systems applied to independent photovoltaic generating occasion
CN112467974A (en) * 2020-11-18 2021-03-09 哈尔滨理工大学 High-gain low-stress DC/DC converter for fuel cell
CN112803768A (en) * 2021-01-18 2021-05-14 福州大学 Three-port high-gain direct current converter
CN113098271A (en) * 2021-04-23 2021-07-09 南京理工大学 High-gain three-port DC-DC converter based on switch capacitor

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