CN114301267B - Driving method and device of switch tube and inverter - Google Patents
Driving method and device of switch tube and inverter Download PDFInfo
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- CN114301267B CN114301267B CN202210225662.3A CN202210225662A CN114301267B CN 114301267 B CN114301267 B CN 114301267B CN 202210225662 A CN202210225662 A CN 202210225662A CN 114301267 B CN114301267 B CN 114301267B
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Abstract
The application discloses a driving method and device of a switching tube and an inverter, and relates to the technical field of inverters. And determining a common mode voltage rejection component of the inverter according to the common mode current and a first impedance, wherein the first impedance comprises at least one of a first resistor, a first inductor and a first capacitor, and the common mode voltage rejection component is used for rejecting the common mode current. And driving the switching tube according to the common mode voltage rejection component. By the mode, the common-mode current can be restrained in the working process of the inverter, and the waveform quality of the inverter inductance current is improved.
Description
Technical Field
The present disclosure relates to the field of inverter technologies, and in particular, to a driving method and device for a switching tube, and an inverter.
Background
In order to reduce the floor drain current of the photovoltaic inverter, the midpoint of a filter capacitor of the existing three-phase inverter is mostly connected to the midpoint of a direct-current bus, so that a low-impedance path is provided for the common-mode current. Therefore, most common-mode current flows back to the midpoint of the direct-current bus through the neutral line, and the current of the inverter to the ground drain can be greatly reduced.
However, the common-mode current loop inside the inverter is composed of a direct-current bus capacitor, a switching tube, an inverter inductor and a filter capacitor, the damping of the path is small, LC resonance is easy to form, the current stress of the switching tube is increased, and the waveform quality of the current of the inverter inductor is influenced.
Disclosure of Invention
The application aims to provide a driving method and device of a switching tube and an inverter, which can suppress common-mode current in the working process of the inverter and improve the waveform quality of inverter inductance current.
In order to achieve the above object, in a first aspect, the present application provides a driving method of a switching tube, the method comprising:
obtaining the current of each phase of the inverter, and determining the common-mode current of the inverter according to the average value of the currents;
determining a common mode voltage rejection component of the inverter according to the common mode current and a first impedance, wherein the first impedance comprises at least one of a first resistor, a first inductor and a first capacitor, and the common mode voltage rejection component is used for rejecting the common mode current;
and driving the switch tube according to the common mode voltage rejection component.
In an alternative form, determining a common-mode voltage rejection component of the inverter from the common-mode current and a first impedance includes:
determining a common mode voltage rejection component of the inverter by:
In an optional manner, the method further comprises:
obtaining a common-mode voltage of the inverter;
determining a system impedance of the inverter according to the common mode voltage and the common mode voltage rejection component;
controlling the imaginary part of the system impedance to be smaller than a first preset threshold value so as to determine a resonance angular frequency;
and determining the system impedance and a system damping ratio according to the resonance angular frequency to determine the size of the parameter of the first impedance, wherein the parameter of the first impedance comprises R0, A and B.
In an alternative form, the controlling the imaginary part of the system impedance to be less than a first preset threshold to determine a resonant angular frequency includes:
defining the imaginary part of the system impedance as a first function, and carrying out differential operation on the first function to obtain a second function;
calculating an initial resonance angular frequency according to the characteristic values of the electronic components in the inverter;
and determining the resonance angular frequency according to the initial resonance angular frequency, the first function and the second function.
In an alternative manner, the determining the resonance angular frequency according to the initial resonance angular frequency, the first function and the second function includes:
setting a value of the first impedance to a first value;
respectively substituting the first numerical value and the initial resonance angular frequency into the first function and the second function for calculation;
judging whether the absolute value of the calculation result of the first function is smaller than a second preset threshold value or not;
if so, taking the current resonance angular frequency as the resonance angular frequency;
if not, respectively substituting the current resonance angular frequency, the difference value between the first numerical value and the ratio between the first function and the second function into the first function and the second function for calculation, and judging whether the absolute value of the calculation result of the first function is smaller than a second preset threshold value or not again.
In an alternative mode, the determining the system impedance to system damping ratio according to the resonance angular frequency to determine the magnitude of the parameter of the first impedance includes:
when a = B =0, the signal is transmitted,
according to
Determining a first curve of the system impedance as a function of the first resistance, wherein Rsys is the system impedance and R is a loop total resistance of the inverter,
for the said resonant angular frequency, the frequency of the resonance,
is a delay factor;
according to
Determining a second curve of the system damping ratio as a function of the first resistance, wherein
Is the system damping ratio;
and determining the size of R0 according to the first curve and the second curve.
In an optional manner, the method further comprises:
acquiring a power grid voltage, and determining an angle of the power grid voltage according to the power grid voltage;
obtaining an inversion voltage of each phase of the inverter based on the angle of the grid voltage and the current of each phase of the inverter;
calculating a zero sequence component according to the inversion voltage and the modulation strategy of each phase of the inverter;
the driving the switching tube according to the common mode voltage rejection component includes:
and driving the switching tube according to the inversion voltage, the zero sequence component and the common mode voltage rejection component of each phase of the inverter.
In an alternative mode, the obtaining the inverted voltage of each phase of the inverter based on the angle of the grid voltage and the current of each phase of the inverter includes:
converting the current of each phase of the inverter through an abc/dq coordinate system based on the angle of the grid voltage and the current of each phase of the inverter to obtain the current under the dq coordinate system;
obtaining an inversion voltage under the dq coordinate system according to the current under the dq coordinate system;
and transforming the inverted voltage in the dq coordinate system through a dq/abc coordinate system to obtain the inverted voltage of each phase in the abc coordinate system, wherein the inverted voltage of each phase in the abc coordinate system is the inverted voltage of each phase of the inverter.
In an optional manner, the calculating the zero sequence component according to the inverter voltage and the modulation strategy of the inverter includes:
and if the modulation strategy is SVPWM, the zero-sequence component is a negative value of half of the sum of the maximum value and the minimum value in each phase of the inverter.
In an optional manner, the driving the switching tube according to the inverted voltage, the zero sequence component and the common mode voltage rejection component of each phase of the inverter includes:
outputting a pulse width modulation signal according to the sum of the inversion voltage of each phase of the inverter, the zero sequence component and the common mode voltage suppression component;
and driving the switch tube according to the pulse width modulation signal.
In a second aspect, the present application provides a driving apparatus for a switching tube, applied to an inverter, the apparatus including:
the common-mode current calculation module is used for acquiring the current of each phase of the inverter and determining the common-mode current of the inverter according to the average value of the currents;
a common mode current rejection module, configured to determine a common mode voltage rejection component of the inverter according to the common mode current and a first impedance, where the first impedance includes at least one of a first resistor, a first inductor, and a first capacitor, and the common mode voltage rejection component is used to reject the common mode current;
and the driving module is used for driving the switching tube according to the common-mode voltage rejection component.
In a third aspect, the present application provides a control processing apparatus comprising:
at least one processor and a memory communicatively coupled to the at least one processor, the memory storing instructions executable by the at least one processor to enable the at least one processor to perform a method as described above.
In a fourth aspect, the present application provides an inverter, including at least one phase inverter circuit and the control processing device as described above;
the inverter circuit comprises at least one switching tube, and the control processing device is used for outputting pulse width modulation signals to drive the switching tube.
In a fifth aspect, the present application provides a non-transitory computer-readable storage medium having stored thereon computer-executable instructions that, when executed by a processor, cause the processor to perform the method as described above.
The beneficial effect of this application is: the driving method of the switching tube is applied to an inverter and comprises the steps of obtaining the current of each phase of the inverter and determining the common-mode current of the inverter according to the average value of the currents. And determining a common mode voltage rejection component of the inverter according to the common mode current and a first impedance, wherein the first impedance comprises at least one of a first resistor, a first inductor and a first capacitor, and the common mode voltage rejection component is used for rejecting the common mode current. Then, the switch tube is driven according to the common mode voltage rejection component. Furthermore, in the working process of the inverter, because the common-mode currents with different sizes can be output by controlling the driving process of the switching tubes, the switching tubes are driven by combining the common-mode voltage suppression component, the purpose of reducing the common-mode currents can be achieved, and the improvement of the waveform quality of the inverter inductance current is facilitated.
Drawings
One or more embodiments are illustrated by way of example in the accompanying drawings, which correspond to the figures in which like reference numerals refer to similar elements and which are not to scale unless otherwise specified.
Fig. 1 is a schematic circuit structure diagram of an inverter provided in an embodiment of the present application;
fig. 2 is a schematic circuit diagram of an inverter according to another embodiment of the present disclosure;
fig. 3 is a flowchart of a driving method of a switching tube according to an embodiment of the present disclosure;
fig. 4 is a flowchart of a method for determining a parameter of a first impedance according to an embodiment of the present disclosure;
fig. 5 is a schematic diagram of an equivalent model of a common mode loop according to an embodiment of the present application;
FIG. 6 is a schematic diagram illustrating an implementation of step 403 shown in FIG. 4, as provided in an embodiment of the present application;
FIG. 7 is a schematic diagram illustrating an implementation manner of step 603 shown in FIG. 6 according to an embodiment of the present application;
FIG. 8 is a schematic diagram of a first curve and a second curve provided by an embodiment of the present application;
FIG. 9 is a schematic illustration of an admittance curve provided by an embodiment of the present application;
fig. 10 is a schematic diagram of a current flowing through an inverter inductor according to an embodiment of the present application;
fig. 11 is a schematic diagram of a current flowing through an inverter inductor according to another embodiment of the present application;
fig. 12 is a schematic diagram of a current flowing through an inverter inductor according to another embodiment of the present application;
fig. 13 is a schematic diagram of a current flowing through an inverter inductor according to another embodiment of the present application;
fig. 14 is a flowchart of a driving method of a switching tube according to another embodiment of the present disclosure;
fig. 15 is a schematic structural diagram of a driving device of a switching tube according to an embodiment of the present disclosure;
fig. 16 is a schematic structural diagram of a driving apparatus of a switching tube according to another embodiment of the present application;
fig. 17 is a schematic structural diagram of a control processing device according to an embodiment of the present application.
Detailed Description
In order to make the objects, technical solutions and advantages of the embodiments of the present application clearer, the technical solutions in the embodiments of the present application will be clearly and completely described below with reference to the drawings in the embodiments of the present application, and it is obvious that the described embodiments are some embodiments of the present application, but not all embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present application.
Referring to fig. 1, fig. 1 is a schematic structural diagram of an inverter according to an embodiment of the present disclosure. As shown in fig. 1, the inverter includes at least one phase inverter circuit and a control processing device (not shown). In this embodiment, an example is given in which the inverter includes a three-phase inverter circuit. Wherein any one phase inverter circuit includes at least one switching tube, for example, the first phase inverter circuit in the inverter includes the first switching tube Q1A second switch tube Q2And a third switching tube Q3And a fourth switching tube Q4. The control processing device is used for outputting a pulse width modulation signal to drive the switch tube, so that direct current voltage on a PV (photovoltaic) solar panel is converted into alternating current voltage, and the alternating current voltage can be fed back to a commercial power transmission system or used for an off-grid power grid. For example, the control processing device can convert the dc voltage on the PV solar panel into the first ac voltage e by outputting the pwm signal to drive the switching tubes in the three-phase inverter circuitaA second alternating voltage ebWith a third alternating voltage ec. Wherein the first alternating voltage eaA second alternating voltage ebWith a third alternating voltage ecAlso referred to as first network voltage eaSecond grid voltage ebTo a third network voltage ec。
In an embodiment, any one of the inverter circuits further includes an inverter inductor, a filter capacitor, and a grid-side inductor. For example, the first phase inverter circuit further includes an inverter inductance L1Filter capacitor Cf1And network side inductance Lg1。
It should be noted that the hardware configuration of the inverter shown in fig. 1 is merely an example, and the inverter may have more or fewer components than shown in the figure, may combine two or more components, or may have a different configuration of components, and the various components shown in the figure may be implemented in hardware, software, or a combination of hardware and software including one or more signal processing and/or application specific integrated circuits. For example, the inverter circuit for each phase in the inverter may be as shown in fig. 2.
Fig. 3 is a flowchart of a driving method of a switching tube according to an embodiment of the present application, where the driving method is applied to an inverter, and here, the structure of the inverter may refer to the above detailed description for fig. 1 to fig. 2, and is not described again here. The driving method of the switching tube comprises the following steps:
step 301: and acquiring the current of each phase of the inverter, and determining the common-mode current of the inverter according to the average value of the currents.
Taking the circuit configuration shown in fig. 1 as an example, the currents of the three phases of the inverter are respectively the first phase currents iLaSecond phase current iLbWith a third phase current iLcThen the common mode current i of the invertercmIs icm＝(iLa＋iLb＋iLc)/3。
Step 302: and determining a common mode voltage rejection component of the inverter according to the common mode current and the first impedance.
The first impedance comprises at least one of a first resistor, a first inductor and a first capacitor, and the common mode voltage rejection component is used for rejecting a common mode current. It can be understood that the first impedance is an impedance virtually set by software, and not an actual electronic component, and the first impedance does not cause a loss of power in the inverter. Therefore, the inverter can keep the original working efficiency unchanged while the common-mode current is restrained through the common-mode voltage restraining component.
In an embodiment, the common mode voltage rejection component of the inverter may be determined by the following equation:
wherein, in the formula (1), Uc(t) is the common mode voltage rejection component, R0Is the resistance value of the first resistor, A is the inductance value of the first inductor, and B is the capacitance value of the first capacitorReciprocal, icm(t) is the common mode current, t is time.
In this embodiment, by setting the first resistance corresponding to proportional operation, the first inductance corresponding to differential operation, and the first capacitance corresponding to integral operation, the formula (1) can be obtained. Meanwhile, in the formula (1), R0At least one of A and B is not 0, wherein if R0When 0, the first impedance does not include the first resistance; if A is 0, the first impedance does not include the first inductor; if B is 0, the first impedance does not include the first capacitance. That is, R0And at least one of A and B is not 0, and the corresponding first impedance comprises at least one of a first resistor, a first inductor and a first capacitor. For example, the first impedance may include only the first resistor, the first resistor and the first inductor, or both the first resistor, the first inductor and the first capacitor.
Since the currents in the inverter can be directly obtained by detection, the common mode current is also a directly available parameter, whereas for equation (1) the parameters in the first impedance, i.e. R, need to be determined for the common mode voltage rejection component0And the sizes of A and B.
In an embodiment, in order to determine the parameter of the first impedance, as shown in fig. 4, the driving method of the switching tube further includes the following steps:
step 401: and acquiring the common-mode voltage of the inverter.
In one embodiment, the common mode voltage can be determined by the common mode current, and the circuit structure shown in fig. 1 is still taken as an example.
From kirchhoff's law:
wherein L is an inverter inductor (e.g. inverter inductor L)1) Inductance value of, R1Is a switching device (e.g. a first switching tube Q)1) Loss and inductance (e.g. inverter inductance L)1) Equivalent resistance of loss, ResrIs a filter capacitor (e.g. filter capacitor C)f1) Parasitic resistance, CfIs a filter capacitor (e.g. filter capacitor C)f1) Capacitance value of iLa、iLbAnd iLcRespectively, a current flowing through an inverter inductor L1Inverter inductor L2And an inverter inductance L3Current value of iCa、iCbAnd iCcRespectively flowing through the filter capacitor Cf1Filter capacitor Cf2And a filter capacitor Cf3Current value of UAOIs the voltage between points A and O, UBOIs the voltage between point B and point O, UCOIs the voltage between point C and point O.
The three equations in equation (2) are added and all the voltage current signals are decomposed into differential and common mode components. Wherein, according to the differential mode component in the current signal being 0, it can obtain:
wherein iLadmRepresents iLaDifferential mode component of (i)LbdmRepresents iLbDifferential mode component of (i)LcdmRepresents iLcDifferential mode component of (i)CadmRepresents iCaDifferential mode component of (i)CbdmRepresents iCbDifferential mode component of (i)CcdmRepresents iCcDifferential mode component of (i)gadmRepresents igaDifferential mode component of (i)gbdmRepresents igbDifferential mode component of (i)gcdmRepresents igcThe differential mode component of (a).
The three equations in equation (2) are added to remove the differential mode component, which can be obtained as follows:
wherein iLcmRepresents iLa、iLbOr iLcDifferential mode component of (i)CcmRepresents iCa、iCbOr iCcThe differential mode component of (a).
Let R ═ R1＋ResrCircuit for indicating inverterTotal resistance, and due to filter capacitance (e.g. filter capacitance C)f1) The capacitance is far larger than the Y capacitance and the parasitic capacitance of the battery panel of the inverter, and i can be approximately consideredLcm=iCcmThen iclcm and iCcm can be collectively denoted as icm, and thus equation (4) can be simplified as:
wherein icmRepresenting common-mode current, U, of inverterscmRepresenting the common mode voltage of the inverter. Then, when the circuit configuration of the inverter has been determined, L, CfAnd R are known values, as shown in equation (5), if the common mode current i is determinedcmCan determine the common mode voltage UcmThe size of (2).
Then, a common mode loop equivalent model is obtained according to equation (5), and the common mode loop equivalent model is shown in fig. 5. Wherein L is123The inductance is L. Cf123Is an equivalent capacitor with a capacitance value of Cf。R123The resistance value is R. The common mode loop is a typical second-order RLC series circuit, and the system is a second-order weak damping system under the condition of not adding extra control because the resistance value of the equivalent resistor is small. In the working process, each switching tube in the inverter is in a switching state, and the common-mode voltage contains more high-frequency components, so that the circuit can form a common-mode current oscillating for a long time. The first impedance provided by the embodiment of the application can suppress the common mode current, so that the stability of the operation of the inverter is improved.
Step 402: and determining the system impedance of the inverter according to the common-mode voltage and the common-mode voltage rejection component.
Step 403: the imaginary part of the system impedance is controlled to be smaller than a first preset threshold value to determine the resonance angular frequency.
After the common mode voltage is determined, the total voltage of the common mode loop in the inverter can be determined according to the common mode voltage and the common mode voltage suppression component, so that the system impedance of the inverter can be determined according to the total voltage of the common mode loop in the inverter. The circuit structure shown in fig. 1 is still taken as an example.
The formula (5) is rewritten into an s-function form, and the total voltage of the common-mode loop in the inverter can be obtained by combining the common-mode voltage rejection component as follows:
wherein the content of the first and second substances,
is the total voltage of the common mode loop in the inverter,
for common-mode voltage rejection components, TsIn order for the controller to control the cycle,
in order to be a delay factor, the delay factor,
in order to control the system delay, the control system delay comprises controller sampling calculation delay and zero-order retainer equivalent delay. And is provided with
Is related to the control scheme, i.e.
The method can be set according to practical application, and the embodiment of the present application is not particularly limited, for example, in one embodiment,
is 1, and in another embodiment,
is 1.5.
Rewriting equation (1) to the form of s function and substituting into equation (6) yields:
substituting s with j ω, the system impedance can be found to be:
where Z (j ω) represents the system impedance and ω represents the resonance angular frequency.
Substituting s in equation (7) with j and substituting into equation (8) can result in:
where Re (Z (j ω)) represents the real part of the system impedance and Im (Z (j ω)) represents the imaginary part of the system impedance.
The larger the real part of the system impedance is, the stronger the resistance is, and the stronger the resonance suppression capability is. Then, in an embodiment, the imaginary part of the system impedance may be controlled to be smaller than a first preset threshold value to promote the resonance suppression capability, and the resonance angular frequency may be determined.
Meanwhile, as can be seen from the formulas (9) and (10)
When the value of the voltage is close to 0,
close to the value of 0 (c) and,
and the value is close to 1, and a larger system damping can be obtained by using the positive virtual resistor at the moment, so that the resonance inhibiting capability is stronger, namely, the effect of inhibiting the common mode current is better. When the temperature is higher than the set temperature
Approach to
When the temperature of the water is higher than the set temperature,
approaching 1, where the use of a virtual inductor or a virtual capacitor can produce greater system damping. Therefore, a =0, B may be made as needed<0 or A>0, B =0, or a>0，B<0, etc., i.e. only R needs to be satisfied0And at least one of a and B is not 0, the purpose of suppressing the common mode current can be achieved.
In an embodiment, the step 403 of controlling the imaginary part of the system impedance to be smaller than the first preset threshold value to determine the resonance angular frequency specifically includes the following steps:
step 601: the imaginary part of the system impedance is defined as a first function and the first function is differentiated to obtain a second function.
Step 602: an initial resonance angular frequency is calculated from the characteristic values of the electronic components in the inverter.
In the following description, the first impedance includes a first resistor, that is, a ═ B ═ 0.
Combining formula (9), formula (10) and i.e. a ═ B ═ 0, we can obtain:
as can be seen from equation (11), when the resonance frequency is low, that is
The first impedance has stronger resistance, and can obviously improve the system damping. When in use
Approach to
In time, the virtual resistor mainly represents a capacitor, and has a small effect on improving the damping of the system.
Further, the resistance value R of the first resistor is not changed under other conditions0And increasing, the resonant frequency will increase. And, at the new resonance frequency, when
Is greater than
At this time, the first impedance generates negative damping, which deteriorates system performance. There is an optimal parameter for the resistance R0 of the first resistor to more effectively improve the system damping, i.e. to better suppress the common mode current.
The specific process is that, firstly, the imaginary part of the system impedance in the formula (11) is defined as a first function, and differential operation is performed on the first function to obtain a second function, which can be obtained as follows:
wherein, the first and the second end of the pipe are connected with each other,
in order to be a function of the first function,
is a second function.
Then, the initial resonance angular frequency can be calculated and obtained according to the characteristic value of the electronic component in the inverter. In one embodiment, the initial resonant angular frequency may be obtained according to the following equation:
the characteristic values of the electronic components in the inverter include inductance L of the inverter inductor and capacitance C of the filter capacitorf。
Step 603: and determining the resonance angular frequency according to the initial resonance angular frequency, the first function and the second function.
Specifically, in an embodiment, the step 603 specifically includes the following steps: firstly, setting the value of the first impedance as a first value, respectively substituting the first value and the initial resonance angular frequency into a first function and a second function for calculation, and judging whether the absolute value of the calculation result of the first function is smaller than a second preset threshold value. And if the absolute value of the calculation result of the first function is smaller than a second preset threshold, taking the current resonance angular frequency as the final resonance angular frequency. If the absolute value of the calculation result of the first function is not less than the second preset threshold, respectively substituting the current resonance angular frequency, the difference value between the first numerical value and the ratio between the first function and the second function into the first function and the second function for calculation, and performing judgment again to determine whether the absolute value of the calculation result of the first function is less than the second preset threshold. Similarly, if the absolute value of the calculation result of the first function is smaller than the second preset threshold, the current resonance angular frequency is used as the final resonance angular frequency. And continuously repeating the steps until the absolute value of the calculation result of the first function is smaller than a second preset threshold value, and determining the final resonance angular frequency.
The first value is a given value, and may be set correspondingly according to different application situations, which is not specifically limited in the embodiments of the present application. At the same time, it is understood that given different first values according to different applications, the resulting calculated resonance angular frequency should be the same or close to the same.
In addition, the second preset threshold may be set according to an actual application situation, and the embodiment of the present application does not specifically limit this. For example, in one embodiment, the second predetermined threshold may be set to 0.001 to obtain a more accurate resonant angular frequency.
The following description will be made by taking an example in which the first impedance includes the first resistor.
Referring to FIG. 7, the initial resonant angular frequency is calculated
Then, the first value is compared with
Are all substituted into the formula (12) and the formula (13) and can be calculated and obtained
And with
The value of (c). Then, judge
Is less than a second preset threshold. If it is not
Is less than a second preset threshold value, the initial resonance angular frequency at that time
I.e. the new resonance angular frequency, i.e. the final desired resonance angular frequency. If, however, there is a
Is not less than a second preset threshold value, then the absolute value of
And
is calculated, and the current resonance angular frequency (in this case, the initial resonance angular frequency) is calculated
And the difference between the first ratio and the second ratio.
Then, the difference (denoted as the first resonance angular frequency) is calculated
) Substituting the formula (12) and the formula (13) again, and calculating to obtain
And
the value of (c). Likewise, the judgment is continued on what is obtained at this time
Is less than a second preset threshold. If it is not
Is less than a second predetermined threshold, the first resonant angular frequency at that time
I.e. the new resonance angular frequency, i.e. the final desired resonance angular frequency. If, however, there is a
Is not less than a second preset threshold value, then the absolute value of
And
and calculating the current resonance angular frequency (in this case, the first resonance angular frequency)
And the difference between the second ratio.
Then, the difference is substituted into the formula (12) and the formula (13) again, and the calculation result is obtained
And
the value of (c). Repeating the above process until the requirement is met
Is smaller than a second preset threshold value to obtain the final desired resonance angular frequency.
Step 404: and determining the system impedance and the system damping ratio according to the resonance angular frequency so as to determine the size of the parameter of the first impedance.
After the final resonance angular frequency is obtained, the system impedance to system damping ratio may be further determined according to the resonance angular frequency.
In one embodiment, when the first impedance includes only the first resistor, the system impedance to system damping ratio may satisfy the following equation:
wherein R issysAs the impedance of the system is to be,
is the system damping ratio.
In this embodiment, after the electronic components of the inverter are all determined, if the resonant angular frequency is also determined, then R and
can be considered to be a known value. The system impedance can be obtained by equation (15)A first curve of the variation of the first resistance, and a second curve of the system damping ratio as a function of the first resistance can be obtained by equation (16). According to the first curve and the second curve, the resistance value R0 of the first resistor can be determined.
Fig. 8 shows a schematic diagram of a first curve and a second curve, where in this exemplary embodiment a = B =0, L =1mH, Cf=10uF，R=0.1Ω，Ts=5e-5s，α=1，
。
As shown in FIG. 8, the resistance R of the first resistor can be obtained from the first curve and the second curve0Between 12 and 16, a larger system impedance and system damping ratio can be obtained. In other words, in this embodiment, to obtain a larger system impedance and system damping ratio, R may be used0Is set to [12,16 ]]To obtain better effect of suppressing the common mode current.
Referring to fig. 9, fig. 9 shows the resistance R of the first resistor when a = B =00The system admittance curves at 0 and 12, respectively, where the system admittance is the inverse of the system impedance. As shown in fig. 9, the resistance value R0Peak value of system admittance at 12 hours relative to resistance value R0A peak in the system admittance at 0, moving towards an increase in frequency, indicates that the actual resonant frequency is greater. At the same time, the resistance value R0The peak value of the system admittance is far less than the resistance value R at 120The peak value of the system admittance at 0 indicates that the resonance oscillation is suppressed, that is, the common mode current can be suppressed by adopting the scheme provided by the embodiment of the application.
Referring to fig. 10 and 11 together, fig. 10 shows that a = B =0 and the resistance R0When the current is 0, the current flows through an inverter inductor (comprising an inverter inductor L)1Inverter inductor L2And an inverter inductance L3) The current value of (1). Fig. 11 shows that a = B =0 and the resistance value R0Flowing through an inverter inductor (including an inverter inductor L) at 12 hours1Inverter inductor L2And an inverter inductance L3) The current value of (2).
As shown in FIGS. 10 and 11, the resistance R0At 12 (equivalent to adding resistance R at this time)012 first resistance) of the current flowing through the inverter inductance, there is almost no harmonic of the frequency of oscillation, and the resistance value R0When the current value is 0 (corresponding to that the first resistor is not added), a large harmonic of the oscillation frequency number exists on the current value flowing through the inverter inductor. Therefore, by adding the first resistor, the harmonic of the original oscillation frequency number can be eliminated, so that the quality of the waveform is improved, which means that the common mode current can be suppressed by adopting the scheme provided by the embodiment of the application.
Please refer to FIG. 12 and FIG. 13, wherein FIG. 12 shows the symbol at R0= B =0, and a is 0, and flows through the inverter inductance (including the inverter inductance L)1Inverter inductor L2And an inverter inductance L3) The current value of (1). Shown in FIG. 13 at R0Flows through the inverter inductor (including the inverter inductor L) when a is 0.0001, and B =01Inverter inductor L2And an inverter inductance L3) The current value of (1). Wherein, in this embodiment, R0=B=0，L=300uH，Cf=10uF，R=0.1Ω，Ts=5e-5s，α=1.5，
Approach to
。
As shown in fig. 12 and 13, when a is 0.0001 (corresponding to the case where the first inductor having an inductance value of 0.0001 is added), the current flowing through the inverter inductor has almost no harmonic of the oscillation frequency, and when a is 0 (corresponding to the case where the first inductor is not added), the current flowing through the inverter inductor has a large harmonic of the oscillation frequency. Therefore, the first inductor is added, so that the harmonic of the original oscillation frequency can be eliminated, the waveform quality is improved, and the common mode current is restrained.
Step 303: and driving the switching tube according to the common mode voltage rejection component.
The magnitude of each parameter in the first impedance can be determined through the above embodiments, so that the magnitude of the common mode voltage rejection component can be further determined. Then, in the working process of the inverter, because the switching process of the switching tube can realize the control of the common mode current, the switching tube is driven by combining the common mode voltage suppression component, and the suppression process of the common mode current can be realized.
In an embodiment, during the operation of the inverter, the signal for driving the switching tube includes not only the common mode voltage rejection component, but also the inversion voltage and the zero sequence component of each phase of the inverter. That is, the driving the switch tube according to the common mode voltage rejection component in step 303 may specifically include the following methods: and driving the switching tube according to the inversion voltage, the zero sequence component and the common mode voltage suppression component of each phase of the inverter.
As shown in fig. 14, in this embodiment, since the inversion voltage and the zero sequence component to each phase of the inverter need to be used, the driving method of the switching tube should further include the following steps:
step 1401: and acquiring the voltage of the power grid, and determining the angle of the voltage of the power grid according to the voltage of the power grid.
In an embodiment, if the inverter comprises a three-phase inverter circuit as shown in fig. 1, the voltage comprises the first grid voltage eaSecond grid voltage ebTo a third network voltage ec。
Step 1402: and obtaining the inversion voltage of each phase of the inverter based on the angle of the grid voltage and the current of each phase of the inverter.
The current of each phase of the inverter is the current in abc coordinates, and taking the circuit structure shown in fig. 1 as an example, the current of each phase of the inverter includes the first phase current i in abc coordinatesLaSecond phase current iLbWith a third phase current iLc。
In an embodiment, the specific implementation process of step 902 is: and converting the current of each phase of the inverter through an abc/dq coordinate system based on the angle of the grid voltage and the current of each phase of the inverter to obtain the current in the dq coordinate system. And obtaining the inversion voltage in the dq coordinate system according to the current in the dq coordinate system. And transforming the inverted voltage in the dq coordinate system through a dq/abc coordinate system to obtain the inverted voltage of each phase in the abc coordinate system, wherein the inverted voltage of each phase in the abc coordinate system is the inverted voltage of each phase of the inverter.
Specifically, a circuit configuration shown in fig. 1 will be described as an example.
Firstly, on the premise of acquiring the angle of the power grid voltage, three-phase currents (including a first phase current i) in an abc coordinate system are subjected to angle matching based on the angle of the power grid voltageLaSecond phase current iLbWith a third phase current iLc) The first current id and the second current iq in the dq coordinate system are converted through abc/dq coordinate system transformation. Wherein the abc/dq coordinate system transformation means converting a parameter in the abc coordinate system into a parameter in the dq coordinate system. And then, obtaining a first inversion voltage Ud and a second inversion voltage Uq under the dq coordinate system according to the first current id and the second current iq under the dq coordinate system. And then, obtaining a first inversion voltage Ua, a second inversion voltage Ub and a third inversion voltage Uc under the abc coordinate system by performing inverse coordinate change (namely dq/abc coordinate system transformation) on the first inversion voltage Ud and the second inversion voltage Uq. The first inversion voltage Ua, the second inversion voltage Ub and the third inversion voltage Uc in the abc coordinate system are inversion voltages of each phase of the inverter, that is, the inversion voltage of the first phase is the first inversion voltage Ua in the abc coordinate system, the inversion voltage of the second phase is the second inversion voltage Ub in the abc coordinate system, and the inversion voltage of the third phase is the third inversion voltage Uc in the abc coordinate system.
Step 1403: and calculating a zero sequence component according to the inversion voltage and the modulation strategy of each phase of the inverter.
In this embodiment, the Modulation strategy may be SVPWM (Space Vector Pulse Width Modulation), DPWM (Discontinuous Pulse Width Modulation), or the like, which is not specifically limited in this embodiment. The SVPWM is adopted to improve the utilization rate of the bus voltage; the DPWM can reduce the loss of the switching tube, and further improve the overall efficiency of the inverter.
In one embodiment, if the modulation strategy is SVPWM modulation, the zero sequence component is a negative value of half of the sum of the maximum value and the minimum value of each phase of the inverter. Still taking the circuit structure shown in fig. 1 as an example, according to the above embodiment, the three-phase inverter voltage of the inverter includes the first inverter voltage Ua, the second inverter voltage Ub, and the third inverter voltage Uc in the abc coordinate system, the maximum value and the minimum value among the first inverter voltage Ua, the second inverter voltage Ub, and the third inverter voltage Uc in the abc coordinate system are obtained, and the zero sequence component can be obtained by summing the maximum value and the minimum value and multiplying the sum by-0.5. For example, in an embodiment, the first inverse voltage Ua in the abc coordinate system is a maximum value, and the third inverse voltage Uc in the abc coordinate system is a minimum value, then the zero-sequence component is:
furthermore, after determining the inversion voltage, the zero sequence component and the common mode voltage suppression component of each phase of the inverter, in an embodiment, the inversion voltage, the zero sequence component and the common mode voltage suppression component of each phase of the inverter are added, and then the corresponding pulse width modulation signal is output according to the result obtained by the addition. The pulse width modulation signal is used for driving a switching tube in the inverter so as to realize the purpose of inhibiting the common mode current of the inverter while keeping the normal work of the inverter.
The embodiment of the application provides a driving device of a switching tube, which is applied to an inverter. Referring to fig. 15, which shows a schematic structural diagram of a driving apparatus of a switching tube according to an embodiment of the present application, the driving apparatus 1500 of the switching tube includes: a common mode current calculating module 1501, a common mode current suppressing module 1502 and a driving module 1503.
The common mode current calculation module 1501 is configured to obtain a current of each phase of the inverter, and determine a common mode current of the inverter according to an average value of the currents.
The common mode current rejection module 1502 is configured to determine a common mode voltage rejection component of the inverter according to the common mode current and a first impedance, where the first impedance includes at least one of a first resistor, a first inductor, and a first capacitor, and the common mode voltage rejection component is configured to reject the common mode current.
The driving module 1503 is configured to drive the switching tube according to the common mode voltage rejection component.
In an embodiment, as shown in fig. 16, the driving apparatus 1500 further includes a parameter calculating module 1504, a pll module 1505, a coordinate transforming module 1506, an output current controlling module 1507, an anti-coordinate transforming module 1508, and a zero sequence component injecting module 1509.
The parameter calculating module 1504 is used for calculating parameters of the first impedance, wherein the parameters of the first impedance include R0A and B. The phase-locked loop module 1505 is used for obtaining the grid voltage, determining the angle of the grid voltage according to the grid voltage, and inputting the angle of the grid voltage to the coordinate transformation module 1506, wherein the grid voltage comprises a first grid voltage eaSecond grid voltage ebTo a third network voltage ec. The coordinate transformation module 1506 is configured to transform the current of each phase of the inverter through an abc/dq coordinate system based on the angle of the grid voltage and the current of each phase of the inverter to obtain a current in the dq coordinate system, where the current of each phase of the inverter includes a first phase current iLaSecond phase current iLbWith a third phase current iLcThe current in dq coordinate system includes a first current id and a second current iq. The output current control module 1507 is configured to obtain an inverted voltage in the dq coordinate system according to a current in the dq coordinate system, and specifically, calculate a first difference between a first preset current id1 and the first current id, calculate a second difference between a second preset current iq1 and the second current iq, and obtain an inverted voltage in the dq coordinate system according to the first difference and the second difference, where the inverted voltage in the dq coordinate system includes a first inverted voltage Ud and a second inverted voltage Uq in the dq coordinate system. The inverse coordinate transformation module 1508 is configured to, after obtaining the first inverse voltage Ud and the second inverse voltage Uq in the dq coordinate system, transform the inverse voltage in the dq coordinate system through the dq/abc coordinate system to obtain an inverse voltage of each phase in the abc coordinate system, where the first inverse voltage Ua, the second inverse voltage Ub, and the third inverse voltage Uc in the abc coordinate system are each of the invertersThe inverted voltage of the phase. The zero sequence component injection module 1509 is configured to calculate a zero sequence component according to the inverter voltage and the modulation strategy of each phase of the inverter, and inject the zero sequence component into the driving module 1503. The driving module 1503 is further configured to output a pulse width modulation signal according to the first inverse voltage Ua, the second inverse voltage Ub, the third inverse voltage Uc, the zero-sequence component, and the common-mode voltage suppression component in the abc coordinate system, so as to drive each switching tube in the inverter according to the pulse width modulation signal.
The product can execute the method provided by the embodiment of the application shown in fig. 3, and has corresponding functional modules and beneficial effects of the execution method. For technical details that are not described in detail in this embodiment, reference may be made to the methods provided in the embodiments of the present application.
Referring to fig. 17, a control processing apparatus 1700 includes: at least one processor 1701; and a memory 1702 communicatively coupled to at least one processor 1701, such as the one processor 1701 in FIG. 17. The memory 1702 stores instructions executable by the at least one processor 1701 to enable the at least one processor 1701 to perform the method for driving a switch tube described above with respect to FIG. 3. The processor 1701 and the memory 1702 may be connected by a bus or other means, and the bus connection is illustrated in fig. 17 as an example.
The memory 1702, which is a non-volatile computer-readable storage medium, may be used to store non-volatile software programs, non-volatile computer-executable programs, and modules, such as program instructions/modules corresponding to the driving method of the switching tube in the embodiment of the present application, for example, the respective modules shown in fig. 15 or fig. 16. The processor 1701 executes various functional applications of the server and data processing, i.e., a driving method of the switching tube implementing the above-described method embodiments, by executing nonvolatile software programs, instructions, and modules stored in the memory 1702.
The memory 1702 may include a program storage area and a data storage area, wherein the program storage area may store an operating system, an application program required for at least one function; the storage data area may store data created according to use of the data transmission apparatus, and the like. Additionally, the memory 1702 may include high speed random access memory, and may also include non-volatile memory, such as at least one magnetic disk storage device, flash memory device, or other non-volatile solid state storage device. In some embodiments, the memory 1702 may optionally include memory located remotely from the processor 1701, and such remote memory may be coupled to the data transfer device via a network. Examples of such networks include, but are not limited to, the internet, intranets, local area networks, mobile communication networks, and combinations thereof.
The one or more modules are stored in the memory 1702 and, when executed by the one or more processors 1701, perform the method for driving a switching tube in any of the method embodiments described above, e.g., the method steps of fig. 3 described above, to implement the functions of the modules in fig. 15.
The product can execute the method provided by the embodiment of the application, and has the corresponding functional modules and beneficial effects of the execution method. For technical details that are not described in detail in this embodiment, reference may be made to the methods provided in the embodiments of the present application.
Embodiments of the present application also provide a non-transitory computer-readable storage medium storing computer-executable instructions for execution by one or more processors, for example, to perform the method steps of fig. 3, 4, 6, 7, and 14 described above and to implement the functions of the modules in fig. 15 and 16.
Embodiments of the present application further provide a computer program product comprising a computer program stored on a non-volatile computer-readable storage medium, the computer program comprising program instructions that, when executed by a computer, cause the computer to perform the method for driving a switching tube in any of the above-described method embodiments, for example, to perform the method steps of fig. 3, fig. 4, fig. 6, fig. 7, and fig. 14 described above, and to implement the functions of the respective modules in fig. 15 and fig. 16.
Finally, it should be noted that: the above embodiments are only used to illustrate the technical solutions of the present application, and not to limit the same; within the context of the present application, where technical features in the above embodiments or in different embodiments may also be combined, the steps may be implemented in any order and there are many other variations of the different aspects of the present application described above which are not provided in detail for the sake of brevity; although the present application has been described in detail with reference to the foregoing embodiments, it should be understood by those of ordinary skill in the art that: the technical solutions described in the foregoing embodiments may still be modified, or some technical features may be equivalently replaced; and the modifications or the substitutions do not make the essence of the corresponding technical solutions depart from the scope of the technical solutions of the embodiments of the present application.
Claims (12)
1. A driving method of a switching tube is characterized by being applied to an inverter, and the method comprises the following steps:
obtaining the current of each phase of the inverter, and determining the common-mode current of the inverter according to the average value of the currents;
determining a common mode voltage rejection component of the inverter by:
obtaining a common-mode voltage of the inverter;
determining a system impedance of the inverter according to the common mode voltage and the common mode voltage rejection component;
controlling the imaginary part of the system impedance to be smaller than a first preset threshold value so as to determine a resonance angular frequency;
determining the system impedance from the resonance angular frequencyAnd system damping ratio to determine a magnitude of a parameter of the first impedance, wherein the parameter of the first impedance comprises R0A and B;
and driving the switch tube according to the common mode voltage rejection component.
2. The method of claim 1, wherein said controlling the imaginary part of the system impedance to be less than a first preset threshold to determine a resonant angular frequency comprises:
defining the imaginary part of the system impedance as a first function, and carrying out differential operation on the first function to obtain a second function;
calculating an initial resonance angular frequency according to the characteristic values of the electronic components in the inverter;
and determining the resonance angular frequency according to the initial resonance angular frequency, the first function and the second function.
3. The method of claim 2, wherein determining the resonant angular frequency from the initial resonant angular frequency, the first function, and the second function comprises:
setting a value of the first impedance to a first value;
respectively substituting the first numerical value and the initial resonance angular frequency into the first function and the second function for calculation;
judging whether the absolute value of the calculation result of the first function is smaller than a second preset threshold value or not;
if so, taking the current resonance angular frequency as the resonance angular frequency;
if not, calculating a ratio between the first function and the second function, calculating a difference between the current resonance angular frequency and the ratio, respectively substituting the first value and the difference into the first function and the second function for calculation, and judging whether the absolute value of the calculation result of the first function is smaller than a second preset threshold value or not.
4. The method of claim 1, wherein determining the system impedance to system damping ratio from the resonant angular frequency to determine a magnitude of a parameter of the first impedance comprises:
when a = B =0, the signal is transmitted,
according to
Determining a first curve of the system impedance as a function of the first resistance, wherein RsysR is the total loop resistance of the inverter,
for the said resonant angular frequency, the frequency of the resonance,
for delay factor, TsControlling the cycle for the controller;
according to
Determining a second curve of the system damping ratio as a function of the first resistance, wherein
L is the inductance value of the inverter inductor, wherein the system damping ratio is L;
determining R according to the first curve and the second curve0The size of (2).
5. The method of claim 1, further comprising:
acquiring a power grid voltage, and determining an angle of the power grid voltage according to the power grid voltage;
obtaining an inversion voltage of each phase of the inverter based on the angle of the grid voltage and the current of each phase of the inverter;
calculating a zero sequence component according to the inversion voltage and the modulation strategy of each phase of the inverter;
the driving the switching tube according to the common mode voltage rejection component includes:
and driving the switching tube according to the inversion voltage, the zero sequence component and the common mode voltage rejection component of each phase of the inverter.
6. The method of claim 5, wherein obtaining the inverted voltage of each phase of the inverter based on the angle of the grid voltage and the current of each phase of the inverter comprises:
converting the current of each phase of the inverter through an abc/dq coordinate system based on the angle of the grid voltage and the current of each phase of the inverter to obtain the current under the dq coordinate system;
obtaining an inversion voltage under the dq coordinate system according to the current under the dq coordinate system;
and transforming the inverted voltage in the dq coordinate system through a dq/abc coordinate system to obtain the inverted voltage of each phase in the abc coordinate system, wherein the inverted voltage of each phase in the abc coordinate system is the inverted voltage of each phase of the inverter.
7. The method of claim 5, wherein the calculating a zero sequence component according to the inverter voltage and modulation strategy of the inverter comprises:
and if the modulation strategy is SVPWM, the zero-sequence component is a negative value of half of the sum of the maximum value and the minimum value in each phase of the inverter.
8. The method of claim 5, wherein the driving the switching tube according to the inverted voltage, the zero sequence component and the common mode voltage rejection component of each phase of the inverter comprises:
outputting a pulse width modulation signal according to the sum of the inversion voltage of each phase of the inverter, the zero sequence component and the common mode voltage suppression component;
and driving the switch tube according to the pulse width modulation signal.
9. A driving device of a switching tube is applied to an inverter, and the device comprises:
the common-mode current calculation module is used for acquiring the current of each phase of the inverter and determining the common-mode current of the inverter according to the average value of the currents;
a common mode current rejection module for determining a common mode voltage rejection component of the inverter by:
obtaining a common-mode voltage of the inverter;
determining a system impedance of the inverter according to the common mode voltage and the common mode voltage rejection component;
controlling the imaginary part of the system impedance to be smaller than a first preset threshold value so as to determine a resonance angular frequency;
determining the system impedance and the system damping ratio according to the resonance angular frequency to determine the size of the parameter of the first impedance, wherein the parameter of the first impedance comprises R0A and B;
and the driving module is used for driving the switching tube according to the common-mode voltage rejection component.
10. A control processing apparatus characterized by comprising:
at least one processor and a memory communicatively coupled to the at least one processor, the memory storing instructions executable by the at least one processor to enable the at least one processor to perform the method of any of claims 1-8.
11. An inverter, characterized by comprising at least one phase inverter circuit and the control processing device according to claim 10;
the inverter circuit comprises at least one switching tube, and the control processing device is used for outputting pulse width modulation signals to drive the switching tube.
12. A non-transitory computer-readable storage medium storing computer-executable instructions that, when executed by a processor, cause the processor to perform the method of any one of claims 1-8.
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