CN114264877A - Sine wave phase difference accurate measurement circuit and measurement method thereof - Google Patents
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Abstract
The invention discloses a sine wave phase difference accurate measurement circuit and a measurement method thereof, wherein the device comprises a first branch circuit and a second branch circuit, the first branch circuit comprises a first coupler, a first AGC amplitude automatic gain controller, a numerical control phase shifter, an AD8302 phase difference measurement module and a measurement result processing module which are sequentially connected, the second branch circuit comprises a second coupler, a second AGC amplitude automatic gain controller, an AD8302 phase difference measurement module and a measurement result processing module which are sequentially connected, wherein the first branch circuit and the second branch circuit share the AD8302 phase difference measurement module and the measurement result processing module, the output of the second AGC amplitude automatic gain controller is directly connected to the AD8302 phase difference measurement module, and a CPU (Central processing Unit) of the measurement result processing module is also electrically connected with the numerical control phase shifter. The circuit is an embedded circuit, the cost is low, the size is small, the practicability is high, and the method is high in measuring speed and accuracy.
Description
Technical Field
The invention relates to an accurate measurement technology of communication electric waves, in particular to a circuit and a method for accurately measuring sine wave phase difference.
Background
In the field of communications, almost all signals are transmitted by electric waves, wherein transmission of a sine wave is used as the most basic signal for a carrier wave of a radio wave, a clock local oscillator of a large electronic system, and the like. Because of the extremely wide bandwidth of optical communication transmission, more and more radio frequency signals are directly transmitted by optical fibers. For example, in the transmitting and receiving of phased array radar, the receiving of multipath short wave antenna signals, the receiving of satellite signals and the like, the A/D, D/A conversion is not needed when the long-distance transmission is carried out, and radio frequency signals can be directly modulated into optical fibers for transmission. In a transmission system of multiple radio frequency signals, the phase is an important index, some signals require the phase of the multiple signals to be consistent, some signals require a fixed phase difference, or when the phase between the signals drifts, the phases need to be measured in time for calibration. At present, the phase of a measuring signal is large, and a multi-purpose special instrument is used, but the special instrument is generally large in size and is not suitable for real-time monitoring and mobile measurement. It is therefore necessary to perform accurate, embedded phase difference measurements at the end of the signal transmission.
Disclosure of Invention
The invention aims to provide a sine wave phase difference accurate measurement circuit and a measurement method thereof, aiming at the defects of the prior art. The circuit is an embedded circuit, the cost is low, the size is small, the practicability is high, and the method is high in measuring speed and accuracy.
The technical scheme for realizing the purpose of the invention is as follows:
a sine wave phase difference accurate measurement circuit comprises a first branch circuit and a second branch circuit, wherein the first branch circuit comprises a first coupler, a first AGC amplitude automatic gain controller, a numerical control phase shifter, an AD8302 phase difference measurement module and a measurement result processing module which are sequentially connected, the second branch circuit comprises a second coupler, a second AGC amplitude automatic gain controller, an AD8302 phase difference measurement module and a measurement result processing module which are sequentially connected, the first branch circuit and the second branch circuit share the AD8302 phase difference measurement module and the measurement result processing module, the output of the second AGC amplitude automatic gain controller is directly connected into the AD8302 phase difference measurement module, a measurement result processing module cpu is also electrically connected with the numerical control phase shifter, the phase difference of two signals of the first branch circuit and the second branch circuit is measured by adopting a phase shifting mode, and the defects of binary property, nonlinearity and error imbalance of a measurement chip are eliminated, the positive and negative phase shifting can be realized by adopting the numerical control phase shifter, the measurement result of the AD8302 is fed back, the moving direction and the size of the numerical control phase shifter are controlled, a nonlinear area of a phase measurement chip is avoided, the binary property is removed, the error imbalance is avoided, the AD8302 measures the phase difference of two paths of measured signals and transmits the phase difference to a measurement result processing module in the form of a voltage value, 12-bit A/D conversion is carried out to obtain a digital measurement result, an actual measurement phase difference angle value is obtained after calculation, and the digital measurement result and the actual measurement phase difference angle value can be directly uploaded to an upper computer for processing or directly sent to a phase control circuit for controlling the phase in real time.
The first coupler and the second coupler are both low-coupling-degree and low-insertion-loss couplers, so that the communication of main channel signals is not influenced by a measuring result.
The AGC amplitude automatic gain controller limits the amplitude of the measured signal to be within an acceptable range of AD8302 and keeps the amplitude unchanged.
A sine wave phase difference accurate measurement method comprises the sine wave phase difference accurate measurement circuit, and comprises the following steps:
1) setting the degree of the phase shifter to be 0, recording the original voltage value of the phase difference of the first branch signal B and the second branch signal A as M0 through AD8302, and recording the original phase difference of two branches corresponding to M0 as theta degree, wherein theta has positive and negative possible values;
2) controlling the numerical control phase shifter to increase the phase of the first branch signal B by 21 degrees, and recording the voltage value measured by the AD8302 as M1;
3) setting the degree of a phase shifter to be 0, and restoring the phase of the first branch signal B to the initial phase;
4) controlling the numerical control phase shifter to reduce the phase of the first branch signal B by 21 degrees, and recording the voltage value measured by AD8302 as M2;
5) the absolute value of the difference between M1 and M0 and the absolute value of the difference between M2 and M0 are obtained through calculation, the direction with a larger absolute value is used as a judgment basis to judge the increase slope of the phase difference, so that whether theta is positive or negative is known, and the accurate value of theta is measured but not necessarily an accurate value;
6) if theta is not in the range of +/-60 degrees and 120 degrees, the measured voltage value M0 has larger error, at the moment, the numerical control phase shifter is controlled to increase the degree of the first branch signal B by delta theta, the purpose is to move the phase difference between the first branch signal B and the second branch signal A to the range of +/-60 degrees and 120 degrees, and at the moment, the phase difference value is changed into theta + delta theta;
7) due to the difference of measurement errors after interval transformation, at this time, the phase difference value between the first branch signal B and the second branch signal a needs to be measured again through the AD8302, and the final phase difference voltage is M3, the degree corresponding to M3 at this time is denoted as θ ', θ' = θ + Δ θ, because θ 'is within a range of ± (60 ° and 120 °), the error is small, and is a relatively accurate value, and because Δ θ is also an accurate value, the original value "θ = θ' - Δ θ" is also an accurate value.
Through the steps, the problems of nonlinearity and error imbalance of the measurement result are solved, and the measurement result is more accurate.
Compared with the prior art, the technical scheme has the following advantages:
1) the circuit is an embedded circuit, has small volume and can be easily embedded into various use occasions compared with a heavy measuring instrument;
2) the transmission of the measured main signal is not influenced, the phase change of the main signal can be monitored and reflected in real time, and a judgment basis is provided for a subsequent circuit;
3) the measurement precision is higher, and theoretically, the measurement precision can reach 0.228 degrees by using 12-bit A/D sampling;
4) compared with the direct measurement by using the AD8302 chip, the method eliminates the measurement defects and has more accurate and precise measurement results.
The circuit is an embedded circuit, the cost is low, the size is small, the practicability is high, and the method is high in measuring speed and accuracy.
Drawings
Fig. 1 is a phase difference measurement response graph of AD8302 in the embodiment;
FIG. 2 is a diagram showing a relationship between phase difference measurement errors of the AD8302 in the embodiment;
FIG. 3 is a schematic circuit diagram of an embodiment;
FIG. 4 is a schematic diagram of a modified scheme of phase difference measurement in the embodiment;
FIG. 5 is a schematic diagram showing a correction scheme of the phase difference measurement result in the embodiment.
Detailed Description
The invention will be further elucidated with reference to the drawings and examples, without however being limited thereto.
Example (b):
referring to fig. 3, a sine wave phase difference accurate measurement circuit includes a first branch and a second branch, the first branch includes a first coupler, a first AGC amplitude automatic gain controller, a digital control phase shifter, an AD8302 phase difference measurement module and a measurement result processing module which are connected in sequence, the second branch includes a second coupler, a second AGC amplitude automatic gain controller, an AD8302 phase difference measurement module and a measurement result processing module which are connected in sequence, wherein the first branch and the second branch share the AD8302 phase difference measurement module and the measurement result processing module, an output of the second AGC amplitude automatic gain controller is directly connected to the AD8302 phase difference measurement module, and a measurement result processing module cpu is further electrically connected to the digital control phase shifter, measures a phase difference between two signals of the first branch and the second branch by using a phase shifting manner, and eliminates an inherent binary property of a measurement chip, The defects of nonlinearity and error imbalance are that positive and negative phase shifting can be realized by adopting the numerical control phase shifter, the moving direction and the size of the numerical control phase shifter are controlled by feeding back the measurement result of the AD8302, the nonlinear area of a phase measurement chip is avoided, the binary property is removed, the error imbalance is avoided, the AD8302 measures the phase difference of two paths of measured signals, the phase difference is transmitted to a measurement result processing module in the form of a voltage value, 12-bit A/D conversion is carried out to obtain a digital measurement result, an actual measurement value is obtained after calculation, and the digital measurement result and the actual measurement value can be directly uploaded to an upper computer for processing or directly sent to a phase control circuit for controlling the phase in real time.
The first coupler and the second coupler are both low-coupling-degree and low-insertion-loss couplers, so that the communication of main channel signals is not influenced by a measuring result.
The AGC amplitude automatic gain controller limits the amplitude of the measured signal to be within an acceptable range of AD8302 and keeps the amplitude unchanged.
A sine wave phase difference accurate measurement method comprises the sine wave phase difference accurate measurement circuit, and comprises the following steps:
1) setting the degree of the phase shifter to be 0, recording the original voltage value of the phase difference of the first branch signal B and the second branch signal A as M0 through AD8302, and recording the original phase difference of two branches corresponding to M0 as theta degree, wherein theta has positive and negative possible values;
2) controlling the numerical control phase shifter to increase the phase of the first branch signal B by 21 degrees, and recording the voltage value measured by the AD8302 as M1;
3) setting the degree of a phase shifter to be 0, and restoring the phase of the first branch signal B to the initial phase;
4) controlling the numerical control phase shifter to reduce the phase of the first branch signal B by 21 degrees, and recording the voltage value measured by AD8302 as M2;
5) the absolute value of the difference between M1 and M0 and the absolute value of the difference between M2 and M0 are obtained through calculation, the direction with a larger absolute value is used as a judgment basis to judge the increase slope of the phase difference, so that whether theta is positive or negative is known, and the accurate value of theta is measured but not necessarily an accurate value;
6) if theta is not in the range of +/-60 degrees and 120 degrees, the measured voltage value M0 has larger error, at the moment, the numerical control phase shifter is controlled to increase the degree of the first branch signal B by delta theta, the purpose is to move the phase difference between the first branch signal B and the second branch signal A to the range of +/-60 degrees and 120 degrees, and at the moment, the phase difference value is changed into theta + delta theta;
7) due to the difference of measurement errors after interval transformation, at this time, the phase difference value between the first branch signal B and the second branch signal a needs to be measured again through the AD8302, and the final phase difference voltage is M3, the degree corresponding to M3 at this time is denoted as θ ', θ' = θ + Δ θ, because θ 'is within a range of ± (60 ° and 120 °), the error is small, and is a relatively accurate value, and because Δ θ is also an accurate value, the original value "θ = θ' - Δ θ" is also an accurate value.
Simulation experiment:
the measurement chip adopted in the experiment is AD8302 of Adenoda, the measurement frequency range of the chip is LP-2.7 GHz, the amplitude range of input signals is-60 dBm-0 dBm, the phase difference detection range is 0-180 degrees, the corresponding output voltage variation range is 0V-1.8V, the output voltage sensitivity is 10 mV/degree, the measurement error is less than 0.5 degrees, and when the phase difference delta phi =0 degrees, the output voltage is 1.8V; when Δ Φ =180 °, the output voltage is 30 mV.
As shown in fig. 1, the measured graphs of the input signal amplitude of-30 dBm and the input frequencies of 100MHz, 900MHz, 1900MHz, 2200MHz, and 2700MHz respectively show that the same output voltage value corresponds to two different phases, for example, the output voltage of 0.8V, which respectively corresponds to two phases of-100 ° and 100 °, which is binary, meaning that the result obtained by direct measurement with the chip is equivalent to taking an absolute value for two-way phase differences, and it cannot be directly determined which way has a larger phase and which way has a smaller phase, in addition, the corresponding curves of the frequencies are slightly different and are concentrated between the phase difference ranges of (-20 °,20 °) and (+/-160 °,180 °), where the curve bending of the measurement result of each frequency is not linear, and the linearity of the curves measured only between +/- (20 °), and (160 °) are still relatively consistent, this is a problem of measurement non-linearity;
as shown in fig. 2, the phase difference measurement result corresponding to a signal with an input amplitude of-30 dBm and a frequency of 2200MHz is represented, wherein the abscissa represents the phase difference, the left ordinate is the same as that in fig. 4, the output measurement result voltage, and the right ordinate is the magnitude of the error corresponding to the measurement of each phase difference, it can be seen from the abscissa and the right ordinate that the measurement error of the measurement result between ± ± 60 ° and 120 ° is close to 0, which is the minimum error interval, and the measurement error gradually increases beyond this range, so that the AD8302 has a problem of measurement error imbalance.
In this example, the coupler with a relatively low coupling couples the signal on the main channel to the measurement circuit with weak power, and the transmission power of the main channel is hardly affected; at the moment, because the power of the detected signal is very small, power amplification is needed, the signal amplitude can be limited to a value which can be accepted by a measuring chip by using an AGC amplitude gain automatic control circuit, and the signal amplitude output after passing through the AGC circuit is unchanged no matter whether the power of the previous signal is changed; a first branch measured signal is input into a measurement channel 1 of the AD8302 through the numerical control phase shifter, a second branch measured signal directly enters a measurement channel 2 of the AD8302, in the measurement result processing module, the CPU controls the numerical control phase shifter to move and is used for eliminating the measurement binary property, the nonlinearity and the error imbalance of an AD8302 measurement chip, and finally, a measurement result is reported to an upper computer or is directly reported to a phase control circuit at the rear end to be used as a reference.
In this example, the signal power of the two main signals after photoelectric conversion is 5dBm, and the frequency is 200 MHz; the coupler is a connector with three connectors of an SMA-KFD19C type, the coupling degree is-20 dB, the coupling output power is-15 dBm, the insertion loss is 0.3dB, the main signal output power is 4.7dBm, the AGC module uses a circuit with a main chip AD8367, the input signal power can be stabilized to-10 dBm output, the power supply is +/-5V, the model of the two-end connector is also an SMA-KFD19C type, the main chip used by the numerical control phase shifter module is PE44820, the phase shift can be controlled through a serial port or a parallel port, the phase shift range is (0 degrees and 358.6 degrees), the phase shift resolution is 1.4 degrees, the input and output interface connector is an SMA-KFD19C type, the signal control and power interface is a J30J-9ZKP type, the power supply is +5V, the main chip of the phase measurement module is AD8302, the two interface connectors are SMA-D3619 type, the power supply is +/-5V, the main CPU chip of the VGT 407 type 3632F, the module is provided with 12-bit A/D sampling interface input and RS232 serial port output, a measuring result input interface is a feedthrough capacitor, the communication interface model is J30J-15ZKP and +5V for power supply, the module can obtain a phase measuring value through the A/D sampling port and convert the phase measuring value into a digital mode, the phase shifting of the phase shifter can be controlled through a program output serial port instruction, information can also be output to a phase control function unit of an upper computer or a rear end, the modules are connected by a radio frequency cable with shielding, and the connector model is SMA-JB 2.
The two curves shown in fig. 4 are idealized graphs of fig. 1, and assuming that the phase shift value of the phase shifter is 0 for the first time and the output voltage of the original phase difference result is M, according to the binary characteristic of the measurement in fig. 1, two points H and H 'are corresponding to the left and right symmetric line segments, and two phase differences θ and θ' are corresponding to the left and right symmetric line segments, and the two angles are symmetric with a positive value and a negative value, and it can be seen from observation that the slopes of the left and right line segments are not uniform, the slope on the left is positive, the output voltage value increases with the increase of the phase difference, the slope on the right is negative, the output voltage value decreases with the increase of the phase difference, so that the slope property can be determined by the movement of the point H to fall on that line segment, and assuming that the point H falls on the positive slope on the left as shown in the left graph of fig. 4, the measured signal B is increased by Δ θ using the numerically controlled phase shifter in fig. 3, the phase difference is changed from theta to theta 1, and the measurement result is changed from M to M1H point becomes H1Here, two cases are distinguished: one is H1Does not cross the 0 highest point, if M1>M, the measurement result increases along with the increase of the phase difference, and then H can be proved to fall on the left positive slope line segment; another situation, as noted in the left diagram of FIG. 4, is H1Over 0 deg. of the highest point, at which time M1The relationship with M is not easily judged, assuming Δ M1= M-M1Δ M1 may be positive, negative or 0, and the position of H point cannot be determined by increasing θ, and this can be determined by decreasing θ, decreasing the measured signal B by Δ θ through the phase shifter, changing the phase difference from θ to θ 2, and changing the measurement result from M to M2H point becomes H2Point, assume Δ M2= M-M2In this case, Δ M2 is always>0, that is, the measurement result decreases with the decrease of the phase difference, so that it can be determined according to the slope relationship that H falls on the left positive slope line segment, and the same method can also be used to determine whether H falls on the right negative slope line segment as shown in the right diagram of fig. 4.
In the above determination process, because the H point has the condition of "mountain-turning" passing through the peak point of 0 ° or "valley-crossing" passing through the valley point of ± 180 °, the determination is performed twice, the Δ θ degree is increased for the first time, and the Δ θ degree is decreased for the second time, and the two measurement nodes are obtainedDifference of fruit, taking Delta M1The larger absolute value of the sum delta M2 is the judgment slope of the confidence taking result, the specific position of H can be judged, in order to avoid the conditions of 'mountain turning' and 'valley crossing' of the point H as much as possible, the smaller delta theta is adopted, the experiment proves that the 21 degrees are more suitable, the binary property of the measurement result can be eliminated through the operation, and the accurate measurement result is obtained.
It can be seen from fig. 2 that the measurement error of the measurement result between ± 60 ° and 120 ° is close to 0, which is the smallest error interval, if the phase difference of the measured signal is well within the interval, the measurement result is the more accurate true value, if the measurement error does not fall within the interval, the measurement error gradually increases towards the two poles, and if the original measurement result H of B and a falls outside ± 60 ° and 120 °, as shown in fig. 5, the phase shifter in fig. 3 may shift the phase to fall within ± (60 °,120 °), to obtain the more accurate result, and then subtract the phase-shifted value to obtain the true phase difference, which is illustrated in the left diagram of fig. 5, and if the H point falls on the left positive slope line segment, but falls within the interval of (-180 °, -120 °), the H point is shifted to (-120 °, at-90 deg. point which is exactly in the middle of-60 deg. interval, the phase shifter is shifted to the right by delta theta = -90 deg. -theta, namely to H1Point, measure H1The phase corresponding to the point is θ 1, and it is noted that because θ has a measurement error θ 1 not equal to-90 °, the final true phase difference value should be "θ 1- Δ θ", i.e., "θ 1 +90 ° + θ".
Through the above operation, the original value is moved to the range of +/-60 degrees and 120 degrees for measurement, so that the range of nonlinear change under different frequencies in fig. 1 is avoided, the measurement of different frequencies is linear and accurate, and the requirement of the range with the minimum phase measurement error in fig. 2 is met.
The AD8302 chip is adopted to measure the phase difference, and the defects of binary property, non-linearity, error imbalance and the like exist, the embodiment firstly ensures that the signal transmission of the main channel cannot be influenced during measurement, secondly overcomes the binary property of the measurement result to ensure the accuracy of the measurement result, and overcomes the non-linearity and error imbalance of the measurement result to ensure the accuracy of the measurement result.
Claims (4)
1. The accurate sine wave phase difference measuring circuit is characterized by comprising a first branch and a second branch, wherein the first branch comprises a first coupler, a first AGC amplitude automatic gain controller, a numerical control phase shifter, an AD8302 phase difference measuring module and a measuring result processing module which are sequentially connected, the second branch comprises a second coupler, a second AGC amplitude automatic gain controller, an AD8302 phase difference measuring module and a measuring result processing module which are sequentially connected, the first branch and the second branch share the AD8302 phase difference measuring module and the measuring result processing module, the output of the second AGC amplitude automatic gain controller is directly connected to the AD8302 phase difference measuring module, and a CPU of the measuring result processing module is electrically connected with the numerical control phase shifter.
2. The sinusoidal phase difference precision measurement circuit of claim 1, wherein the first and second couplers are low coupling, low insertion loss couplers.
3. The sine wave phase difference precision measurement circuit of claim 1, wherein the AGC amplitude automatic gain controller limits the amplitude of the measured signal to be within an acceptable range for AD8302 and keeps the amplitude unchanged.
4. A sine wave phase difference accurate measurement method comprising the sine wave phase difference accurate measurement circuit according to any one of claims 1 to 3, the method comprising the steps of:
setting the degree of the numerical control phase shifter to be 0, measuring the original voltage value of the phase difference of the first branch signal B and the second branch signal A through AD8302, and recording the original voltage value as M0, wherein the original phase difference of two branches corresponding to M0 is theta degree, and at the moment, theta has positive and negative possible values;
2) controlling the numerical control phase shifter to increase the phase of the first branch signal B by 21 degrees, and recording the voltage value measured by the AD8302 as M1;
3) setting the degree of the numerical control phase shifter to be 0, and restoring the phase of the first branch signal B to the initial phase;
4) controlling the numerical control phase shifter to reduce the phase of the first branch signal B by 21 degrees, and recording the voltage value measured by AD8302 as M2;
5) the absolute value of the difference between M1 and M0 and the absolute value of the difference between M2 and M0 are obtained through calculation, the direction with a larger absolute value is used as a judgment basis to judge the increase slope of the phase difference, so that whether theta is positive or negative is known, and the accurate value of theta is measured but not necessarily an accurate value;
6) if theta is not in the range of +/-60 degrees and 120 degrees, the measured voltage value M0 has larger error, the numerical control phase shifter is controlled to increase the degree of the first branch signal B by delta theta, and the phase difference value is changed into theta + delta theta;
7) due to the difference of measurement errors after interval transformation, the phase difference value between the first branch signal B and the second branch signal a is measured again through the AD8302, and the final phase difference voltage is M3, the degree corresponding to M3 is recorded as θ ', θ' = θ + Δ θ, θ 'is an accurate value in the range of ± 60 ° and 120 °, Δ θ is also an accurate value, and the original value "θ = θ' - Δ θ" is also an accurate value.
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