CN114221560B - PWM rectifier LLCL filter design structure and method - Google Patents
PWM rectifier LLCL filter design structure and method Download PDFInfo
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- CN114221560B CN114221560B CN202111295104.6A CN202111295104A CN114221560B CN 114221560 B CN114221560 B CN 114221560B CN 202111295104 A CN202111295104 A CN 202111295104A CN 114221560 B CN114221560 B CN 114221560B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/145—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means
- H02M7/155—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/12—Arrangements for reducing harmonics from ac input or output
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
- H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
- H03H7/01—Frequency selective two-port networks
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
- H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
- H03H7/01—Frequency selective two-port networks
- H03H2007/013—Notch or bandstop filters
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention provides a design structure of a LLCL filter of a PWM rectifier, wherein the LLCL filter is arranged at the input end of the PWM rectifier and is used for filtering harmonic current generated by the action of a switching tube; the device mainly comprises a network side reactor L1, a bridge side reactor L2, a trap branch resonance reactor L3, a trap branch filter capacitor Cf and a trap branch damping resistor Rd. Wherein the bridge side reactor L2 has attenuation function on bridge arm side current; the trap branch resonance reactor L3 and the trap branch filter capacitor Cf are connected in series to form a trap for filtering harmonic current near the switching frequency; the series connection of the notch branch damping resistor Rd and the notch branch filter capacitor Cf can inhibit resonance of the system; the grid-side reactor L1 can further attenuate the grid-side current harmonics. The invention also provides a design method of the LLCL filter of the PWM rectifier.
Description
Technical Field
The invention relates to the field of a design method of an input filter of a PWM rectifier, in particular to a design structure and a design method of an LLCL filter of the PWM rectifier.
Background
In many fields of modern industry, life and the like, in order to meet the working requirements of electric equipment and obtain better economic benefits at the same time, a large number of power conversion devices are emerging, and a rectifier can convert alternating current into direct current to be provided for the electric equipment.
The traditional diode rectification or thyristor rectification, although simple in control and stable in operation, has a low power factor, and can increase current in a line, so that unnecessary loss is caused.
The PWM rectifier uses IGBT or MOSFET as a switching tube, so that the power factor of the rectifier can be greatly improved, the size can be obviously reduced, meanwhile, energy can flow bidirectionally, and the energy can be fed back to a power grid in certain occasions, so that the PWM rectifier is widely applied.
The traditional PWM rectifier input filter has poor filtering effect and large loss, and is not suitable for a high-power PWM rectifier.
It is therefore necessary to design a new PWM rectifier LLCL filter to overcome the above problems.
Disclosure of Invention
The invention aims to overcome the defects of the prior art, and provides a design structure and a method of a LLCL filter of a PWM rectifier, which at least solve part of the problems in the prior art.
The invention is realized in the following way:
the invention provides a design structure of a pulse-width modulation (PWM) rectifier light-load control (LLCL) filter, which comprises an LLCL filter arranged at the input end of a three-phase PWM rectifier and used for filtering harmonic current generated by the action of a switching tube in the three-phase PWM rectifier, wherein the LLCL filter comprises three branches corresponding to three-phase voltage, each branch is provided with a net side reactor L1 and a bridge side reactor L2, the net side reactor L1 and the bridge side reactor L2 are connected in series, the other end of the net side reactor L1 is directly connected with a power grid, the other end of the bridge side reactor L2 is connected to the three-phase PWM rectifier, the LLCL filter further comprises three notch branch resonant reactors L3, three notch branch filter capacitors Cf and three notch branch damping resistors Rd, the three notch branch resonant reactors L3 are in one-to-one correspondence with the three branches, the middle points of the net side reactor L1 and the bridge side reactor L2 are connected in series, the three notch filter capacitors Cf and the three notch branch are connected with one end points of the three notch resonant branches, one end points of the three notch resonant branches are connected with one end points of the three notch resonant branches, and one end points of the three notch resonant branches are connected with one end points of the three triangle resonant branches 3, and the triangular end points are formed between the three notch resonant branches are connected with one end points.
The invention also provides a design method of the LLCL filter of the PWM rectifier, which comprises the following steps: s1, in order to meet the four-quadrant operation of a rectifier, the upper limit value of a network side reactor L1+ bridge side reactor L2 and an upper limit value of the network side reactor L2 are required to meet the limit requirement;
s2, limiting ripple waves of output current of a switching tube bridge arm in order to meet the loss of a trap branch and the stability of system control, namely, a bridge side reactor L2 is required to meet the minimum inductance requirement;
s3, the network side reactor L1 needs to follow a proper harmonic attenuation index;
s4, in order to meet reactive power loss of the system, the upper limit value of the notch branch filter capacitor Cf is required to meet the limiting requirement;
s5, the trap branch resonance reactor L3 is connected with a trap branch filter capacitor Cf in series to form a trap for filtering harmonic current near the switching frequency;
s6, a notch branch damping resistor Rd is connected with a notch branch filter capacitor Cf in series, so that the suppression effect on resonance is met, and the requirement on limiting the impedance is met.
Preferably, in step S1, the bridge side reactor L1 and the upper limit value L1+L2 of the screening side reactor L2 are confirmed based on the rated input line voltage effective value E, the direct current side voltage U, the phase current effective value I, the fundamental wave frequency f and the carrier frequency fsw of the three-phase PWM rectifier,
preferably, in step S2, the value of bridge-side reactor L2 is checked based on attenuation coefficient α of the bridge-side current ripple,
preferably, in step S3, the value of grid-side reactor L1 is checked from attenuation coefficient β of the grid-side current to the bridge arm-side ripple, l1=βl2.
Preferably, in step S4, according to the reactive power duty ratio requirement of the system, γ is the proportion of reactive power to active power P on the notch branch filter capacitor Cf, v is the voltage across the notch branch filter capacitor Cf, where the notch branch filter capacitor Cf is connected in a triangle, v is equal to the line voltage effective value E, the value of the notch branch filter capacitor Cf is confirmed,
preferably, in step S5, the value of the notch branch resonance reactor L3 is determined based on the notch branch filter capacitance Cf and the carrier frequency fsw,
checking whether the resonant frequency fres of the whole LLCL filter is more than or equal to 10f and less than or equal to 0.5fsw, and if not, re-selecting the correlation coefficient for calculation until the requirement is met.
Preferably, in step S6, the value of the notch branch damping resistor Rd is determined based on the resonant frequency fres of the whole system and the value of the notch branch filter capacitance Cf,rd value +.>Z of (2) Cf 。
The invention has the following beneficial effects:
compared with the traditional LLCL filter, the filter capacitor Cf has the advantages that the filter capacitor Cf adopts a triangle connection mode, a better filtering effect can be achieved under the same capacitance value, meanwhile, the damping resistor Rd is connected with the filter capacitor Cf in series, the current flowing through the damping resistor Rd is smaller under the same condition, namely, the loss is lower, and the heat dissipation design of the high-power rectifier is facilitated while the efficiency is improved.
Drawings
In order to more clearly illustrate the embodiments of the invention or the technical solutions in the prior art, the drawings that are required in the embodiments or the description of the prior art will be briefly described, it being obvious that the drawings in the following description are only some embodiments of the invention, and that other drawings may be obtained according to these drawings without inventive effort for a person skilled in the art.
FIG. 1 (a) is a bird's diagram of a conventional LCL filter circuit, and FIG. 1 (aa) is a partial enlarged view of FIG. 1 (a); fig. 1 (b) is a bode diagram of an LLCL filter circuit used in the present invention, and fig. 1 (bb) is a partial enlarged diagram of fig. 1 (b);
fig. 2 (a) is a PWM rectifier topology based on the LLCL filtering used in the present invention, and fig. 2 (b) is a simplified PWM rectifier topology based on the conventional LLCL filtering;
FIG. 3 (a) shows the result of Fourier analysis of the current at the net side of the conventional LLCL filter, and FIG. 3 (b) shows the effective value of the current flowing through the damping resistor of the conventional LLCL filter;
fig. 4 (a) shows the fourier analysis result of the network side current using the same filter inductance, filter capacitance and damping resistance parameters in the present invention, and fig. 4 (b) shows the effective value of the current flowing through the damping resistance using the same filter inductance, filter capacitance and damping resistance parameters in the present invention.
Detailed Description
The following description of the embodiments of the present invention will be made clearly and completely with reference to the accompanying drawings, in which it is apparent that the embodiments described are only some embodiments of the present invention, but not all embodiments. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
As shown in fig. 1-4, the first embodiment of the present invention provides a design structure of a LLCL filter of a PWM rectifier, which includes an LLCL filter disposed at an input end of a three-phase PWM rectifier and configured to filter harmonic currents generated by switching tube actions in the three-phase PWM rectifier, where the LLCL filter includes three branches corresponding to three-phase voltages, each branch is provided with a network side reactor L1 and a bridge side reactor L2, the network side reactors L1 and the bridge side reactors L2 are connected in series, the other end of the network side reactor L1 is directly connected to a power grid, the other end of the bridge side reactor L2 is connected to a bridge arm midpoint of the three-phase PWM rectifier, that is, between two switching tubes connected in series with a conventional three-phase PWM rectifier, the bridge side reactors L2 play an attenuation role on bridge arm side currents, the network side reactors L1 can further play an attenuation role on network side current harmonics, the LLCL filter further includes three notch branch resonant reactors L3, three notch filter capacitors Cf, three notch branch resistors, three notch resistors, one end-to-end triangular filter end points, and three notch resistors L3 are connected in series, and one end-to-end points of the three notch resistors L3 are connected in series, and one end points of the three notch resistors L3 are connected in each notch filter.
The damping resistor Rd is connected with the filter capacitor Cf in series to inhibit resonance of the system. The trap branch resonance reactor L3 and the trap branch filter capacitor Cf are connected in series to form a trap, and the trap is mainly used for filtering harmonic current near the switching frequency. Compared with the traditional LLCL filter, the filter capacitor Cf has the advantages that the filter capacitor Cf adopts a triangle connection mode, a better filtering effect can be achieved under the same capacitance value, meanwhile, the damping resistor Rd is connected with the filter capacitor Cf in series, the current flowing through the damping resistor Rd is smaller under the same condition, namely, the loss is lower, and the heat dissipation design of the high-power rectifier is facilitated while the efficiency is improved.
The second embodiment of the invention provides a design method of a LLCL filter of a PWM rectifier, which comprises the following steps: s1, in order to meet the four-quadrant operation of a rectifier, the upper limit value of a network side reactor L1+ bridge side reactor L2 and an upper limit value of the network side reactor L2 are required to meet the limit requirement;
s2, limiting ripple waves of output current of a switching tube bridge arm in order to meet the loss of a trap branch and the stability of system control, namely, a bridge side reactor L2 is required to meet the minimum inductance requirement;
s3, the network side reactor L1 needs to follow a proper harmonic attenuation index;
s4, in order to meet reactive power loss of the system, the upper limit value of the notch branch filter capacitor Cf is required to meet the limiting requirement;
s5, the trap branch resonance reactor L3 is connected with a trap branch filter capacitor Cf in series to form a trap for filtering harmonic current near the switching frequency;
s6, a notch branch damping resistor Rd is connected with a notch branch filter capacitor Cf in series, so that the suppression effect on resonance is met, and the requirement on limiting the impedance is met.
The specific design method comprises the following steps:
according to the rated input line voltage effective value E, direct-current side voltage U, phase current effective value I, fundamental wave frequency f and carrier frequency fsw of PWM rectifier, the upper limit value L1+L2 of bridge side inductance screening side inductance sum is confirmed,
confirming the value of the inductance L2 at the bridge side according to the attenuation coefficient alpha of the current ripple at the bridge arm side,
confirming the value of the network side inductance L1 according to the attenuation coefficient beta of the network side current to the bridge arm side ripple wave, wherein L1=βL2;
according to the requirement of the system on the reactive power ratio, gamma is the proportion of the reactive power on the capacitor Cf to the active power P, v is the voltage at two ends of the capacitor Cf, the capacitor Cf is in triangular connection, v is equal to the effective value E of the line voltage, the value of the notch branch filter capacitor Cf is confirmed,
the value of the resonant inductance L3, namely the resonant reactor, is determined according to the notch branch filter capacitor Cf and the carrier frequency fsw,
checking whether the resonant frequency fres of the whole LLCL filter is more than or equal to 10f and less than or equal to 0.5fsw, wherein f is the fundamental frequency, fsw is the carrier frequency, and if not, re-selecting the correlation coefficient for calculation until the requirement is met;
determining damping electricity according to the resonance frequency fres of the whole system and the value of the notch branch filter capacitor CfResistance Rd, capacitance of notch branch filter capacitor CfRd value +.>Z of (2) Cf ；
The invention adopts the calculation method of the traditional LCL filter, but the filter capacitor adopts a triangle connection mode, the damping resistor is connected with the filter capacitor in series, the better filtering effect can be achieved on the premise of not changing the capacitance value and the resistance value of the capacitor, and the loss on the resistor is lower.
In this embodiment, a 132KW PWM rectifier is taken as an example, and a PWM rectifier LLCL filter design method is described, in which the effective value u=380v of the side line voltage of the power grid, the rectifier switching frequency fsw=4khz, and the rectifier switching frequency, i.e. the carrier frequency fsw.
The design method of the invention is further described below with reference to the accompanying drawings.
Referring to fig. 2 (a) below, the PWM rectifier LLCL filter of the present invention is constructed as follows:
the network side inductor L1 and the bridge side inductor L2 are connected in series, the network side inductor is a network side reactor, the bridge side inductor is a bridge side reactor, the other end of the network side inductor L1 is directly connected with a power grid, and the other end of the bridge side inductor L2 is connected to the middle point of a bridge arm; the midpoint of the series connection of the net side inductor L1 and the bridge side inductor L2 is led out and is connected with one end of the notch branch resonant reactor L3; the damping resistor Rd is connected with the filter capacitor Cf in series, the head and the tail form a triangle connection, and each end point of the triangle is connected to the midpoint of the series connection of the network side inductor L1 and the bridge side inductor L2 respectively. Note that when selecting the filter capacitor Cf, it is necessary to consider that the voltage across the capacitor Cf is close to the three-phase voltage.
The following are the electrical parameters of the component obtained according to the design method of the invention:
| element labels | Electrical parameters |
| L1 | 400UH |
| L2 | 100UH |
| L3 | 13UH |
| CF | 40UF |
| Rd | 0.4Ω |
Fig. 3 (a) shows the result of fourier analysis of the net side current of the conventional LLCL filter under the above parameters, where the total harmonic distortion THD of the net side current is 2.52%, (b) shows the effective value of the current flowing through the damping resistor of the conventional LLCL filter, which is close to 12A after stabilization; in fig. 3 (b), the abscissa represents Time(s) and the ordinate represents a;
fig. 4 (a) shows the result of fourier analysis of the current on the network side of the present invention under the same parameters as described above, wherein the THD value of the total harmonic distortion of the current on the network side is 2.20%, (b) shows the effective value of the current flowing through the damping resistor of the present invention, which is close to 7A after stabilization; in fig. 4 (b), the abscissa represents Time(s) and the ordinate represents a;
comparing the two groups of simulation results, the invention finds that the THD value of the current at the net side is obviously lower than that of the traditional scheme under the condition that only the withstand voltage level of the capacitor is changed and other electrical parameters of the element are not changed, and the loss on the damping resistor is also much lower, so that the characteristic is more obvious in a high-power low-frequency PWM rectifier.
The foregoing description of the preferred embodiments of the invention is not intended to be limiting, but rather is intended to cover all modifications, equivalents, alternatives, and improvements that fall within the spirit and scope of the invention.
Claims (8)
1. A PWM rectifier LLCL filter, characterized by: the three-phase PWM rectifier comprises an LLCL filter arranged at the input end of the three-phase PWM rectifier and used for filtering harmonic current generated by the action of a switching tube in the three-phase PWM rectifier, the LLCL filter comprises three branches corresponding to three-phase voltage, a net side reactor L1 and a bridge side reactor L2 are arranged on each branch, the net side reactor L1 and the bridge side reactor L2 are connected in series, the other end of the net side reactor L1 is directly connected with a power grid, the other end of the bridge side reactor L2 is connected to the three-phase PWM rectifier, the LLCL filter further comprises three trap branch resonant reactors L3, three trap branch filter capacitors Cf and three trap branch damping resistors Rd, the three trap branch resonant reactors L3 are in one-to-one correspondence with the three branches, midpoints of the net side reactor L1 and the bridge side reactor L2 are led out and are connected with one end of the trap branch resonant reactor L3, the three trap filter capacitors Cf and the three trap branch tail resistors Rd are connected with one another end point of the three triangle resonant branches, and one end points of the triangle resonant branch resonant reactors are connected with one end point of the triangle resonant reactors Cf, and one end point of the triangle resonant branch is connected with one end point Ctrap capacitor C is arranged between the triangle resonant branch 3 and one end point.
2. A method of designing a PWM rectifier LLCL filter according to claim 1, characterized in that: s1, in order to meet the four-quadrant operation of a rectifier, the upper limit value of a network side reactor L1+ bridge side reactor L2 and an upper limit value of the network side reactor L2 are required to meet the limit requirement;
s2, limiting ripple waves of output current of a switching tube bridge arm in order to meet the loss of a trap branch and the stability of system control, namely, a bridge side reactor L2 is required to meet the minimum inductance requirement;
s3, the network side reactor L1 needs to follow a proper harmonic attenuation index;
s4, in order to meet reactive power loss of the system, the upper limit value of the notch branch filter capacitor Cf is required to meet the limiting requirement;
s5, the trap branch resonance reactor L3 is connected with a trap branch filter capacitor Cf in series to form a trap for filtering harmonic current near the switching frequency;
s6, a notch branch damping resistor Rd is connected with a notch branch filter capacitor Cf in series, so that the suppression effect on resonance is met, and the requirement on limiting the impedance is met.
3. The PWM rectifier LLCL filter design method of claim 2, wherein:
in step S1, the upper limit value L1+L2 of the bridge side reactor L2 and the network side reactor L1 is confirmed according to the rated input line voltage effective value E, the direct current side voltage U, the phase current effective value I and the fundamental wave frequency f of the three-phase PWM rectifier,
4. the PWM rectifier LLCL filter design method of claim 3, wherein:
in step S2, the value of bridge-side reactor L2 is checked based on carrier frequency fsw and attenuation coefficient α of the bridge-arm-side current ripple,
5. the PWM rectifier LLCL filter design method as in claim 4, further comprising:
in step S3, the value of network-side reactor L1 is checked from attenuation coefficient β of network-side current to bridge arm-side ripple, l1=βl2.
6. The PWM rectifier LLCL filter design method of claim 5, wherein:
in step S4, according to the reactive power duty ratio requirement of the system, γ is the proportion of reactive power to active power P on the notch branch filter capacitor Cf, v is the voltage across the notch branch filter capacitor Cf, where the notch branch filter capacitor Cf is connected in a triangle, v is equal to the line voltage effective value E, the value of the notch branch filter capacitor Cf is confirmed,
7. the PWM rectifier LLCL filter design method of claim 6, wherein:
in step S5, the value of the notch branch resonance reactor L3 is determined based on the notch branch filter capacitance Cf and the carrier frequency fsw,
checking whether the resonant frequency fres of the whole LLCL filter is more than or equal to 10f and less than or equal to 0.5fsw, and if not, re-selecting the correlation coefficient for calculation until the requirement is met.
8. The PWM rectifier LLCL filter design method of claim 7, wherein:
in step S6, the value of the notch branch damping resistance Rd is determined based on the resonance frequency fres of the entire system and the value of the notch branch filter capacitance Cf,rd value +.>Z of (2) Cf 。
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| CN102468651A (en) * | 2010-11-12 | 2012-05-23 | 吴卫民 | Filter for specific frequency current bypass |
| CN103746587A (en) * | 2014-01-22 | 2014-04-23 | 开封光利高科实业有限责任公司 | Control damping method applied to the resonance inhibition of LLCL single-phase grid connected inverter |
| CN205657582U (en) * | 2016-04-26 | 2016-10-19 | 江苏易立电气股份有限公司 | LLCL type bank electricity variable frequency power supply shipboard filter circuit |
| CN207926186U (en) * | 2017-12-19 | 2018-09-28 | 齐齐哈尔工程学院 | A kind of active filter |
| CN210839320U (en) * | 2019-10-28 | 2020-06-23 | 安徽建筑大学 | LCLC type passive damping circuit, single-phase and three-phase grid-connected inverter system |
| KR20220132825A (en) * | 2021-03-24 | 2022-10-04 | 한국전력공사 | HARMONIC CURRENT REDUCTION FILTER and DISTRIBUTION LINKAGE SYSTEM COMPRISING IT |
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2021
- 2021-11-03 CN CN202111295104.6A patent/CN114221560B/en active Active
Patent Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102468651A (en) * | 2010-11-12 | 2012-05-23 | 吴卫民 | Filter for specific frequency current bypass |
| CN103746587A (en) * | 2014-01-22 | 2014-04-23 | 开封光利高科实业有限责任公司 | Control damping method applied to the resonance inhibition of LLCL single-phase grid connected inverter |
| CN205657582U (en) * | 2016-04-26 | 2016-10-19 | 江苏易立电气股份有限公司 | LLCL type bank electricity variable frequency power supply shipboard filter circuit |
| CN207926186U (en) * | 2017-12-19 | 2018-09-28 | 齐齐哈尔工程学院 | A kind of active filter |
| CN210839320U (en) * | 2019-10-28 | 2020-06-23 | 安徽建筑大学 | LCLC type passive damping circuit, single-phase and three-phase grid-connected inverter system |
| KR20220132825A (en) * | 2021-03-24 | 2022-10-04 | 한국전력공사 | HARMONIC CURRENT REDUCTION FILTER and DISTRIBUTION LINKAGE SYSTEM COMPRISING IT |
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| CN114221560A (en) | 2022-03-22 |
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