CN113964548A - In-band scattering reduction structure based on four-dimensional antenna array and control method thereof - Google Patents

In-band scattering reduction structure based on four-dimensional antenna array and control method thereof Download PDF

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CN113964548A
CN113964548A CN202111242709.9A CN202111242709A CN113964548A CN 113964548 A CN113964548 A CN 113964548A CN 202111242709 A CN202111242709 A CN 202111242709A CN 113964548 A CN113964548 A CN 113964548A
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antenna
array
rcs
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scattering
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杨仕文
李子豪
杨锋
陈益凯
屈世伟
胡俊
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University of Electronic Science and Technology of China
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
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Abstract

The invention belongs to the technical field of antenna engineering and discloses an in-band scattering reduction structure based on a four-dimensional antenna array and a control method thereof. The rear end of each unit port of the antenna is sequentially connected with a four-dimensional T/R component, a coaxial line with characteristic impedance of 50 ohms and a broadband load; the four-dimensional T/R component comprises a radio frequency switch, a phase shifter and an attenuator. The scattering of the mode item of the antenna is dynamically regulated and controlled by optimizing the time sequence of the switch connected with each unit, so that the total scattering field of the antenna generates periodic change, and the total scattering field of the array is estimated by using a method of multiplying the RCS of the units by the scattering array factor of the array. According to the Fourier series theory, RCS of the center frequency is partially transferred to the side band, so that in-band RCS reduction is realized. The invention makes full use of the time dimension freedom of the four-dimensional antenna array to ensure that the RCS of the antenna is jointly distributed in the space domain and the frequency domain, and has obvious RCS reduction effect compared with the traditional phased array.

Description

In-band scattering reduction structure based on four-dimensional antenna array and control method thereof
Technical Field
The invention belongs to the technical field of antenna engineering, and relates to an in-band scattering reduction structure based on a four-dimensional antenna array and a control method thereof.
Background
With the gradual development of the information-based war, especially the rapid progress of the radar detection technology, the stealth technology plays an increasingly important role in the modern electronic war. The Radar Cross Section (Radar Cross Section), abbreviated as RCS, is an important index for measuring the stealth performance of a detected target. The size of a radar scattering cross section directly determines the stealth performance of a detected target, and an antenna serving as one of strong scattering sources of a carrier platform has great influence on RCS (radar cross section). The antenna is an active target, and when the antenna is subjected to stealth processing, the antenna must be ensured to be capable of normally receiving and transmitting electromagnetic waves, so that the conventional stealth means cannot directly act on the antenna.
At present, most of technical researches on antenna RCS reduction mainly focus on single antennas such as microstrip, waveguide slot, slot and the like, and a plurality of effective methods are provided, and the following ideas are mainly included in summary: 1) RCS is reduced by utilizing antenna shape correction, loading impedance or short-circuit probe technology; 2) loading a wave absorbing material on a structure which does not influence the normal radiation of the antenna to absorb the energy of the incident wave, thereby reducing the scattering of the antenna; 3) using the frequency selective surface FSS to filter out incident waves under the threat frequency domain condition, and further controlling an antenna RCS; 4) the RCS is reduced by using a novel artificial material (such as holographic metamaterial HM, polarization conversion metamaterial PCM, artificial magnetic conductor AMC and the like) to counteract backscattering waves. A small amount of literature studies the scattering properties of antenna arrays, but most are limited to the reduction of the scattering properties of the array elements, and the scattering properties are not considered from the array synthesis perspective.
In the patent with publication number CN105655723B, a method for reducing the in-band RCS of a phased array antenna by a method of randomly rotating array elements around a feeding point is proposed, and random scattering phases are generated by randomly rotating the array elements, so that scattering fields of different array elements cannot be superposed in phase in a main lobe region, but are dispersed to a wider angle domain space, thereby reducing the RCS of the array antenna. Meanwhile, for the radiation situation, the radiation fields of different array elements can still realize in-phase superposition in the main lobe area through the phase compensation of the array element excitation, so that the radiation performance of the array antenna is basically not reduced. However, the patent does not disclose the fact that the method is only suitable for the antenna element with the polarization form of circular polarization, otherwise, the random rotation of the array elements can change the polarization state of each array element, and the radiation performance of the array is deteriorated after different array elements are superposed.
In both of the patents CN108493625B and CN107086369A, a method of processing the structure of the strongly coupled wideband phased array antenna element itself is adopted, and the purpose of suppressing the in-band RCS of the array is attempted by improving the in-band impedance matching characteristics to reduce the scattering of the antenna pattern items of the element. Because the method only focuses on the scattering control at the antenna unit level and does not introduce the idea of array synthesis, the method is not easy to be applied to arrays of any other structural types and has poor universality.
The utility model provides a reconfigurable phased array antenna RCS reduces method based on scattering polarization in the patent for CN108879108A, every array element of phased array antenna includes three kinds of different polarization modes, when phased array antenna radiates, all array elements are in the same polarization mode, form unified polarization array, after phased array antenna radiation, make the polarization mode random distribution of each array element, form random polarization array, thereby can accomplish on the basis of the radiation performance who does not influence array antenna, the RCS after array antenna radiation ends is showing to reduce. The method sets the polarization states of the array units in the radiation and scattering states independently, each array unit needs to be controlled by switching on and off of a PIN diode, an external control processor for controlling the polarization mode of the array elements needs to be additionally arranged, the complexity of the system is increased, and in addition, the design method has larger limitations in antenna form selection and broadband phased array application.
In patent No. CN109950704A, an in-band RCS control method for a strongly-coupled wideband phased array antenna is introduced, in which the length of a coaxial delay line at the rear end of each antenna element is optimized to regulate and control the phase of a reflection coefficient at a port of each antenna element, so as to implement scattering cancellation. However, the patent only carries out optimization design aiming at the mode term RCS of the antenna, does not take the structural term RCS into consideration, and has great limitation.
As a new system array, the four-dimensional antenna array adopts a high-speed radio frequency switch on an array feed network structure, and the on-off of the switch is controlled by an FPGA circuit board, so that the working state of an antenna unit is controlled. Because of introducing new degree of freedom, the four-dimensional antenna array has certain advantages in various fields compared with the traditional array, in the published documents, the four-dimensional antenna array can realize the beam scanning without a phase shifter, simultaneously generate multi-beam, DOA estimation, secret communication, radar with low interception probability and the like, but the document for realizing the RCS reduction of the antenna by utilizing the four-dimensional antenna array does not appear.
Therefore, the invention discloses an in-band scattering reduction structure based on a four-dimensional antenna array and a control method thereof, wherein the four-dimensional T/R component, a coaxial line and other circuits are connected at the rear end of an antenna, a periodic time sequence is loaded, the time modulation is carried out on a mode item scattering field of the antenna, the total scattering field of the antenna is further dynamically regulated and controlled, and the scattered energy is jointly controlled in a space domain and a frequency domain.
Disclosure of Invention
The invention is realized in view of the background, overcomes the defects of the prior art, provides an in-band scattering reduction structure based on a four-dimensional antenna array and a control method thereof, fully utilizes the time dimension freedom degree brought by the four-dimensional antenna array, and obviously reduces the RCS of the array antenna.
In order to achieve the purpose, the invention adopts the following technical scheme.
Establishing an antenna model in three-dimensional high-frequency structure electromagnetic field simulation software (HFSS), setting a period boundary condition, and setting an electromagnetic wave with the same polarization in a band to be incident to an antenna array surface.
Open circuits (Z) are respectively arranged at the antenna portslInfinity) and short circuit (Z)l0), simulating to obtain a one-dimensional infinite environmentBottom, the scattered field E of the same polarization of the antennas(∞) and Es(0) And extracting the input impedance Z of the antennainThereby obtaining the antenna termination arbitrary load ZlThe structural term fringe field and the mode term fringe field of the antenna.
Figure BDA0003319793270000031
Figure BDA0003319793270000032
Es(Zl)＝Est+Ean(Zl) (3)
In formulae (1) to (3), EstStructural terms representing the antenna elements, scattered field, Ean(Zl) Mode term fringe field representing antenna element, Es(Zl) Representing the total scattered field of the antenna element.
The four-dimensional T/R component, the 50 ohm coaxial line and the broadband load Z are connected at the rear end of the antennal. The four-dimensional T/R component comprises a radio frequency switch, a phase shifter and an attenuator. For theoretical analysis and verification, an S parameter matrix when an absorption radio frequency switch operating in an X band is turned on and off is tested, which respectively includes:
Figure BDA0003319793270000033
converting the S parameter matrix of the switch into a Z matrix, and calculating the formula of each item in the Z matrix according to formulas (5) to (7):
Figure BDA0003319793270000041
Figure BDA0003319793270000042
Figure BDA0003319793270000043
establishing a reference plane S between an antenna element and a four-dimensional T/R assembly port 11The reference plane looking to the left is the input impedance Z of the antennainThe reference surface is viewed to the right as the equivalent impedance Z of the back-end circuitn. Establishing a reference plane S between a four-dimensional T/R assembly port 2 and a 50 ohm coaxial line2The equivalent impedance of the reference surface looking to the right is Zm. When the switch is on and off, ZnAre each equal to Zon,ZoffThe specific calculation formula is as follows:
Figure BDA0003319793270000044
in the formula, Z0Characteristic impedance of coaxial line, Z, for switch back connectionlThe load is a broadband load connected with the coaxial line, beta is 2 pi/lambda is wave number, lambda is the working wavelength of the antenna, and l is the length of the coaxial line. Then, in the two states, the reflection coefficients of the antenna and the back-end circuit are respectively:
Figure BDA0003319793270000051
in the formula, Zin *Representing the conjugate of the antenna input impedance. Because the switch is an active device, the S parameter in the on and off states is not easy to control, so the length l of the characteristic impedance of the 50 ohm coaxial line and the broadband load Z need to be optimizedlSuch that the port reflection coefficient satisfies the following condition in both states:
Figure BDA0003319793270000052
the optimal condition is that the ratio is 0, port reflection coefficients in the two states are in equal amplitude and opposite phase, corresponding mode item scattering fields meet the condition that the amplitudes are the same, the phase difference is 180 degrees, and scattering cancellation can be carried out through reasonably optimizing a time sequence.
When the switch is switched on and off, the total scattered field of the antenna unit is respectively expressed as:
Figure BDA0003319793270000053
the method for obtaining the total scattering field estimation expression of the one-dimensional linear array by using the unit scattering directional diagram multiplied by the array scattering array factor is as follows:
Figure BDA0003319793270000054
wherein d is the array element spacing, θ0Denotes an electromagnetic wave incident direction, θ denotes an electromagnetic wave scattering direction, N denotes the number of antenna elements, β denotes a free space wave number (generally, β may be set to 2 pi/λ, and λ denotes a free space wavelength),
for a four-dimensional antenna array, each antenna unit is loaded with different time sequences, and the mode item scattered field of the antenna is subjected to time modulation, namely E is obtainedan(Zon) And Ean(Zoff) A periodic variation is performed. The expression for the mode term fringe field for the kth cell is:
Figure BDA0003319793270000055
Figure BDA0003319793270000056
in formula (13), TpFor the modulation period of the switch, tkIs the starting time, tau, when the switch connected with the kth antenna unit is turned onkThe duration of the switch connected to the kth antenna element being turned on. Formula (14) represents tkAnd τkThe constraint of (2). According to Fourier series theory, the m-th order sideband mode term scattered field of the k unitThe number of levels of the inner leaf can be expressed as:
Figure BDA0003319793270000061
assuming that the frequency of the incident electromagnetic wave is f0Because the switch is loaded at the rear end of the antenna, the structural item of the antenna has unchanged scattered field and frequency of f0. The mode term fringe field is temporally modulated, producing sideband components. The total scattered field of the antenna is thus divided into two parts. For the center frequency f0Its scattered field is the superposition of the structure term scattered field and the mode term scattered field, and the side band has only the mode term scattered field.
By optimizing the time sequence of each unit of the antenna, the estimation expressions of the scattered field of the center frequency of the one-dimensional linear array and the scattered field of the side band can be respectively obtained:
Figure BDA0003319793270000062
Figure BDA0003319793270000063
for convenience of description, when all switches connected with the antenna units are conducted, the array is a reference array 1; when all the switches connected with the antenna units are disconnected, the array is a reference array 2; the two are static arrays, namely, the traditional phased array, and the RCS is respectively as follows:
Figure BDA0003319793270000064
the RCS of each sideband component of the four-dimensional antenna array can be obtained by the same method:
Figure BDA0003319793270000065
the scattering energy of the center frequency and the side bands needs to be suppressed, and the maximum value of the scattering energy of each frequency point needs to be ensured to be as small as possible, so that the RCS of the four-dimensional antenna array is defined as follows:
Figure BDA0003319793270000071
equations (12), (16) - (17) are estimated and approximated by multiplying the element scattering pattern by the array scattering array factor. Although the edge truncation effect of the limited large array is ignored and the result has a certain difference with the result under the real condition, the calculation amount can be saved, the calculation efficiency is improved, and the method has a certain value for realizing the rapid analysis of the scattering characteristic of the array antenna.
In general, the general technical scheme of the invention is as follows: the four-dimensional T/R component, the 50-ohm coaxial line and the broadband load are loaded at the rear end of each unit port of the antenna. Firstly, under a periodic environment, separating a structure item scattered field and a mode item scattered field of an antenna unit, and then optimizing the length of a coaxial line and the value of a broadband load according to the formulas (8) to (10). And then combining the estimated expressions of the expressions (16) - (17) on the scattering characteristics of the array, and taking the starting time and the duration of the conduction of a switch connected with each unit of the antenna as optimization variables, and optimizing the scattering performance of the array by adopting an optimization algorithm to realize the scattering control in a specified threat space in the working band of the array antenna, so that the RCS is lower than that of a static reference array.
The invention provides an inband scattering reduction structure based on a four-dimensional antenna array and a control method thereof, and realizes the inband RCS reduction of the array antenna. Meanwhile, the invention has the beneficial effects that: the time dimension freedom degree of the four-dimensional antenna array is fully utilized, the mode item scattered field is subjected to time modulation while the antenna structure item scattered field is kept unchanged, so that the total scattered field of the antenna is dynamically regulated and controlled, and according to the Fourier series theory, the total scattered field is distributed in a spatial domain and a frequency domain, and the limitation that the traditional phased array can only regulate and control RCS in the spatial dimension is broken through. The circuit at the rear end of the antenna has a simple structure and is easy to design and realize.
Drawings
FIG. 1 is a topological schematic diagram of a technical solution of the present invention, wherein the rear end of each unit of an array antenna is sequentially connected with a four-dimensional T/R assembly, a 50 ohm coaxial line and a broadband load; the four-dimensional T/R component consists of a radio frequency switch, a phase shifter and an attenuator; the radio frequency switch is controlled by a field programmable gate array with a preloaded time sequence;
FIG. 2 is a schematic diagram of a four-dimensional T/R assembly including a radio frequency switch, a phase shifter and an attenuator;
FIG. 3 is a schematic diagram of a specific structure of an antenna unit and a back-end circuit, which establishes a reference plane S between the antenna unit and a port 1 of a four-dimensional T/R module1The reference plane looking to the left is the input impedance Z of the antennainThe reference surface is viewed to the right as the equivalent impedance Z of the back-end circuitn. Establishing a reference plane S between a four-dimensional T/R assembly port 2 and a 50 ohm coaxial line2The equivalent impedance of the reference surface looking to the right is Zm；
FIG. 4 is a time series diagram of each optimized unit in example 1, with the vertical axis representing the optimized tk,τk(k-1, 2, …,16) for period TpA normalized value of (d);
FIG. 5 is a four-dimensional antenna array center frequency f obtained by simulation in example 1 by substituting the timing sequence of FIG. 40And the first three sidebands f0+fp、f0+2fpAnd f0+3fpThe dual station RCS pattern of (a);
fig. 6 is a diagram of a two-station RCS directional diagram of a four-dimensional antenna array, a reference array 1 and a reference array 2 obtained by simulation by substituting the timing sequence in fig. 4 in embodiment 1;
FIG. 7 is a time series diagram of each optimized unit in example 2, and the vertical axis represents the optimized tk,τk(k-1, 2, …,16) for period TpA normalized value of (d);
FIG. 8 is a four-dimensional antenna array center frequency f obtained by simulation in example 2 by substituting the timing sequence of FIG. 70And the first three sidebands f0+fp、f0+2fpAnd f0+3fpThe single station RCS pattern;
fig. 9 is a single-station RCS directional diagram of the four-dimensional antenna array, reference array 1 and reference array 2 obtained by simulation by substituting the timing sequence in fig. 7 in embodiment 2.
Detailed description of the preferred embodiments
Taking a gradient slot antenna working at 10gHz as an example, the main polarization of the antenna is in the y direction, the main boundary condition and the auxiliary boundary condition are set along the y direction, and the structure term scattered field and the mode term scattered field of the antenna and the input impedance of the antenna are obtained through simulation. In fig. 1, the four-dimensional T/R assembly, the 50 ohm coaxial line and the RCS in the broadband load control band are connected in sequence behind each unit port of the antenna. In fig. 2, one of the antenna units is analyzed, and first, the length l of the coaxial line and the value Z of the broadband load are optimized according to the differential evolution algorithm and the formulas (8) to (10)l. And then, optimizing the scattering performance of the array by using the conduction time and duration of a switch connected with each unit as optimization variables and adopting a prediction method and a differential evolution algorithm to realize the scattering control in the specified threat airspace of the array antenna in band. The objective function is set to:
Figure BDA0003319793270000081
in the formula, σ4D、σonAnd σoffThe RCS of the four-dimensional array, the RCS of the reference array 1 and the RCS of the reference array 2, f, respectively, are the objective functions. w is a1And w2Respectively, representing the corresponding weighting coefficients.
Example 1: dual station RCS control of vertical incidence for 1 x 16 tapered slot antenna arrays
Specifically, when considering that the central frequency of the gradually-changed slot antenna is 10GHz, the distance between array elements is 10GHz corresponding half wavelength of free space, and the in-band co-polarized incident wave irradiates the array antenna along the direction of theta 0 degrees, the total RCS of the array antenna is optimally controlled by taking double station angles of-30 degrees and 30 degrees as main threat angle domains. The length of the coaxial line obtained through final optimization is 10mm, and the broadband load is 100 ohms. The time sequence of the individual units is shown in fig. 4. Fig. 5 shows a scattering directional diagram of the central frequency and the front third-order sidebands of the four-dimensional antenna array, which illustrates that time modulation can shift a part of scattering energy of the central frequency to the sidebands, thereby realizing the joint regulation of the spatial domain and the frequency domain of the RCS. As can be seen from fig. 6, the maximum RCS peak of the reference array 1 and the reference array 2 appears in the direction θ is 0 °, and for a combat carrier such as an airplane, the region near the direction is the airspace most easily intercepted by a detection radar, and is also the key angular range reduced by the RCS of the phased array antenna. By optimizing the time sequence of each unit, the RCS maximum reduction of the four-dimensional antenna array compared with a reference array 1 is 21dB, the minimum reduction is 3dB and the average reduction is 12dB within the range of a double standing angle of-30 degrees and 30 degrees; compared with the RCS of the reference array 2, the RCS has the maximum reduction amount of 24dB, the minimum reduction amount of 3dB and the average reduction amount of 11 dB. Meanwhile, two larger peak values are generated at positions of theta (58 degrees) and theta (56 degrees) outside the threat angle domain by the four-dimensional antenna array, which shows that the four-dimensional antenna array can shift the scattering peak value of the antenna out of the threat angle domain set before optimization, thereby achieving the purpose of suppressing scattering.
Example 2: oblique incidence single station RCS control of 1 x 16 gradient slot antenna array
Specifically, consider the RCS optimization problem of the array antenna with single station angle [ -10 °, 10 ° ] as the threat angle domain when the in-band co-polarized incident wave obliquely irradiates the array antenna along the yoz plane at the center frequency of 10 GHz. The coaxial line length and the broadband load were the same as in example 1. The time series of the respective units obtained by the final optimization is shown in fig. 7. Fig. 8 shows a scattering directional diagram of the central frequency and the front third sidebands of the four-dimensional antenna array, which illustrates that time modulation can shift a part of scattering energy of the central frequency to the sidebands to realize the joint regulation of the spatial domain and the frequency domain of the RCS. FIG. 9 shows a single-station RCS comparison of a four-dimensional antenna array and two reference arrays, wherein the maximum RCS reduction of the four-dimensional antenna array compared with the reference array 1 is 20dB, the minimum RCS reduction is 2dB, and the average RCS reduction is 7dB in the single-station angle range of-10 degrees and 10 degrees by optimizing the time sequence of each unit; the RCS of the comparison reference array 2 has the maximum reduction of 27dB, the minimum reduction of 2dB and the average reduction of 13 dB. The four-dimensional antenna array can significantly reduce the RCS of the array compared with a static array (a traditional phased array).
Two specific embodiments of the present invention have been described above, it being understood that these are presented by way of example only, and not limitation. It will, therefore, be apparent to persons skilled in the art that various changes in form and detail can be made therein without departing from the spirit and scope of the invention without the use of inventive faculty. All of which are considered to be within the scope of the present invention.

Claims (4)

1. An in-band scattering reduction structure based on a four-dimensional antenna array is characterized by comprising a four-dimensional array antenna unit, a four-dimensional T/R component, a 50-ohm coaxial line and a broadband load; the four-dimensional T/R component consists of a radio frequency switch, a phase shifter and an attenuator; the radio frequency switch is controlled by a field programmable gate array with a preloaded time sequence to generate periodic on-off; the antenna unit is connected with the four-dimensional T/R assembly firstly and then connected with the 50-ohm coaxial line, and the terminal is connected with the broadband load.
2. A method for controlling an in-band scattering reduction structure based on a four-dimensional antenna array as claimed in claim 1, comprising the steps of:
s1, establishing a periodic boundary condition of the four-dimensional array antenna unit based on electromagnetic full-wave simulation software, and separating a structural item RCS and a mode item RCS of the antenna unit; calculating a mode item RCS of the antenna unit when a switch is switched on and off after the rear end of the antenna is connected with circuits such as a four-dimensional T/R component and the like;
s2, estimating the total RCS of the array when all switches are switched on and off by using a method of multiplying the RCS by the scattering array factor of the array; for convenience of description, the array when all the switches are on is a reference array 1, the array when all the switches are off is a reference array 2, and both the arrays are static arrays, namely the traditional phased array; formula as in formula (1)
Figure FDA0003319793260000011
Wherein d is the array element spacing, θ0Denotes an electromagnetic wave incident direction, θ denotes an electromagnetic wave scattering direction, N denotes the number of antenna elements, β denotes a free space wave number (usually, β is 2 pi/λ, λ denotes a free space wavelength), and Z denotesonAnd ZoffThe equivalent impedance of the antenna back end circuit when the switch is switched on and off respectively;
Figure FDA0003319793260000012
and
Figure FDA0003319793260000013
the total scattered field of the antenna unit is respectively when the switch is switched on and off;
Figure FDA0003319793260000014
and
Figure FDA0003319793260000015
respectively estimating total scattering fields of a reference array 1 and a reference array 2;
s3, optimizing the central frequency RCS of the four-dimensional antenna array and the RCS of the side band according to a differential evolution algorithm;
Figure FDA0003319793260000016
Figure FDA0003319793260000017
Figure FDA0003319793260000018
e in the formula (2)stStructural terms RCS, E representing antenna elementsan(Zon) And Ean(Zoff) The antenna element mode term RCS when the switch is on and off respectively,
Figure FDA0003319793260000021
an RCS representing a center frequency; in the formula (3)
Figure FDA0003319793260000022
RCS representing mth order sidebands; t ispFor the modulation period of the switch, tkIs the starting time, tau, when the switch connected with the kth antenna unit is turned onkThe duration of the conduction of the switch connected with the kth antenna unit; formula (4) represents tkAnd τkThe constraint of (2).
3. The control method according to claim 2, characterized in that: the estimation method adopts an estimation approximation means of the unit RCS multiplied by the array scattering array factor when the scattering characteristics of the antenna are optimized, although the edge truncation effect of a limited large array is neglected and the result has a certain difference with the result in the real situation, the calculation amount can be saved, the calculation efficiency is improved, and the quick analysis of the scattering characteristics of the array antenna is favorably realized.
4. The control method according to claim 2, characterized in that: the time dimension degree of freedom of the four-dimensional antenna array is fully utilized, the impedance of the antenna rear-end circuit is dynamically regulated, the reflection coefficients of the antenna and the rear-end circuit are changed, the mode item RCS and the total RCS of the antenna are subjected to time modulation while the RCS of the antenna structure item is unchanged, the RCS of the antenna is finally controlled in a space domain and a frequency domain in a combined mode, the limitation that the traditional phased array can only regulate and control the distribution of the RCS in the space dimension is broken through, and the RCS of the array antenna is effectively reduced.
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CN111564702A (en) * 2020-04-14 2020-08-21 西安电子科技大学 Radar cross section reduction method and regulation and control system loaded on antenna array

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN114499580A (en) * 2022-01-25 2022-05-13 电子科技大学 Method for calculating signal coupling power of co-frequency full-duplex broadband phased array antenna
CN114499580B (en) * 2022-01-25 2022-10-11 电子科技大学 Method for calculating signal coupling power of co-frequency full-duplex broadband phased array antenna

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