CN113938048A - Control method and controller for turning on wave crests and wave troughs - Google Patents

Control method and controller for turning on wave crests and wave troughs Download PDF

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Publication number
CN113938048A
CN113938048A CN202111053955.XA CN202111053955A CN113938048A CN 113938048 A CN113938048 A CN 113938048A CN 202111053955 A CN202111053955 A CN 202111053955A CN 113938048 A CN113938048 A CN 113938048A
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tube
synchronous
comparison result
vin
main switching
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不公告发明人
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Mornsun Guangzhou Science and Technology Ltd
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Mornsun Guangzhou Science and Technology Ltd
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Priority to CN202111053955.XA priority Critical patent/CN113938048A/en
Publication of CN113938048A publication Critical patent/CN113938048A/en
Priority to PCT/CN2022/117716 priority patent/WO2023036220A1/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/66—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal
    • H02M7/68—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters
    • H02M7/72—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/79—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/797—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

The invention discloses a control method and a controller for turning on wave crests and wave troughs, which are applied to a synchronous rectification circuit, wherein the synchronous rectification circuit comprises a main switching tube, a synchronous rectification tube and an energy storage inductor, and the method comprises the following steps: obtaining the highest switching frequency limit finishing moment of the synchronous rectification circuit; comparing the voltages at the two ends of the energy storage inductor at the ending moment to obtain a comparison result signal; according to the working state of the synchronous rectification circuit and a preset condition, one of the following actions is selected to be executed: starting timing at the signal turning moment of the comparison result, and controlling the main switching tube to be switched on at the wave crest or the wave trough of the connection node of the main switching tube and the synchronous rectifier tube after the first preset time is finished; and starting timing at the signal turning moment of the comparison result, and controlling the synchronous rectifier tube to be switched on at the wave crest or the wave trough of the connection node of the main switch tube and the synchronous rectifier tube after the second preset time is ended. The invention can improve the power density and efficiency of the switch converter, reduce the volume and reduce the EMI and the cost.

Description

Control method and controller for turning on wave crests and wave troughs
Technical Field
The invention relates to a switching power supply, in particular to a method and a controller for controlling the turning-on of wave crests and wave troughs.
Background
With the development of power supply technology, a synchronous rectification circuit with high frequency, high efficiency and high power density has become a trend, a hard switching technology has large switching loss during high-frequency switching, reduces the efficiency of the circuit, and has a serious problem of electromagnetic interference, and to solve the problem, a soft switching technology is developed and gradually applied to a converter to reduce the switching loss and the EMI noise, and specifically, a Zero Voltage Switching (ZVS) technology is mainly used to realize zero voltage switching of an MOS transistor.
Take a quasi-resonant flyback circuit as an example: the main switching tube is switched on at the wave trough of resonance of the primary inductance of the transformer and the parasitic capacitance of the main switching tube, ZVS switching-on of the main switching tube can be realized, the primary inductance of the transformer is large, so the resonance period is long, the control circuit has enough time to realize detection from the wave trough, and the main switching tube is switched on from internal logic processing to the wave trough.
However, for the synchronous rectification circuits shown in fig. 1a and 1b, where fig. 1 is a step-down synchronous rectification circuit, fig. 1b is a step-up synchronous rectification circuit, when the switching frequency is high, such as greater than 500KHz, the synchronous rectification circuit operates in the discontinuous mode and the energy storage inductor L1 completes demagnetization, the energy storage inductor L1 starts to resonate with the parasitic capacitors of the switching tube Q1 and the switching tube Q2, the resonant frequency reaches about 10MHz, peak or trough detection is performed at such a high resonant frequency, and the switching tube is turned on at the peak or trough to achieve ZVS turn-on of the switching tube, which puts extremely high requirements on the performance of the controller and the parameter matching of the power circuit, and no document or product exists at present to achieve this function.
Disclosure of Invention
In view of the above, the technical problems solved by the present invention are: a wave crest and trough turn-on controller and a control method are provided to ensure that a main switch tube and a synchronous rectifier tube are just turned on at a wave crest or a trough when a switching power supply adopting a synchronous rectification technology works in an intermittent mode, realize ZVS turn-on, reduce EMI and improve the efficiency of the switching power supply.
In order to solve the technical problems, the invention adopts the following technical scheme:
aiming at the application scene of the synchronous rectification circuit, the technical scheme of the method for controlling the opening of the wave peak and the wave trough provided by the invention is as follows:
a control method for turning on wave crest and trough is applied to a synchronous rectification circuit, the synchronous rectification circuit comprises a main switch tube, a synchronous rectification tube and an energy storage inductor, and the control method is characterized by comprising the following steps:
obtaining the highest switching frequency limit finishing moment of the synchronous rectification circuit;
comparing the voltages at two ends of the energy storage inductor at the ending moment to obtain a comparison result signal;
according to the working state of the synchronous rectification circuit and a preset condition, one of the following actions is selected and executed:
starting timing at the signal turning moment of the comparison result, and controlling the main switching tube to be switched on at the wave crest or the wave trough of the connection node of the main switching tube and the synchronous rectifier tube after first preset time is finished;
and starting timing at the signal turning moment of the comparison result, and controlling the synchronous rectifier tube to be switched on at the wave crest or the wave trough of the connection node of the main switch tube and the synchronous rectifier tube after the second preset time is finished.
Preferably, the highest switching frequency limit end time of the synchronous rectification circuit is obtained by a limit timer.
Preferably, the comparator compares voltages at two ends of the energy storage inductor to obtain the comparison result signal.
Preferably, the first predetermined time is obtained by a first timer that is enabled by a rising edge of the comparison result signal or enabled by a falling edge of the comparison result signal.
Preferably, the second predetermined time is obtained by a second timer, which is enabled by a rising edge of the comparison result signal or by a falling edge of the comparison result signal.
Further, when the working state of the synchronous rectification circuit is voltage reduction, the predetermined condition is as follows:
when Vin-Vth < ═ 2 Vo, selecting the main switching tube to be switched on at the peak of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is ended;
when Vin-Vth >2 Vo, selecting the synchronous rectifier tube to be switched on at the wave trough of the connection node of the main switch tube and the synchronous rectifier tube after the second preset time is finished;
vin is the input voltage of the synchronous rectification circuit, Vo is the output voltage of the synchronous rectification circuit, and Vth is a set voltage greater than or equal to 0V.
Further, when the operating state of the synchronous rectification circuit is boosting, the predetermined condition is:
when 2 Vin-Vth ═ Vo, selecting the main switching tube to be switched on at the wave trough of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is ended;
when 2 Vin-Vth > Vo, selecting the synchronous rectifying tube to be switched on at the peak of the connection node of the main switching tube and the synchronous rectifying tube after the second preset time is ended;
vin is the input voltage of the synchronous rectification circuit, Vo is the output voltage of the synchronous rectification circuit, and Vth is a set voltage greater than or equal to 0V.
Aiming at the application scene of the diode rectifying circuit, the technical scheme of the method for controlling the turning-on of the wave peak and the wave trough provided by the invention is as follows:
a control method for turning on wave crests and wave troughs is applied to a diode rectifying circuit, the diode rectifying circuit comprises a main switching tube, a rectifying diode and an energy storage inductor, and the control method is characterized by comprising the following steps:
obtaining the highest switching frequency limit finishing moment of the diode rectifying circuit;
comparing the voltages at two ends of the energy storage inductor at the ending moment to obtain a comparison result signal;
and starting timing at the signal turning moment of the comparison result, and controlling the main switching tube to be switched on at the wave crest of a connection node of the main switching tube and the synchronous rectifier tube after first preset time is finished according to the working state of the diode rectifier circuit and preset conditions.
Preferably, the highest switching frequency limit end time of the diode rectifying circuit is obtained through a frequency limit timer; comparing the voltages at two ends of the energy storage inductor through a comparator to obtain a comparison result signal; the first predetermined time is obtained by a first timer which is enabled by a rising edge of the comparison result signal or by a falling edge of the comparison result signal.
Further, when the working state of the diode rectifier circuit is voltage reduction, the predetermined condition is that:
when Vin-Vth < ═ 2 Vo, the main switching tube is switched on at the peak of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is ended;
vin is the input voltage of the diode rectifying circuit, Vo is the output voltage of the diode rectifying circuit, and Vth is a set voltage greater than or equal to 0V.
Further, when the operating state of the diode rectifier circuit is boosting, the predetermined condition is:
when 2 Vin-Vth ═ Vo, the main switching tube is switched on at the wave trough of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is finished;
vin is the input voltage of the diode rectifying circuit, Vo is the output voltage of the diode rectifying circuit, and Vth is a set voltage greater than or equal to 0V.
Aiming at the application scene of the synchronous rectification circuit, the technical scheme of the wave crest and trough switching-on controller provided by the invention is as follows:
the utility model provides a crest and trough turn-on controller, is applied to synchronous rectifier circuit, synchronous rectifier circuit include main switch tube, synchronous rectifier tube and energy storage inductance, its characterized in that, crest and trough turn-on control method, including the following unit:
the trigger unit is used for acquiring the highest switching frequency limit finishing time of the synchronous rectification circuit;
the comparison unit is used for comparing the voltages at the two ends of the energy storage inductor at the end moment to obtain a comparison result signal;
the execution unit is used for selecting and executing one of the following actions according to the working state of the synchronous rectification circuit and a preset condition:
starting timing at the signal turning moment of the comparison result, and controlling the main switching tube to be switched on at the wave crest or the wave trough of the connection node of the main switching tube and the synchronous rectifier tube after first preset time is finished;
and starting timing at the signal turning moment of the comparison result, and controlling the synchronous rectifier tube to be switched on at the wave crest or the wave trough of the connection node of the main switch tube and the synchronous rectifier tube after the second preset time is finished.
Preferably, the triggering unit obtains the highest switching frequency limit end time of the synchronous rectification circuit through a frequency limit timer.
Preferably, the comparison unit compares the voltages at two ends of the energy storage inductor through a comparator to obtain the comparison result signal.
Preferably, the execution unit obtains the first predetermined time through a first timer, and the first timer is enabled by a rising edge of the comparison result signal or enabled by a falling edge of the comparison result signal.
Preferably, the execution unit obtains the second predetermined time through a second timer, and the second timer is enabled by a rising edge of the comparison result signal or is enabled by a falling edge of the comparison result signal.
Further, when the working state of the synchronous rectification circuit is voltage reduction, the predetermined condition is as follows:
when Vin-Vth < ═ 2 Vo, selecting the main switching tube to be switched on at the peak of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is ended;
when Vin-Vth >2 Vo, selecting the synchronous rectifier tube to be switched on at the wave trough of the connection node of the main switch tube and the synchronous rectifier tube after the second preset time is finished;
vin is the input voltage of the synchronous rectification circuit, Vo is the output voltage of the synchronous rectification circuit, and Vth is a set voltage greater than or equal to 0V.
Further, when the operating state of the synchronous rectification circuit is boosting, the predetermined condition is:
when 2 Vin-Vth ═ Vo, selecting the main switching tube to be switched on at the wave trough of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is ended;
when 2 Vin-Vth > Vo, selecting the synchronous rectifying tube to be switched on at the peak of the connection node of the main switching tube and the synchronous rectifying tube after the second preset time is ended;
vin is the input voltage of the synchronous rectification circuit, Vo is the output voltage of the synchronous rectification circuit, and Vth is a set voltage greater than or equal to 0V.
Aiming at the application scene of the diode rectifying circuit, the technical scheme of the peak-valley switching-on controller provided by the invention is as follows:
the utility model provides a crest and trough turn-on controller, is applied to diode rectifier circuit, diode rectifier circuit include main switch tube, rectifier diode and energy storage inductance, its characterized in that, crest and trough turn-on controller, include following unit:
the trigger unit is used for obtaining the highest switching frequency limit finishing time of the diode rectifying circuit;
the comparison unit is used for comparing the voltages at the two ends of the energy storage inductor at the end moment to obtain a comparison result signal;
and the execution unit starts timing at the signal turning moment of the comparison result, and controls the main switching tube to be switched on at the wave crest or the wave trough of the connection node of the main switching tube and the synchronous rectifier tube after first preset time according to the working state of the diode rectifier circuit and preset conditions.
Preferably, the triggering unit obtains the highest switching frequency limit end time of the diode rectifying circuit through a frequency limit timer; the comparison unit compares the voltages at two ends of the energy storage inductor through a comparator to obtain a comparison result signal; the execution unit obtains the first predetermined time through a first timer, and the first timer is enabled by a rising edge of the comparison result signal or is enabled by a falling edge of the comparison result signal.
Further, when the operating state of the diode rectifier circuit is step-down, the predetermined condition is:
when Vin-Vth < ═ 2 Vo, the main switching tube is switched on at the peak of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is ended;
vin is the input voltage of the diode rectifying circuit, Vo is the output voltage of the diode rectifying circuit, and Vth is a set voltage greater than or equal to 0V.
Further, when the operating state of the diode rectifier circuit is boosting, the predetermined condition is:
when 2 Vin-Vth ═ Vo, the main switching tube is switched on at the wave trough of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is finished;
vin is the input voltage of the diode rectifying circuit, Vo is the output voltage of the diode rectifying circuit, and Vth is a set voltage greater than or equal to 0V.
Compared with the prior art, the invention has the following beneficial effects:
each period of a voltage Vs resonance waveform at one end of an energy storage inductor of the rectification circuit is kept unchanged, and the characteristic that resonance is carried out by taking the voltage at the other end of the energy storage inductor as a center is utilized, wave crest or wave trough detection is not directly carried out, but the voltages at two ends of the energy storage inductor are compared at the moment when the highest switching frequency limitation of the rectification circuit is finished, and the conduction of a switching tube in the rectification circuit is controlled by using a comparison result signal, so that the rectification circuit works in an intermittent mode, ZVS (zero voltage switch) opening can be realized at the wave crest or the wave trough of high-frequency resonance of a connection node of a main switching tube and the rectification tube, the efficiency is improved, and EMI (electro-magnetic interference) noise is reduced.
Drawings
FIG. 1a is a schematic diagram of a conventional buck synchronous rectifier circuit;
FIG. 1b is a schematic diagram of a conventional boost synchronous rectification circuit;
FIG. 2 is a schematic diagram of the application of the peak-to-valley open-circuit controller of the present invention in a synchronous rectification circuit;
fig. 3 is a timing chart of the synchronous rectification circuit according to the first embodiment of the present invention operating in the peak-on mode;
FIG. 4 is a timing diagram of FIG. 3 at a partial enlargement of the time axis according to the present invention;
FIG. 5 is a schematic diagram of a first internal circuit of the peak-to-valley turn-on controller of the present invention (the timers share the same comparator output enable signal);
fig. 6 is a timing chart of the synchronous rectification circuit according to the first embodiment of the present invention operating in the valley on mode;
FIG. 7 is a schematic diagram of a second internal circuit of the peak-to-valley turn-on controller of the present invention (the comparator outputs a rising edge enable signal and a falling edge enable signal to enable the timer, respectively);
FIG. 8 is a schematic diagram of a third internal circuit of the peak-to-valley power-on controller of the present invention (the enable signals for the timers are from respective comparators);
FIG. 9 is a schematic diagram of a fourth internal circuit of the peak-to-valley switching controller according to the present invention (only the switching on of the peak or the valley of the main switching tube is realized);
FIG. 10 is a schematic diagram of a fifth internal circuit of the peak-to-valley open-loop controller according to the present invention (only the peak or valley of the synchronous rectifier is opened);
fig. 11 is a timing chart of the synchronous rectification circuit according to the second embodiment of the present invention operating in the valley on mode;
fig. 12 is a timing chart of the synchronous rectification circuit according to the second embodiment of the present invention operating in the peak-on mode;
the drawings described above do not limit the scope of the inventive concept but illustrate it to those skilled in the art by reference to specific embodiments.
Detailed Description
Fig. 2 is a schematic diagram of an application of the peak-to-valley open-circuit controller of the present invention in a synchronous rectification circuit, where the synchronous rectification circuit includes a first voltage transmission port P1, a second voltage transmission port P2, a ground port GND switch Q1, a switch Q2, and an energy storage inductor L1;
the drain of the switching tube Q1 is used for connecting the first voltage transmission port P1, the source of the switching tube Q1 is simultaneously connected with the drain of the switching tube Q2 and one end of the energy storage inductor L1, the other end of the energy storage inductor L1 is used for connecting the second voltage transmission port P2, and the source of the switching tube Q2 is used for connecting the ground port GND;
when the synchronous rectification circuit works at a step-down state, the first voltage transmission port P1 is a port for receiving an input voltage Vin, the second voltage transmission port P2 is a port for outputting a regulated voltage Vo, the main switch tube is a switch tube Q1, and the synchronous rectification tube is a switch tube Q2;
when the synchronous rectification circuit works in boosting, the second voltage transmission port P2 is a port for receiving the input voltage Vin, the first voltage transmission port P1 is a port for outputting the regulated voltage Vo, the main switch tube is a switch tube Q2, and the synchronous rectification tube is a switch tube Q1.
The wave crest and trough switching-on controller is integrated in a control IC of the synchronous rectification circuit and at least comprises a comparator and a timer, the wave crest and trough switching-on controller compares voltages obtained by sampling two ends of the energy storage inductor L1 through the comparator at the moment of finishing the limitation of the highest switching frequency of the synchronous rectification circuit, the timer is enabled at the moment of rising or falling edge of an output signal of the comparator, and the soft switching-on of a main switching tube or the synchronous rectification tube can be realized at the wave crest or trough of one end Vs of the energy storage inductor L1 when the timing of the timer is finished.
Coss1 and Coss2 in fig. 2 are parasitic output capacitances of the switching tube Q1 and the switching tube Q2, respectively, and are separately drawn for convenience of description.
After the energy storage inductor L1 of the synchronous rectification circuit completes demagnetization, the energy storage inductor L1 starts to resonate with the parasitic capacitor Coss1 of the switching tube Q1 and the parasitic capacitor Coss2 of the switching tube Q2, because the resonant frequency of the voltage Vs at one end of the energy storage inductor L1 is high and the resonant frequency is high, and the voltage Vs at the other end of the energy storage inductor L1 is lowThe invention utilizes the characteristic that each period of a voltage Vs resonance waveform at one end of an energy storage inductor L1 is kept unchanged and resonance is carried out by taking the voltage at the other end of the energy storage inductor L1 as the center, peak or trough detection is not directly carried out, a peak and trough turn-on controller compares the voltages at two ends of the energy storage inductor L1 through a comparator at the time of finishing the limitation of the highest switching frequency of a synchronous rectification circuit, a timer is enabled at the rising or falling edge time of an output signal of the comparator, the timing time of the timer is superposed with the sampling of the peak and trough turn-on controller, and all delays of comparison, logic processing, driving and the like are all delays
Figure BDA0003253644110000071
(n is an integer greater than or equal to zero, T is a resonance period), the timing time of the timer can be set through an external pin of the wave crest and wave trough switching-on controller, and can also be burnt into the control IC in a digital circuit mode. When the timer finishes timing, a main switching tube or a synchronous rectifier tube can be switched on at the wave crest or the wave trough of the voltage Vs resonance at one end of the energy storage inductor L1, so that the soft switching-on of the switching tube is realized.
In order to make the objects, technical solutions and advantages of the present application more clear, the present application will be further described in detail with reference to the accompanying drawings.
First embodiment
The synchronous rectification circuit of this embodiment works in a step-down state, the main switch tube is the switch tube Q1, the synchronous rectification tube is the switch tube Q2, in this embodiment, when the input voltage Vin, the output voltage Vo and the threshold voltage Vth satisfy the following relation: when Vin-Vth is 2 Vo, after the energy storage inductor L1 of the synchronous rectification circuit completes demagnetization, the peak-valley open controller opens the main switching tube Q1 at the peak of Vs resonance; when the input voltage Vin, the output voltage Vo, and the threshold voltage Vth satisfy the relation: when Vin-Vth >2 Vo, after the energy storage inductor L1 of the synchronous rectification circuit completes demagnetization, the wave crest and wave trough opening controller opens the synchronous rectification tube Q2 at the wave trough of Vs resonance; the threshold voltage Vth has a value equal to or greater than zero volts.
FIG. 3 shows a first embodiment of the present inventionReferring to fig. 3, a Timer in fig. 3 is an output waveform of a frequency-limiting Timer for limiting a highest switching frequency of the synchronous rectification circuit, and the frequency-limiting Timer is enabled when the main switch Q1 is turned on. Vgs1Is the control signal waveform of the grid of the main switch tube Q1, Vgs2Control signal waveform i of gate of synchronous rectifier Q2L1Is the current waveform, V, flowing through the energy storage inductor L1SIs the voltage waveform of the terminal Vs of the energy storage inductor L1.
The voltage range of Vin is 18V to 75V, the Vin voltage is 30V, the Vo voltage is 12V, and the threshold voltage Vth is 10V, which are referred to as an operating state 1, the synchronous rectifier Q2 is turned off when demagnetization of the energy storage inductor L1 is finished at time t3, the energy storage inductor L1, the parasitic capacitor Coss1 and the parasitic capacitor Coss2 resonate around the output voltage Vo, theoretically, the lowest voltage of the resonance is 0V, the highest voltage is 2 Vo, and the maximum resonant voltage 2 Vo of Vs at one end of the energy storage inductor L1 is greater than Vin-Vth because Vin-Vth < >2 Vo under the operating state, which is defined in a broad sense implemented by the soft switch: when the resonant maximum voltage of Vs at one end of the energy storage inductor L1 reaches Vin or is lower than Vin by a smaller threshold voltage Vth (Vth greater than or equal to 0V), the main switching transistor Q1 is turned on, and it can be considered that the main switching transistor Q1 realizes soft turn-on.
FIG. 3 shows the synchronous rectification circuit in the working state 1, from t0To t0+ T the specific working process within one working period T is as follows:
stage t 0-t 1: also called as an excitation stage, the main switch tube Q1 is turned on at the moment of t0, the frequency limiting Timer starts to time, the voltage at two ends of the energy storage inductor L1 is equal to the difference between the input voltage Vin and the output voltage Vo, and the current i of the energy storage inductor L1L1With a slope
Figure BDA0003253644110000081
And (4) rising.
Stage t 1-t 2: at time t1, the main switch tube Q1 is turned off, and the current i of the energy storage inductor L1L1The parasitic capacitor Coss1 of the main switch tube Q1 is charged, the parasitic capacitor Coss2 of the synchronous rectifier tube Q2 is discharged, and the voltage of one end Vs of the energy storage inductor L1 is equal to the voltage of the outputThe input voltage Vin is reduced to 0V, and the synchronous rectifier Q2 realizes ZVS switching at time t 2.
Stage t 2-t 3: also called the demagnetization phase, current i of the storage inductor L1L1With a slope
Figure BDA0003253644110000082
Current i of the energy storage inductor L1 is reducedL1And (4) reducing to zero at the time t3, ending demagnetization, turning off the synchronous rectifier tube Q2 at the moment, and enabling the demagnetization ending time t3 to be earlier than the end time t' of the frequency limiting timer.
Stage T3-T0 + T: also called as a resonance stage, in order to describe the resonance stage in more detail, the resonance stage is enlarged according to a time axis to obtain fig. 4, please refer to fig. 4, the voltage at one end Vs of the energy storage inductor L1 starts to resonate from the time T3, fig. 5 is a schematic diagram of a first internal circuit of the peak-to-valley turn-on controller of the present invention, please refer to fig. 5, the voltage at two ends of the energy storage inductor L1 is compared from the time T' when the Timer of the frequency limiting Timer ends, the voltage at Vs starts to change from being greater than Vo to being less than Vo at the time f, the output voltage of the comparator starts to turn over, the first Timer is enabled at the rising edge time of the output signal of the comparator, the first Timer in fig. 5 ends at the time T0+ T and turns on the main switching tube Q1 at the peak of Vs resonance, soft Vth on of the main switching tube Q1 is realized, and the Timer enable selection module in fig. 5 is based on the formula Vin-to-Vth<Vo determines that the rising edge of the comparator output signal can only enable the first timer, and from time f to time T0+ T may be as in fig. 4
Figure BDA0003253644110000083
Or can be
Figure BDA0003253644110000084
Figure BDA0003253644110000085
Or
Figure BDA0003253644110000086
And the like.
The cycle is ended and the next duty cycle is started and the above stages are repeated.
The other conditions of the operating state 1 are not changed, and only the Vin voltage is increased to 60V, which is referred to as an operating state 2, the timer enabling selection module in fig. 5 determines that only the second timer can be enabled at the rising edge time of the comparator output signal according to the operating condition that Vin-Vth >2 Vo, and the synchronous rectifier Q2 is turned on at the trough of Vs resonance, so that the synchronous rectifier Q2 is turned on softly.
Fig. 6 is a timing diagram illustrating the synchronous rectification circuit according to the first embodiment of the present invention operating in the valley-powered mode, please refer to fig. 6, where fig. 6 illustrates a specific working process of the working state 2 in a working period T, as follows:
the operation process from the t0 stage to the t3 stage is the same as that of the operation state 1.
Stage t 3-t 4: referring to fig. 5, the voltage across the energy storage inductor L1 starts to be compared from the end time t' of the Timer of the frequency limiting Timer, the voltage across the energy storage inductor L1 starts to resonate at the voltage Vs, at the time f, the voltage Vs starts to change from being greater than Vo to being smaller than Vo, the output voltage of the comparator in fig. 5 starts to invert, the second Timer is enabled at the rising edge time of the output signal of the comparator, the second Timer ends at the time t4, the synchronous rectifier Q2 is turned on at the trough of the Vs resonance, the soft turn-on of the synchronous rectifier Q2 is realized, and the time from the time f to the time t4 may be the time in fig. 6
Figure BDA0003253644110000091
Or can be
Figure BDA0003253644110000092
Or
Figure BDA0003253644110000093
And the like.
Stage t 4-t 5: also called reverse phase, current i of the energy storage inductor L1L1With a slope
Figure BDA0003253644110000094
Decreasing from zero to a negative current, the synchronous rectifier Q2 is turned off at time t 5.
Stage T5-T0 + T: the output voltage Vo is discharged to a parasitic capacitor Coss1 of the main switching tube Q1 through an energy storage inductor L1, the parasitic capacitor Coss2 of the synchronous switching tube Q2 is charged, the voltage of one end Vs of an energy storage inductor L1 is larger than Vin-Vth at the moment of T0+ T, and ZVS on of the main switching tube Q1 is achieved.
The cycle is ended and the next duty cycle is started and the above stages are repeated.
In addition to the connection form of fig. 5, the internal circuit schematic diagram of the peak-valley open-circuit controller also has the connection forms of fig. 7 to 10, the connection relations of the positive and negative input ends of the comparators can be exchanged, the rising edge enable and the falling edge enable of the output signals of the comparators can be exchanged, only the control logic needs to be slightly modified, because the connection relations and the logic relations of the internal circuit schematic diagram of the peak-valley open-circuit controller are very many, in the embodiment of the present invention, the description is not needed, and only the simple difference description is made on fig. 7 to 10 below:
the first timer and the second timer in fig. 5 use the same comparator output enable signal, the first timer and the second timer in fig. 7 use opposite comparator output enable signals, the first timer and the second timer in fig. 8 use independent comparator output enable signals, and fig. 9 and 10 can only realize the soft-on of the peak or the valley of the main switch Q1 or the synchronous rectifier Q2.
Second embodiment
The synchronous rectification circuit of the present embodiment operates in a boost state, the main switch is a switch Q2, and the synchronous rectification circuit is a switch Q1, which will be mainly described below with respect to the differences from the first embodiment.
In this embodiment, when the input voltage Vin, the output voltage Vo, and the threshold voltage Vth satisfy the following relation: when Vin-Vth ═ Vo is 2, the operating state is called as 3, and after the demagnetization of the energy storage inductor L1 of the synchronous rectification circuit is finished, the peak and trough switching-on controller switches on the main switching tube Q2 at the trough of Vs resonance; when the input voltage Vin, the output voltage Vo, and the threshold voltage Vth satisfy the relation: when 2 Vin-Vth > Vo is called as a working state 4, after the demagnetization of the energy storage inductor L1 of the synchronous rectification circuit is finished, the wave crest and wave trough open-close controller opens the synchronous rectification tube Q1 at the wave crest of Vs resonance; the threshold voltage Vth has a value equal to or greater than zero volts.
FIG. 11 is a timing diagram illustrating a synchronous rectification circuit operating in a valley-powered mode according to a second embodiment of the present invention, referring to FIG. 11, FIG. 11 illustrates the synchronous rectification circuit operating in a boost mode and 2 × Vin-Vth<When Vo is equal to t, from t0To t0+ T the specific working process within one working period T is as follows:
stage t 0-t 1: also called as an excitation stage, the main switch tube Q2 is conducted at the time of t0, the frequency limiting Timer starts to time, and the current i of the energy storage inductor L1L1With a slope
Figure BDA0003253644110000101
And (4) rising.
Stage t 1-t 2: at time t1, the main switch tube Q2 is turned off, and the current i of the energy storage inductor L1L1The parasitic capacitor Coss2 of the main switch tube Q2 is charged, the parasitic capacitor Coss1 of the synchronous rectifier tube Q1 is discharged, the voltage of one end Vs of the energy storage inductor L1 rises from 0V to the output voltage Vo, and the synchronous rectifier tube Q1 realizes ZVS switching-on at the time t 2.
Stage t 2-t 3: also called the demagnetization phase, the voltage across the storage inductor L1 is equal to the output voltage Vo minus the input voltage Vin, and the current i of the storage inductor L1L1With a slope
Figure BDA0003253644110000102
Current i of the energy storage inductor L1 is reducedL1And (4) reducing to zero at the time t3, ending demagnetization, turning off the synchronous rectifier tube Q1 at the moment, and enabling the demagnetization ending time t3 to be earlier than the end time t' of the frequency limiting timer.
Stage T3-T0 + T: also called a resonance stage, from the time t3, the voltage at the end Vs of the energy storage inductor L1 starts to resonate, the schematic diagram of the internal circuit of the peak-to-valley open-circuit controller can be shown in fig. 5, referring to fig. 5, taking fig. 5 as an example to explain any one of fig. 7, fig. 8 and fig. 9, the voltage across the energy storage inductor L1 is compared from the end time t' of the Timer of the frequency limiting Timer, at time f, the Vs voltage begins to change from greater than Vin to less than Vin, the output voltage of the comparator begins to flip, enabling the first timer at the rising edge time of the output signal of the comparator, wherein the first timer finishes timing at the time T0+ T in FIG. 5 and turns on the main switch tube Q2 at the trough of the Vs resonance, thereby realizing the soft turn-on of the main switch tube Q2, the timer enable selection module in fig. 5 determines that only the first timer can be enabled at the rising edge of the output signal of the comparator according to formula 2 Vin-Vth < ═ Vo.
The cycle is ended and the next duty cycle is started and the above stages are repeated.
Fig. 2 shows that when the synchronous rectification circuit operates at a boosted voltage and Vin-Vth >2 Vo, the timer enable selection module in fig. 5 determines that only the second timer can be enabled at the rising edge time of the output signal of the comparator according to the relation Vin-Vth >2 Vo, and turns on the synchronous rectification tube Q2 at the peak of Vs resonance, so as to realize soft turn-on of the synchronous rectification tube Q2, corresponding to the operating state 4.
Fig. 12 is a timing chart of the synchronous rectification circuit according to the second embodiment of the present invention operating in the peak-on mode, please refer to fig. 12, fig. 12 shows a specific working process of the working state 4 in a working period T, as follows:
the working process of the t 0-t 3 stage is the same as that of the t 0-t 3 stage in the working state 3.
Stage t 3-t 4: also called a resonant phase, starting from time t3, the voltage at one end Vs of the energy storage inductor L1 starts to resonate, the schematic diagram of the internal circuit of the peak-to-valley open-circuit controller can be any one of fig. 5, fig. 7, fig. 8, and fig. 10, and is now described by taking fig. 5 as an example, please refer to fig. 5, comparing the voltage at two ends of the energy storage inductor L1 from the timing end time t' of the frequency limiting Timer, starting to change the voltage from less than Vin to greater than Vin at time e, starting to turn over the output voltage of the comparator in fig. 5 to generate a falling edge signal, but the Timer described in fig. 5 only recognizes the rising edge, so the Timer does not operate, starting to change the voltage Vs from greater than Vin to less than Vin at time f, starting to turn over the output voltage of the comparator in fig. 5, enabling the second Timer at the rising edge time of the output signal of the comparator, ending at time t4, turning on the synchronous rectifier Q1 at the peak of Vs resonance, and soft switching-on of the synchronous rectifier Q1 is realized.
Stage t 4-t 5: also called reverse phase, current i of the energy storage inductor L1L1With a slope
Figure BDA0003253644110000111
Decreasing from zero to a negative current, the synchronous rectifier Q1 is turned off at time t 5.
Stage T5-T0 + T: the energy storage inductor L1 discharges the parasitic capacitor Coss2 of the main switching tube Q2 and charges the parasitic capacitor Coss1 of the synchronous switching tube Q1, and the voltage of one end Vs of the energy storage inductor L1 is smaller than Vth at the time of T0+ T, so that ZVS on of the main switching tube Q2 is achieved.
The cycle is ended and the next duty cycle is started and the above stages are repeated.
It should be noted that the present invention is also applicable to a diode rectifier circuit, that is, the synchronous rectifier tube in fig. 2 is replaced by a diode, only the main switching tube needs to be controlled at this time, the corresponding circuit structure of the controller may be deleted, or may not be deleted, but the related pin is suspended, pulled high, or pulled low, and the like.
The above embodiments should not be construed as limiting the present invention, and the scope of the present invention should be determined by the scope of the appended claims. It will be apparent to those skilled in the art that many equivalent substitutions, modifications and alterations can be made without departing from the spirit and scope of the invention, and further that the circuit can be fine-tuned by simple series-parallel connection of devices according to application, and such modifications and alterations should also be considered as the scope of the invention.

Claims (22)

1. A control method for turning on wave crest and trough is applied to a synchronous rectification circuit, the synchronous rectification circuit comprises a main switch tube, a synchronous rectification tube and an energy storage inductor, and the control method is characterized by comprising the following steps:
obtaining the highest switching frequency limit finishing moment of the synchronous rectification circuit;
comparing the voltages at two ends of the energy storage inductor at the ending moment to obtain a comparison result signal;
according to the working state of the synchronous rectification circuit and a preset condition, one of the following actions is selected and executed:
starting timing at the signal turning moment of the comparison result, and controlling the main switching tube to be switched on at the wave crest or the wave trough of the connection node of the main switching tube and the synchronous rectifier tube after first preset time is finished;
and starting timing at the signal turning moment of the comparison result, and controlling the synchronous rectifier tube to be switched on at the wave crest or the wave trough of the connection node of the main switch tube and the synchronous rectifier tube after the second preset time is finished.
2. The method according to claim 1, wherein: and obtaining the highest switching frequency limit end time of the synchronous rectification circuit through a frequency limit timer.
3. The method according to claim 1, wherein: and comparing the voltages at two ends of the energy storage inductor through a comparator to obtain the comparison result signal.
4. The method according to claim 1, wherein: the first predetermined time is obtained by a first timer which is enabled by a rising edge of the comparison result signal or by a falling edge of the comparison result signal.
5. The method according to claim 1, wherein: the second predetermined time is obtained by a second timer that is enabled by a rising edge of the comparison result signal or by a falling edge of the comparison result signal.
6. The method according to any one of claims 1 to 5, wherein: when the working state of the synchronous rectification circuit is voltage reduction, the preset conditions are as follows:
when Vin-Vth < ═ 2 Vo, selecting the main switching tube to be switched on at the peak of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is ended;
when Vin-Vth >2 Vo, selecting the synchronous rectifier tube to be switched on at the wave trough of the connection node of the main switch tube and the synchronous rectifier tube after the second preset time is finished;
vin is the input voltage of the synchronous rectification circuit, Vo is the output voltage of the synchronous rectification circuit, and Vth is a set voltage greater than or equal to 0V.
7. The method according to any one of claims 1 to 5, wherein: when the working state of the synchronous rectification circuit is boosting, the preset conditions are as follows:
when 2 Vin-Vth ═ Vo, selecting the main switching tube to be switched on at the wave trough of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is ended;
when 2 Vin-Vth > Vo, selecting the synchronous rectifying tube to be switched on at the peak of the connection node of the main switching tube and the synchronous rectifying tube after the second preset time is ended;
vin is the input voltage of the synchronous rectification circuit, Vo is the output voltage of the synchronous rectification circuit, and Vth is a set voltage greater than or equal to 0V.
8. A control method for turning on wave crests and wave troughs is applied to a diode rectifying circuit, the diode rectifying circuit comprises a main switching tube, a rectifying diode and an energy storage inductor, and the control method is characterized by comprising the following steps:
obtaining the highest switching frequency limit finishing moment of the diode rectifying circuit;
comparing the voltages at two ends of the energy storage inductor at the ending moment to obtain a comparison result signal;
and starting timing at the signal turning moment of the comparison result, and controlling the main switching tube to be switched on at the wave crest of a connection node of the main switching tube and the synchronous rectifier tube after first preset time is finished according to the working state of the diode rectifier circuit and preset conditions.
9. The method according to claim 8, wherein: obtaining the highest switching frequency limit finishing moment of the diode rectifying circuit through a frequency limit timer; comparing the voltages at two ends of the energy storage inductor through a comparator to obtain a comparison result signal; the first predetermined time is obtained by a first timer which is enabled by a rising edge of the comparison result signal or by a falling edge of the comparison result signal.
10. The method according to any one of claims 8 to 9, wherein: when the working state of the diode rectifying circuit is voltage reduction, the preset conditions are as follows:
when Vin-Vth < ═ 2 Vo, the main switching tube is switched on at the peak of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is ended;
vin is the input voltage of the diode rectifying circuit, Vo is the output voltage of the diode rectifying circuit, and Vth is a set voltage greater than or equal to 0V.
11. The method according to any one of claims 8 to 9, wherein: when the working state of the diode rectifying circuit is boosting, the preset conditions are as follows:
when 2 Vin-Vth ═ Vo, the main switching tube is switched on at the wave trough of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is finished;
vin is the input voltage of the diode rectifying circuit, Vo is the output voltage of the diode rectifying circuit, and Vth is a set voltage greater than or equal to 0V.
12. The utility model provides a crest and trough turn-on controller, is applied to synchronous rectifier circuit, synchronous rectifier circuit include main switch tube, synchronous rectifier tube and energy storage inductance, its characterized in that, crest and trough turn-on control method, including the following unit:
the trigger unit is used for acquiring the highest switching frequency limit finishing time of the synchronous rectification circuit;
the comparison unit is used for comparing the voltages at the two ends of the energy storage inductor at the end moment to obtain a comparison result signal;
the execution unit is used for selecting and executing one of the following actions according to the working state of the synchronous rectification circuit and a preset condition:
starting timing at the signal turning moment of the comparison result, and controlling the main switching tube to be switched on at the wave crest or the wave trough of the connection node of the main switching tube and the synchronous rectifier tube after first preset time is finished;
and starting timing at the signal turning moment of the comparison result, and controlling the synchronous rectifier tube to be switched on at the wave crest or the wave trough of the connection node of the main switch tube and the synchronous rectifier tube after the second preset time is finished.
13. The peak-to-valley power-on controller of claim 12, wherein: the triggering unit obtains the highest switching frequency limit finishing moment of the synchronous rectification circuit through the frequency limit timer.
14. The peak-to-valley power-on controller of claim 12, wherein: and the comparison unit compares the voltages at two ends of the energy storage inductor through a comparator to obtain the comparison result signal.
15. The peak-to-valley power-on controller of claim 12, wherein: the execution unit obtains the first predetermined time through a first timer, and the first timer is enabled by a rising edge of the comparison result signal or is enabled by a falling edge of the comparison result signal.
16. The peak-to-valley power-on controller of claim 12, wherein: the execution unit obtains the second predetermined time through a second timer, and the second timer is enabled by a rising edge of the comparison result signal or is enabled by a falling edge of the comparison result signal.
17. The peak-to-valley power-on controller of claims 12 to 15, wherein: when the working state of the synchronous rectification circuit is voltage reduction, the preset conditions are as follows:
when Vin-Vth < ═ 2 Vo, selecting the main switching tube to be switched on at the peak of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is ended;
when Vin-Vth >2 Vo, selecting the synchronous rectifier tube to be switched on at the wave trough of the connection node of the main switch tube and the synchronous rectifier tube after the second preset time is finished;
vin is the input voltage of the synchronous rectification circuit, Vo is the output voltage of the synchronous rectification circuit, and Vth is a set voltage greater than or equal to 0V.
18. The peak-to-valley power-on controller of any one of claims 12 to 15, wherein: when the working state of the synchronous rectification circuit is boosting, the preset conditions are as follows:
when 2 Vin-Vth ═ Vo, selecting the main switching tube to be switched on at the wave trough of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is ended;
when 2 Vin-Vth > Vo, selecting the synchronous rectifying tube to be switched on at the peak of the connection node of the main switching tube and the synchronous rectifying tube after the second preset time is ended;
vin is the input voltage of the synchronous rectification circuit, Vo is the output voltage of the synchronous rectification circuit, and Vth is a set voltage greater than or equal to 0V.
19. The utility model provides a crest and trough turn-on controller, is applied to diode rectifier circuit, diode rectifier circuit include main switch tube, rectifier diode and energy storage inductance, its characterized in that, crest and trough turn-on controller, include following unit:
the trigger unit is used for obtaining the highest switching frequency limit finishing time of the diode rectifying circuit;
the comparison unit is used for comparing the voltages at the two ends of the energy storage inductor at the end moment to obtain a comparison result signal;
and the execution unit starts timing at the signal turning moment of the comparison result, and controls the main switching tube to be switched on at the wave crest or the wave trough of the connection node of the main switching tube and the synchronous rectifier tube after first preset time according to the working state of the diode rectifier circuit and preset conditions.
20. The peak-to-valley power-on controller of claim 19, wherein: the triggering unit obtains the highest switching frequency limit finishing moment of the diode rectifying circuit through a frequency limit timer; the comparison unit compares the voltages at two ends of the energy storage inductor through a comparator to obtain a comparison result signal; the execution unit obtains the first predetermined time through a first timer, and the first timer is enabled by a rising edge of the comparison result signal or is enabled by a falling edge of the comparison result signal.
21. The peak-to-valley power-on controller of any one of claims 19 to 20, wherein: when the working state of the diode rectifying circuit is voltage reduction, the preset conditions are as follows:
when Vin-Vth < ═ 2 Vo, the main switching tube is switched on at the peak of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is ended;
vin is the input voltage of the diode rectifying circuit, Vo is the output voltage of the diode rectifying circuit, and Vth is a set voltage greater than or equal to 0V.
22. The peak-to-valley power-on controller of any one of claims 19 to 20, wherein: when the working state of the diode rectifying circuit is boosting, the preset conditions are as follows:
when 2 Vin-Vth ═ Vo, the main switching tube is switched on at the wave trough of the connection node of the main switching tube and the synchronous rectifying tube after the first preset time is finished;
vin is the input voltage of the diode rectifying circuit, Vo is the output voltage of the diode rectifying circuit, and Vth is a set voltage greater than or equal to 0V.
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