CN110504835B - Switch converter and control method thereof - Google Patents

Switch converter and control method thereof Download PDF

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Publication number
CN110504835B
CN110504835B CN201910790273.3A CN201910790273A CN110504835B CN 110504835 B CN110504835 B CN 110504835B CN 201910790273 A CN201910790273 A CN 201910790273A CN 110504835 B CN110504835 B CN 110504835B
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switching tube
turned
inductor
tube
switching
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CN110504835A (en
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卢鹏飞
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Mornsun Guangzhou Science and Technology Ltd
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Mornsun Guangzhou Science and Technology Ltd
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Priority to PCT/CN2020/094483 priority patent/WO2021036392A1/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Rectifiers (AREA)

Abstract

The invention discloses a switching converter and a control method thereof, wherein the switching converter comprises an input power supply positive electrode, an output voltage positive electrode, a power supply common ground, a switching tube Q1, a switching tube Q2, a switching tube Q3, a diode D1, an inductor L1 and a capacitor C1; the drain of the switching tube Q1 is connected to the positive input power supply, the source of the switching tube Q1 and the drain of the switching tube Q2 are connected to one end of an inductor L1, the source of the switching tube Q3 and the cathode of a diode D1 are connected to the other end of an inductor L1, the drain of the switching tube Q3 is connected to one end of a capacitor C1, and the source of the switching tube Q2, the anode of the diode D1 and the other end of the capacitor C1 are connected to the power supply common ground. The invention solves the problem that the voltage reduction circuit has low comprehensive efficiency when working in a wide input voltage and load range, and simultaneously eliminates oscillation and improves EMI.

Description

Switch converter and control method thereof
Technical Field
The present invention relates to switching power supplies, and more particularly, to a switching converter circuit and a control method thereof.
Background
Fig. 1 shows a conventional voltage reduction circuit, which has a large effective current value when the circuit operates in an intermittent mode, a MOS transistor Q1 is a hard switch, and the diode D1 has a large conduction loss.
Fig. 2 is a voltage-reducing circuit with a synchronous rectification function, which reduces the conduction loss at the freewheeling stage compared with the conventional voltage-reducing circuit, and can also realize ZVS switching of the MOS transistor Q1 in the FCCM mode, because the ZVS switching and high-efficiency working ranges of the MOS transistor Q1 are relatively narrow, the problem of relatively low comprehensive efficiency exists in the full-load range in the wide voltage input range.
Fig. 3 is an abstract drawing of taiwan patent with application number 100137357 entitled "control method and apparatus for improving light load efficiency of synchronous buck converter", which solves the problem of efficiency reduction under light load of fig. 2, because the driving of MOS transistor Q1 is complementary to the driving of MOS transistor Q2 in FCCM mode, and the negative current of inductor L is very large. Fig. 4 is a timing chart of the patent, and as shown in the figure, the MOS transistor Q2 is turned off when the current of the inductor L drops to zero under light load, so as to avoid energy loss caused by the negative current of the inductor L; and then, before the MOS tube Q1 is switched on, the MOS tube Q2 is controlled to be switched on for a short time, so that the current of the inductor L is a proper negative value, a condition is created for realizing ZVS switching-on of the MOS tube Q1, and the light load efficiency is improved. However, for a scene with a large ratio of input and output voltages and a large current output, current mainly flows through the MOS transistor Q2 instead of the MOS transistor Q1, so that the current capacity of the MOS transistor Q2 is large during circuit design, so that the input capacitance Ciss of the MOS transistor Q2 is large, the MOS transistor Q2 is switched twice in one period, the driving loss is large, and meanwhile, in order to realize short-time conduction of the MOS transistor Q2 during high-frequency application, the driving time of the MOS transistor Q2 is too short, so that the control IC is difficult to send out too short driving signals; and the high frequency resonance of the drain electrode of the MOS transistor Q2 exists at the time t3 to t4, and the EMI problem exists.
Disclosure of Invention
In view of the technical defects of the existing voltage reduction circuit, the improved patent circuit and the control mode thereof, the invention provides a switching converter and a control method thereof, and solves the problems that the voltage reduction circuit has low comprehensive efficiency in a wide voltage input range and a full load range, the driving loss of an MOS (metal oxide semiconductor) transistor Q2 is large, and the high-frequency resonance of the drain electrode of the MOS transistor Q2 at the time from t3 to t4 causes EMI and the narrow pulse driving at the time from t4 to t5 is difficult to send out in the patent of the control method and the control device for improving the light load efficiency of the synchronous voltage reduction converter.
In order to achieve the purpose, the invention adopts the following technical scheme:
a switching converter comprises an input power supply positive Vin, an output voltage positive Vo, a power supply common ground GND, a switching tube Q1, a switching tube Q2, a switching tube Q3, a one-way conducting device D1, an inductor L1 and a capacitor C1; the drain of the switch tube Q1 is connected to the input power positive Vin, the source of the switch tube Q1 and the drain of the switch tube Q2 are connected to one end of an inductor L1, the other end of the inductor L1 is connected to the source of the switch tube Q3 and the cathode of the unidirectional conducting device D1, the drain of the switch tube Q3 and one end of a capacitor C1 are connected to the output voltage positive Vo, and the anode of the unidirectional conducting device D1, the source of the switch tube Q2 and the other end of the capacitor C1 are connected to the power common ground GND.
Preferably, the switching tube Q1, the switching tube Q2 and the switching tube Q3 are MOS tubes, triodes or IGBTs.
Preferably, the unidirectional device D1 is a diode, an MOS transistor, a triode, or an IGBT, a cathode of the diode, a drain of the MOS transistor, a collector of the triode, or a drain of the IGBT is a cathode of the unidirectional device D1, and an anode of the diode, a drain of the MOS transistor, an emitter of the triode, or a source of the IGBT is an anode of the unidirectional device D1.
The control method of the switching converter comprises the following steps:
stage t 0-t 1: at time t0, switching tube Q1 is turned on, the voltage across inductor L1 is Vin-Vo, inductor L1 is excited, and current i of inductor L1LRising, and turning off a switching tube Q1 at the time t 1;
stage t 1-t 2: after the switch tube Q1 is turned off, the current i of the inductor L1LOutput capacitance Cos for the switching tube Q1s1, discharging an output capacitor Coss2 of the switch tube Q2, reducing the voltage of one end of an inductor L1 from Vin to 0V at the time of t2, and realizing ZVS switching-on of the switch tube Q2;
stage t 2-t 3: the voltage across inductor L1 is Vo, demagnetizing inductor L1, and the current iLDecreasing, current i of inductor L1 at time t3LReducing to zero, turning off a switching tube Q3, and turning off ZCS by a switching tube Q3;
stage t 3-t 4: at the time of t3, the output capacitor Coss3 of the switching tube Q3 and the inductor L1 form a resonant network to start resonance, when the voltage at the other end of the inductor L1 drops from Vo to 0V, the one-way conduction device D1 clamps the Coss3 voltage to end the resonance, and the current of the inductor L1 is very small, so that the current drops to zero quickly;
stage t 4-t 5: at the time of t4, switching tube Q3 is switched on, switching tube Q3 realizes ZCS switching on, Vo reversely excites inductor L1, and when reverse excitation current i isLWhen the ZVS switching-on condition of the switching tube Q1 is met, the switching tube Q2 is turned off at the time t 5;
stage T5-T0 + T: current i of inductor L1LCharging an output capacitor Coss2 of a switching tube Q2, discharging an output capacitor Coss1 of a switching tube Q1, increasing the voltage of one end of an inductor L1 to Vin from 0V at the time of T0+ T, and realizing ZVS switching-on by the switching tube Q1;
the cycle is ended and the next duty cycle is started and the above stages are repeated.
Current i of inductor L1 at time t3 as a control method of the switching converter described aboveLAnother specific embodiment of the present invention is characterized in that: current i of inductor L1 at time t3LAnd the voltage drops to 0 +/-1A, and the switching tube Q3 is turned off.
The invention also provides a second switching converter with the same inventive concept, and the technical scheme is as follows:
a switching converter comprises an input power supply positive Vin, an output voltage positive Vo, a power supply common ground GND, a switch tube Q1, a switch tube Q2, a switch tube Q3, an inductor L1 and a capacitor C1; the drain of the switching tube Q1 is connected to the input power positive Vin, the source of the switching tube Q1 and the drain of the switching tube Q2 are connected to one end of an inductor L1, the other end of the inductor L1 is connected to the source of the switching tube Q3, the drain of the switching tube Q3 and one end of a capacitor C1 are connected to the output voltage positive Vo, and the source of the switching tube Q2 and the other end of the capacitor C1 are connected to the power common ground GND.
Preferably, the switching tube Q1, the switching tube Q2 and the switching tube Q3 are MOS tubes, triodes or IGBTs.
The control method of the switching converter comprises the following steps:
stage t 0-t 1: at time t0, switching tube Q1 is turned on, the voltage across inductor L1 is Vin-Vo, inductor L1 is excited, and current i of inductor L1LRising, and turning off a switching tube Q1 at the time t 1;
stage t 1-t 2: after the switch tube Q1 is turned off, the current i of the inductor L1LCharging an output capacitor Coss1 of a switching tube Q1, discharging an output capacitor Coss2 of a switching tube Q2, reducing the voltage of one end of an inductor L1 from Vin to 0V at the time of t2, and realizing ZVS (zero voltage switching) switching-on by a switching tube Q2;
stage t 2-t 3: the voltage across inductor L1 is Vo, demagnetizing inductor L1, and the current iLDecreasing, current i of inductor L1 at time t3LReducing to zero, turning off a switching tube Q3, and turning off ZCS by a switching tube Q3;
stage t 3-t 4: at the time of t3, the output capacitor Coss3 of the switching tube Q3 and the inductor L1 form a resonant network to start resonance, so that the voltage at the other end of the inductor L1 oscillates from Vo to-Vo, and then the switching tube Q3 is switched on at the time of t4 according to the requirement of closed-loop control;
stage t 4-t 5: vo reversely excites inductor L1 when reverse exciting current iLWhen the ZVS switching-on condition of the switching tube Q1 is met, the switching tube Q2 is turned off at the time t 5;
stage T5-T0 + T: current i of inductor L1LCharging an output capacitor Coss2 of a switching tube Q2, discharging an output capacitor Coss1 of a switching tube Q1, increasing the voltage of one end of an inductor L1 to Vin from 0V at the time of T0+ T, and realizing ZVS switching-on by the switching tube Q1;
the cycle is ended and the next duty cycle is started and the above stages are repeated.
Current i of inductor L1 at time t3 as a control method of the switching converter described aboveLAnother specific embodiment of the present invention is characterized in that: current i of inductor L1 at time t3LAnd the voltage drops to 0 +/-1A, and the switching tube Q3 is turned off.
Description of the meaning of the terms:
a unidirectional conducting device refers to a device in which current can only flow from the anode to the cathode, but cannot flow from the cathode to the anode;
grid electrode of the switching tube: for the MOS tube, a grid electrode is referred, for the triode, a base electrode is referred, for the IGBT, the grid electrode is referred, and other switching tubes can correspond to each other according to the knowledge of a person skilled in the art and are not listed one by one;
drain electrode of the switching tube: for the MOS tube, a drain electrode is referred, for the triode, a collector electrode is referred, for the IGBT, a drain electrode is referred, and other switching tubes can correspond to each other according to the knowledge of a person skilled in the art and are not listed one by one;
source electrode of the switching tube: for the MOS transistor, the source electrode, the emitter electrode, and the source electrode, the other switching transistors may correspond to each other according to the knowledge of those skilled in the art, and are not listed.
Compared with the prior art, the invention has the following beneficial effects:
1) ZVS (zero voltage switch) switching-on of the switching tube Q1 and the switching tube Q2 and ZCS (zero voltage switch) switching of the switching tube Q3 are realized even under light load, and the negative current of the inductor L1 is small, so that the full-input voltage range and the full-load comprehensive efficiency are high;
2) the voltage withstanding of the switching tube Q3 is Vo and is much smaller than that of the switching tube Q2, so that the input capacitance Ciss of the switching tube Q3 under the same Rdson is much smaller than that of the switching tube Q2, and the driving loss of each time of the switching tube Q2 and the switching tube Q3 in one period is lower than the twice driving loss of the switching tube Q2 in FIG. 4;
3) resonance at stages t 3-t 4 in FIG. 4 is eliminated, and EMI is reduced; although the second switching converter scheme does not eliminate the resonance from the stage t3 to the stage t4, the total energy of the resonance comes from the output capacitor Coss3, while the total energy of the resonance in fig. 4 comes from the Coss2, actually, the Coss3 is smaller than the Coss2, so the second switching converter scheme of the invention has small resonance energy, fast attenuation and improved EMI;
4) the switching tube Q2 and the switching tube Q3 are conducted at the same time, namely, the intersection part is reversely excited by the inductor L1, and the problem that the control IC is difficult to send out a too short driving signal due to too short second driving time of the switching tube Q2 in fig. 4 is solved.
Drawings
FIG. 1 is a schematic diagram of a conventional voltage step-down circuit;
FIG. 2 is a schematic diagram of a voltage step-down circuit with synchronous rectification;
FIG. 3 is a schematic diagram of the buck patent circuit of application number 100137357;
FIG. 4 is a timing diagram illustrating the operation of the buck circuit of application No. 100137357;
FIG. 5 is a schematic circuit diagram of a first embodiment of the present invention;
FIG. 6 is a timing diagram illustrating operation of the first embodiment of the present invention;
FIG. 7 is a schematic circuit diagram of a second embodiment of the present invention;
FIG. 8 is a timing diagram illustrating operation of the second embodiment of the present invention.
Detailed Description
First embodiment
Fig. 5 is a schematic circuit diagram of a first embodiment of the present invention. The power supply comprises an input power supply positive Vin, an output voltage positive Vo, a power supply common ground GND, a MOS tube Q1, a MOS tube Q2, a MOS tube Q3, a diode D1, an inductor L1 and a capacitor C1; the drain of the MOS transistor Q1 is connected to the input power positive Vin, the source of the MOS transistor Q1 and the drain of the MOS transistor Q2 are connected to one end of an inductor L1, the source of the MOS transistor Q3 and the cathode of a diode D1 are connected to the other end of an inductor L1, the drain of the MOS transistor Q3 is connected to one end of a capacitor C1, and the source of the MOS transistor Q2, the anode of the diode D1 and the other end of the capacitor C1 are connected to the power common ground GND.
Coss1, Coss2 and Coss3 in fig. 5 are output capacitances of MOS transistor Q1, MOS transistor Q2 and MOS transistor Q3, respectively, and body diodes of MOS transistor Q1, MOS transistor Q2 and MOS transistor Q3 are also shown in fig. 5.
The diode D1 is used to clamp the voltage of Coss3 only, and the current flowing through it is extremely small, so the diode D1 is a very small device, and the diode D1 can be even eliminated according to practical application.
It should be noted that:
in this embodiment, the one-way conducting device is the diode D1, but it may also be an MOS transistor, a triode, or an IGBT, where a drain of the MOS transistor, a collector of the triode, or a drain of the IGBT is a cathode of the diode D1, and a drain of the MOS transistor, an emitter of the triode, or a source of the IGBT is an anode of the diode D1.
It is common practice for those skilled in the art to replace MOS transistor Q1, MOS transistor Q2, and MOS transistor Q3 with other types of switching transistors such as transistors or IGBTs.
Fig. 6 shows the operation sequence of the present embodiment, which is specifically as follows:
stage t 0-t 1: at time t0, MOS transistor Q1 is turned on, the voltage across inductor L1 is Vin-Vo, inductor L1 is excited, and current i of inductor L1LRising, and turning off the MOS tube Q1 at the time t 1;
stage t 1-t 2: after the MOS transistor Q1 is turned off, the current i of the inductor L1LCharging an output capacitor Coss1 of an MOS tube Q1, discharging an output capacitor Coss2 of an MOS tube Q2, reducing the voltage of SW1 at one end of an inductor L1 from Vin to 0V at the time of t2, and realizing ZVS (zero voltage switching) switching-on of the MOS tube Q2;
stage t 2-t 3: the voltage across inductor L1 is Vo, demagnetizing inductor L1, and the current i of inductor L1LDecreasing, current i of inductor L1 at time t3LReducing to zero, and realizing ZCS turn-off by the MOS tube Q3;
stage t 3-t 4: at time t3, output capacitor Coss3 of MOS transistor Q3 and inductor L1 form a resonant network to start resonance, when the voltage of SW2 at the other end of inductor L1 drops from Vo to 0V, diode D1 clamps Coss3 voltage to end resonance, and the current i of inductor L1 is small because the current of inductor L1 is smallLThe voltage quickly drops to zero, and at the time of t4, the MOS tube Q3 realizes ZCS opening;
stage t 4-t 5: vo reversely excites inductor L1 when reverse exciting current iLThe MOS tube Q2 is turned off at the time t5 when the ZVS turn-on condition of the MOS tube Q1 is met;
stage T5-T0 + T: current i of inductor L1LOutput capacitor Cos for MOS transistor Q2s2 is charged to discharge an output capacitor Coss1 of the MOS tube Q1, the voltage of the SW1 at one end of the inductor L1 rises to Vin from 0V at the time of T0+ T, and the ZVS is turned on by the MOS tube Q1;
the cycle is ended and the next duty cycle is started and the above stages are repeated.
Since the circuit operates periodically, T in T0+ T means the time length of one cycle.
Since the diode D1 flows a small current and has a reverse breakdown voltage Vo and a low Vo voltage, the diode D1 is a small diode with a small current and a small breakdown voltage.
The reverse withstand voltage of the MOS transistor Q3 is Vo, the reverse withstand voltage of the MOS transistor Q2 is Vin, and the withstand voltage of the MOS transistor Q3 is much smaller than that of the MOS transistor Q2 in terms of device selection, so that the input capacitance Ciss and the output capacitance Coss3 of the MOS transistor Q3 are much smaller under the same Rdson condition according to a formula
Figure BDA0002179344750000061
The corresponding drive losses are much smaller.
In particular, inductor L1 has a current i at time t3LTaking any value within 0 +/-1A, the MOS transistor Q3 is turned off, and the current iLThe smaller the error value of (3), the higher the turn-off efficiency of the MOS transistor Q3.
Second embodiment
Fig. 7 is a schematic circuit diagram of a second embodiment of the present invention, in which the diode D1 is removed and the other connection relationship is unchanged based on the first embodiment.
Fig. 8 shows the operation sequence of the second embodiment, which is as follows:
stage t 0-t 1: at time t0, MOS transistor Q1 is turned on, the voltage across inductor L1 is Vin-Vo, inductor L1 is excited, and current i of inductor L1LRising, and turning off the MOS tube Q1 at the time t 1;
stage t 1-t 2: after the MOS transistor Q1 is turned off, the current i of the inductor L1LCharging an output capacitor Coss1 of an MOS tube Q1, discharging an output capacitor Coss2 of an MOS tube Q2, reducing the voltage of SW1 at one end of an inductor L1 from Vin to 0V at the time of t2, and realizing ZVS (zero voltage switching) switching-on of the MOS tube Q2;
t2～stage t 3: the voltage across inductor L1 is Vo, demagnetizing inductor L1, and the current iLDecreasing, current i of inductor L1 at time t3LReducing to zero, and realizing ZCS turn-off by the MOS tube Q3;
stage t 3-t 4: at the time of t3, an output capacitor Coss3 of the MOS transistor Q3 and an inductor L1 form a resonant network to start resonance, so that the voltage of SW2 at the other end of the inductor L1 oscillates from Vo to-Vo, and then the MOS transistor Q3 is switched on at the time of t4 according to the requirement of closed-loop control;
stage t 4-t 5: vo reversely excites inductor L1 when reverse exciting current iLThe MOS tube Q2 is turned off at the time t5 when the ZVS turn-on condition of the MOS tube Q1 is met;
stage T5-T0 + T: current i of inductor L1LCharging an output capacitor Coss2 of a MOS transistor Q2, discharging an output capacitor Coss1 of a MOS transistor Q1, increasing the voltage of a SW1 at one end of an inductor L1 from 0V to Vin at the time of T0+ T, and realizing ZVS switching-on by the MOS transistor Q1;
the cycle is ended and the next duty cycle is started and the above stages are repeated.
The cost can be reduced by removing the diode D1, but the resonance exists between the stages t3 and t4, the influence of the resonance on the EMI can be determined according to practical application, and if the influence is within an acceptable range, the cost can be reduced by removing the diode D1.
In particular, inductor L1 has a current i at time t3LTaking any value within 0 +/-1A, the MOS transistor Q3 is turned off, and the current iLThe smaller the error value of (b), the higher the turn-off efficiency of the MOS transistor Q3, and when the current i is smallerLThe SW2 node oscillation at the stage t 3-t 4 is larger when the time is less than zero.
The above embodiments should not be construed as limiting the present invention, and the scope of the present invention should be determined by the scope of the appended claims. It will be apparent to those skilled in the art that many equivalent substitutions, modifications and alterations can be made without departing from the spirit and scope of the invention, such as fine tuning of the circuit by simple series-parallel connection of devices, etc., depending on the application, and such modifications and alterations should also be considered as the scope of the invention.

Claims (7)

1. A switching converter, characterized by: the power supply circuit comprises an input power supply positive Vin, an output voltage positive Vo, a power supply common ground GND, a switching tube Q1, a switching tube Q2, a switching tube Q3, a one-way conduction device D1, an inductor L1 and a capacitor C1; the drain of the switching tube Q1 is connected to the input power positive Vin, the source of the switching tube Q1 and the drain of the switching tube Q2 are connected to one end of an inductor L1, the other end of the inductor L1 is connected to the source of the switching tube Q3 and the cathode of a unidirectional conducting device D1, the drain of the switching tube Q3 and one end of a capacitor C1 are connected to the output voltage positive Vo, and the anode of the unidirectional conducting device D1, the source of the switching tube Q2 and the other end of the capacitor C1 are connected to the power common ground GND;
the working sequence of one cycle is as follows:
stage t 0-t 1: the switch tube Q1 is switched on, the switch tube Q2 is switched off, the switch tube Q3 is switched on, and the inductor L1 is excited;
stage t 1-t 2: the switching tube Q1 is turned off, the switching tube Q2 is turned off, the switching tube Q3 is turned on, the inductor L1 charges the output capacitor Coss1 of the switching tube Q1 and discharges the output capacitor Coss2 of the switching tube Q2;
stage t 2-t 3: the switching tube Q1 is turned off, the switching tube Q2 is turned on, the switching tube Q3 is turned on, and the inductor L1 is demagnetized;
stage t 3-t 4: the switching tube Q1 is turned off, the switching tube Q2 is turned on, the switching tube Q3 is turned off, and the output capacitor Coss3 of the switching tube Q3 and the inductor L1 form a resonant network to start resonance;
stage t 4-t 5: the switching tube Q1 is turned off, the switching tube Q2 is turned on, the switching tube Q3 is turned on, and the inductor L1 is excited reversely;
stage T5-T0 + T: the switching tube Q1 is turned off, the switching tube Q2 is turned off, the switching tube Q3 is turned on, the inductor L1 charges the output capacitor Coss2 of the switching tube Q2, and discharges the output capacitor Coss1 of the switching tube Q1.
2. The switching converter according to claim 1, wherein: the switching tube Q1, the switching tube Q2 and the switching tube Q3 are MOS tubes, triodes or IGBTs.
3. The switching converter according to claim 1, wherein: the unidirectional device D1 is a diode, an MOS tube, a triode or an IGBT, the cathode of the diode, the drain of the MOS tube, the collector of the triode or the drain of the IGBT is the cathode of the unidirectional device D1, and the anode of the diode, the drain of the MOS tube, the emitter of the triode or the source of the IGBT is the anode of the unidirectional device D1.
4. The switching converter according to claim 1, wherein: the current i of the inductor L1 at the time t3LAnd the voltage drops to 0 +/-1A, and the switching tube Q3 is turned off.
5. A switching converter, characterized by: the power supply comprises an input power supply positive Vin, an output voltage positive Vo, a power supply common ground GND, a switching tube Q1, a switching tube Q2, a switching tube Q3, an inductor L1 and a capacitor C1; the drain of the switching tube Q1 is connected to the input power positive Vin, the source of the switching tube Q1 and the drain of the switching tube Q2 are connected to one end of an inductor L1, the other end of the inductor L1 is connected to the source of the switching tube Q3, the drain of the switching tube Q3 and one end of a capacitor C1 are connected to the output voltage positive Vo, and the source of the switching tube Q2 and the other end of the capacitor C1 are connected to the power common ground GND;
the working sequence of one cycle is as follows:
stage t 0-t 1: the switch tube Q1 is switched on, the switch tube Q2 is switched off, the switch tube Q3 is switched on, and the inductor L1 is excited;
stage t 1-t 2: the switching tube Q1 is turned off, the switching tube Q2 is turned off, the switching tube Q3 is turned on, the inductor L1 charges the output capacitor Coss1 of the switching tube Q1 and discharges the output capacitor Coss2 of the switching tube Q2;
stage t 2-t 3: the switching tube Q1 is turned off, the switching tube Q2 is turned on, the switching tube Q3 is turned on, and the inductor L1 is demagnetized;
stage t 3-t 4: the switching tube Q1 is turned off, the switching tube Q2 is turned on, the switching tube Q3 is turned off, and the output capacitor Coss3 of the switching tube Q3 and the inductor L1 form a resonant network to start resonance;
stage t 4-t 5: the switching tube Q1 is turned off, the switching tube Q2 is turned on, the switching tube Q3 is turned on, and the inductor L1 is excited reversely;
stage T5-T0 + T: the switching tube Q1 is turned off, the switching tube Q2 is turned off, the switching tube Q3 is turned on, the inductor L1 charges the output capacitor Coss2 of the switching tube Q2, and discharges the output capacitor Coss1 of the switching tube Q1.
6. The switching converter according to claim 5, wherein: the switching tube Q1, the switching tube Q2 and the switching tube Q3 are MOS tubes, triodes or IGBTs.
7. The switching converter according to claim 5, wherein: the current i of the inductor L1 at the time t3LAnd the voltage drops to 0 +/-1A, and the switching tube Q3 is turned off.
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CN110504835B (en) * 2019-08-26 2021-09-14 广州金升阳科技有限公司 Switch converter and control method thereof
CN111404236B (en) * 2020-04-24 2022-05-13 深圳硕日新能源科技有限公司 Charging circuit of photovoltaic charging controller and photovoltaic charging controller
CN112087138B (en) * 2020-09-28 2022-05-20 广州金升阳科技有限公司 Multi-mode soft switching converter and control method thereof

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