CN113395005B - Inverter circuit, driving method thereof, multiphase inverter circuit and inverter - Google Patents

Inverter circuit, driving method thereof, multiphase inverter circuit and inverter Download PDF

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Publication number
CN113395005B
CN113395005B CN202110938748.6A CN202110938748A CN113395005B CN 113395005 B CN113395005 B CN 113395005B CN 202110938748 A CN202110938748 A CN 202110938748A CN 113395005 B CN113395005 B CN 113395005B
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China
Prior art keywords
switch
unit
inverter circuit
time sequence
inverter
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CN202110938748.6A
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CN113395005A (en
Inventor
雷健华
唐朝垠
马辉
秦赓
尹相柱
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Shenzhen Delian Minghai New Energy Co ltd
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Shenzhen Poweroak Newener Co Ltd
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Priority to PCT/CN2022/085381 priority patent/WO2023019969A1/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/083—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the ignition at the zero crossing of the voltage or the current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

The inverter circuit comprises a first switch, a follow current unit, a resonance unit, a bridge arm unit and a control unit, wherein the first switch is respectively connected with a direct current power supply and the midpoint of the follow current unit, the resonance unit is respectively connected with the midpoint of the follow current unit and the midpoint of the bridge arm unit, the midpoint of the bridge arm unit is also used for being connected with a load, the follow current unit is connected with the bridge arm unit in parallel and is connected with the direct current power supply, the control unit is respectively connected with the first switch and the control end of the bridge arm unit, and the control unit is used for controlling the switching state of the first switch and controlling the switching state of an inverter switch in the bridge arm unit so as to convert the direct current of the direct current power supply into alternating current and output the alternating current at the midpoint of the bridge arm unit. By the mode, the inverter function can be realized through a simple circuit, and the cost is low.

Description

Inverter circuit, driving method thereof, multiphase inverter circuit and inverter
Technical Field
The present disclosure relates to the field of power electronics technologies, and in particular, to an inverter circuit and a driving method thereof, and a multiphase inverter circuit and an inverter.
Background
The development of industrialization places increasingly higher demands on the size, cost, operating frequency and efficiency of power electronic devices. The pursuit of high frequency, high efficiency, low cost, and miniaturization of power electronic devices has become a development concept. Hard-switched inverters, when operated at high frequencies, not only produce severe switching losses, but are also associated with severe noise pollution and electromagnetic interference. For this reason, soft switching technology was born and applied to hard switching inverters. The soft switching inverter is characterized in that an auxiliary resonant circuit is added in the hard switching inverter, and the resonance effect of an inductor and a capacitor in the auxiliary circuit is utilized to realize zero-voltage switching or zero-current switching, reduce switching loss and reduce noise pollution and electromagnetic interference.
Meanwhile, compared with a resonant direct-current link soft switching inverter, the resonant pole type soft switching inverter has more outstanding excellent performance, the inverter generally adopts three groups of auxiliary resonant circuits which are respectively connected to each phase of the three-phase inverter, the three groups of auxiliary circuits of the inverter can realize independent control, soft switching conditions are created for main switches on bridge arms of each phase of the three-phase inverter, the problem of conflict of the auxiliary switches and the main switches of the inverter on synchronous operation is solved, and the conventional Pulse Width Modulation (PWM) strategy can be conveniently adopted for output voltage control.
However, in the conventional resonant pole soft switching inverter, a large number of auxiliary switches and a transformer are required in the inverter, which not only complicates the circuit but also increases the cost of the inverter.
Disclosure of Invention
The embodiment of the application aims to provide an inverter circuit, a driving method, a multi-phase inverter circuit and an inverter, which can realize an inverter function through a simpler circuit and have lower cost.
To achieve the above object, in a first aspect, the present application provides an inverter circuit comprising:
the device comprises a first switch, a follow current unit, a resonance unit, a bridge arm unit and a control unit;
the first switch is respectively connected with the midpoint of the follow current unit and the DC power supply, the resonance unit is respectively connected with the midpoint of the follow current unit and the midpoint of the bridge arm unit, the midpoint of the bridge arm unit is also used for being connected with a load, the follow current unit is connected with the bridge arm unit in parallel, and the follow current unit and the bridge arm unit are both connected with the DC power supply;
the control unit is respectively connected with the first switch and the control end of the bridge arm unit, and is used for controlling the switching state of the first switch and controlling the switching state of an inverter switch in the bridge arm unit so as to convert the direct current of the direct current power supply into alternating current, and the alternating current is output at the midpoint of the bridge arm unit.
In one embodiment, the resonant unit includes a resonant inductor and a resonant capacitor;
the resonance inductor is connected with the resonance capacitor in series, the non-series end of the resonance inductor is connected with the midpoint of the follow current unit, and the non-series end of the resonance capacitor is connected with the midpoint of the bridge arm unit.
In one embodiment, the bridge arm unit includes a second switch and a third switch;
the first end of the second switch and the first end of the third switch are both connected with the control unit, the second end of the second switch and the third end of the third switch are both connected with the non-series end of the resonant capacitor, the third end of the second switch is connected with the anode of the direct-current power supply, and the second end of the third switch is connected with the cathode of the direct-current power supply.
In one embodiment, the freewheel unit includes a first diode and a second diode;
the cathode of the first diode is connected with the anode of the direct current power supply, the anode of the first diode is connected with the cathode of the second diode, and the anode of the second diode is connected with the cathode of the direct current power supply;
and the connection point between the first diode and the second diode is the midpoint of the free-wheeling unit.
In a second aspect, the present application provides a driving method of an inverter circuit, for driving the inverter circuit described in any of the above embodiments, the driving method including:
in a first time sequence, the first switch is controlled to be closed, and the first inversion switch and the second inversion switch of the bridge arm unit are controlled to be opened, so that IL1= I0, perform second timing; wherein, IL1Is the resonance current in the resonance unit, I0 is the load current;
in the second time sequence, keeping the first switch closed and the first inversion switch open, and controlling the second inversion switch to be closed to enable IL1=0，UC1= U2, perform the second stepThree time sequences; wherein, UC1Is the resonance voltage in the resonance unit, U2 is the maximum value of the forward voltage of the resonance unit;
in the third time sequence, keeping the first inversion switch open and the second inversion switch closed, and controlling the first switch to be open so as to enable IL1=0, and UC1= U3, execute fourth timing; wherein-E<U3<0 and E are voltage values of the direct current power supply;
in the fourth time sequence, keeping the first inversion switch open and the second inversion switch closed, and controlling the first switch to be closed so as to enable IL1= I0, perform fifth timing;
in the fifth time sequence, keeping the first switch closed and the first inversion switch open, and controlling the second inversion switch to open so as to enable IL1=0, and UC1= U2, execute sixth timing;
in the sixth time sequence, the first inversion switch is kept disconnected and the second inversion switch is kept disconnected, and the first switch is controlled to be disconnected so as to enable IL1=0, and UC1= U0, and causes the inverter circuit to recover to an initial state; u0 is the initial voltage value of the resonance unit when the inverter circuit is in the initial state.
In one embodiment, the driving method further includes an initial timing sequence;
and in the initial time sequence, controlling the first switch, the first inverter switch and the second inverter switch to be disconnected so as to enable the inverter circuit to be in the initial state, and executing the first time sequence.
In one embodiment, the driving method further comprises maintaining a timing sequence;
in the third sequence, when the IL1=0, and UC1= U3, performing the sustain timing in which the first switch and the first inversion switch are kept open and the second inversion switch is kept closed to keep the resonance current 0 and the resonance voltage U3, and then performing the sustain timingAnd the fourth timing sequence is performed.
In a third aspect, the present application provides a multi-phase inverter circuit, comprising at least two inverter circuits as described in any of the above embodiments;
one end of the first switch in each inverter circuit is used for being connected with the negative electrode of the direct current power supply, and two ends of the follow current unit in each inverter circuit are respectively connected with two ends of the direct current power supply.
In an embodiment, any one of the inverter circuits is driven by the driving method described in any one of the above embodiments.
In a third aspect, the present application provides an inverter comprising the inverter circuit described in any of the above embodiments;
or, the inverter circuit and the driving method described in any of the above embodiments are included;
or, the multi-phase inverter circuit described in any of the above embodiments is included.
The beneficial effects of the embodiment of the application are that: the inverter circuit provided by the application comprises a first switch, a follow current unit, a resonance unit, a bridge arm unit and a control unit, wherein the first switch is respectively connected with the midpoint of the follow current unit and a direct current power supply, the resonance unit is respectively connected with the middle of the follow current unit and the midpoint of the bridge arm unit, the midpoint of the bridge arm unit is also used for being connected with a load, the follow current unit is connected with the bridge arm unit in parallel and is connected with the direct current power supply, and the control unit is respectively connected with the first switch and the bridge arm unit The auxiliary switch only needs to comprise the first switch, a transformer does not need to be arranged like the prior art, the circuit structure is simple, and the cost is reduced.
Drawings
One or more embodiments are illustrated by way of example in the accompanying drawings, which correspond to the figures in which like reference numerals refer to similar elements and which are not to scale unless otherwise specified.
Fig. 1 is a schematic structural diagram of an inverter circuit provided in an embodiment of the present application;
fig. 2 is a schematic circuit diagram of an inverter circuit according to an embodiment of the present disclosure;
fig. 3 is a flowchart of a driving method provided in an embodiment of the present application;
fig. 4a is a schematic diagram of a first control state of the inverter circuit in one cycle according to the embodiment of the present application;
fig. 4b is a schematic diagram illustrating a second control state of the inverter circuit in one cycle according to the embodiment of the present application;
fig. 4c is a schematic diagram illustrating a third control state of the inverter circuit in one cycle according to the embodiment of the present application;
fig. 4d is a schematic diagram illustrating a fourth control state of the inverter circuit in one cycle according to the embodiment of the present application;
fig. 4e is a schematic diagram of a fifth control state of the inverter circuit in one cycle according to the embodiment of the present application;
fig. 4f is a schematic diagram illustrating a sixth control state of the inverter circuit in one cycle according to the embodiment of the present application;
fig. 4g is a schematic diagram of a seventh control state of the inverter circuit in one cycle according to the embodiment of the present application;
fig. 4h is a schematic diagram of an eighth control state of the inverter circuit in one cycle according to the embodiment of the present application;
fig. 4i is a schematic diagram of a ninth control state of the inverter circuit in one cycle according to the embodiment of the present application;
fig. 4j is a schematic diagram of a tenth control state of the inverter circuit in one cycle according to the embodiment of the present application;
fig. 4k is a schematic diagram of an eleventh control state of the inverter circuit in one cycle according to the embodiment of the present application;
fig. 5 is a waveform diagram of signals in an inverter circuit according to an embodiment of the present disclosure;
fig. 6 is a schematic structural diagram of a driving device according to an embodiment of the present application;
fig. 7 is a schematic circuit structure diagram of a multi-phase inverter circuit according to an embodiment of the present application.
Detailed Description
In order to make the objects, technical solutions and advantages of the embodiments of the present application clearer, the technical solutions in the embodiments of the present application will be clearly and completely described below with reference to the drawings in the embodiments of the present application, and it is obvious that the described embodiments are some embodiments of the present application, but not all embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present application.
Referring to fig. 1, fig. 1 is a schematic structural diagram of an inverter circuit according to an embodiment of the present disclosure. As shown in fig. 1, the inverter circuit 100 includes a first switch 10, a freewheel unit 20, a resonance unit 30, a bridge arm unit 40, and a control unit 50. The first end of the first switch 10 is connected to the second end of the dc power supply 200, the second end of the first switch 10 is connected to a midpoint P1 of the freewheel unit 20, the first end of the resonance unit 30 is connected to a midpoint P1 of the freewheel unit 20, the second end of the resonance unit 30 is connected to a midpoint P2 of the bridge arm unit 40, the midpoint P2 of the bridge arm unit 40 is further connected to the load 300, the freewheel unit 20 is connected to the bridge arm unit 40 in parallel, that is, the first end of the freewheel unit 20 is connected to the first end of the bridge arm unit 40, the second end of the freewheel unit 20 is connected to the second end of the bridge arm unit 40, the first end and the second end of the freewheel unit 20 are further connected to two ends of the dc power supply 200, and the control unit 50 is connected to the first switch 10 and the bridge arm unit 40, respectively.
Specifically, the first switch 10 and the inverter switches in the bridge arm unit 40 are both controlled by the control unit 50, and then the control unit 50 can convert the dc power provided by the dc power supply 200 into ac power by controlling the switching state of the first switch 10 and controlling the switching state of each inverter switch in the bridge arm unit 40, and output the ac power to the load 300 at the midpoint P2 of the bridge arm unit 40 to be used as the power supply voltage of the load 300. The switching state of each switch refers to a state in which each switch is closed or opened.
In the process, the direct current is converted into the alternating current, namely, the inversion function is realized. Meanwhile, in the inverter circuit 100, only the first switch 10 serves as an auxiliary switch, so that the number of the auxiliary switches is small, and a transformer is not required to be provided as in the prior art, so that the circuit structure is also simplified, and the cost is reduced.
For better understanding of the present application, a circuit configuration of the inverter circuit shown in fig. 2 will be described as an example.
As shown in fig. 2, the first switch 10 is a first switch Q1 (in the figure, an IGBT switching tube Q1). The gate (i.e., G pole) of the IGBT Q1 is connected to the control unit 50, the emitter (i.e., E pole) of the IGBT Q1 is connected to the negative pole of the dc power supply 200, and the collector (i.e., C pole) of the IGBT Q1 is connected to the midpoint P1 of the freewheel unit 20.
Optionally, the freewheel unit 20 includes a first diode D1 and a second diode D2. An anode of the first diode D1 is connected to a cathode of the second diode D2, a cathode of the first diode D1 is connected to an anode of the dc power supply 200, an anode of the second diode D2 is connected to a cathode of the dc power supply 200, and a connection point between the first diode D1 and the second diode D2 is a midpoint P1 of the freewheel unit 20. In one embodiment, the first diode D1 and the second diode D2 are both freewheeling diodes.
Optionally, the resonant unit 30 includes a resonant inductor L1 and a resonant capacitor C1. The resonant inductor L1 is connected in series with the resonant capacitor C1, the non-series connection end of the resonant inductor L1 is connected with the midpoint P1 of the freewheeling unit 20, and the non-series connection end of the resonant capacitor C1 is connected with the midpoint P2 of the bridge arm unit 40. Specifically, by adopting the resonant unit 30 composed of the resonant inductor L1 and the resonant capacitor C1, since the resistances of the resonant inductor L1 and the resonant capacitor C1 are small, the power consumption of the resonant inductor L1 and the resonant capacitor can be approximately zero when the inverter circuit operates, and thus the power loss of the inverter circuit is reduced.
In one embodiment, the bridge arm unit 40 includes a second switch and a third switch. The first end of the second switch and the first end of the third switch are both connected with the control unit, the second end of the second switch and the third end of the third switch are both connected with the non-series end of the resonant capacitor, the third end of the second switch is connected with the positive pole of the direct-current power supply, and the second end of the third switch is connected with the negative pole of the direct-current power supply.
In an embodiment, the second switch and the third switch are both IGBT transistors, the second switch corresponds to the IGBT transistor Q2 in fig. 2, and the third switch corresponds to the IGBT transistor Q3 in fig. 2.
The gates of the IGBT switching tube Q2 and the IGBT switching tube Q3 are both connected to the control unit 50, the emitter of the IGBT switching tube Q2 is connected to the collector of the IGBT switching tube Q3, the collector of the IGBT switching tube Q2 is connected to the positive electrode of the dc power supply 200, and the emitter of the IGBT switching tube Q3 is connected to the negative electrode of the dc power supply 200. The connection point between the IGBT switching tube Q2 and the IGBT switching tube Q3 is the midpoint P2 of the bridge arm unit 40.
In the inverter circuit 100, the first switch, the second switch, and the third switch are all exemplified by IGBT switching tubes. In other embodiments, the first switch, the second switch, and the third switch may be any power electronic component, such as a field effect transistor MOSFET, a thyristor SCR, a gate turn-off thyristor GTO, a power transistor GTR, or any commonly used switch, such as a contactor, a relay, a delay switch, a photoelectric switch, a tact switch, a proximity switch, or any combination thereof. Meanwhile, the first switch, the second switch and the third switch may be the same or different.
Taking the first switch as an example, if the first switch is an IGBT switch, the gate of the IGBT switch is the first terminal of the first switch, the emitter of the IGBT switch is the second terminal of the first switch, and the collector of the IGBT switch is the third terminal of the first switch.
In the inverter circuit, direct current can be converted into alternating current only by adopting the first switch, the resonant capacitor, the resonant inductor and the two auxiliary diodes, the structure is simple, the control strategy is simplified, the inverter volume is reduced, and the inverter cost is reduced.
In an embodiment, the present application provides a driving method of an inverter circuit, where the driving method of the inverter circuit in any of the above embodiments includes:
in a first time sequence, the first switch is controlled to be closed, and the first inversion switch and the second inversion switch of the bridge arm unit are controlled to be opened, so that IL1= I0, perform second timing; wherein, IL1Is the resonant current in the resonant cell, I0 is the load current;
in a second time sequence, keeping the first switch closed and the first inversion switch open, and controlling the second inversion switch to be closed so as to enable IL1=0，UC1= U2, perform third timing; wherein, UC1Is the resonance voltage in the resonance unit, U2 is the maximum value of the forward voltage of the resonance unit;
in a third time sequence, keeping the first inversion switch open and the second inversion switch closed, and controlling the first switch to be open so as to enable IL1=0, and UC1=U3（-E<U3<0) Executing the fourth timing; wherein E is the voltage value of the direct current power supply;
in a fourth time sequence, keeping the first inversion switch open and the second inversion switch closed, and controlling the first switch to be closed so as to enable IL1= I0, perform fifth timing;
in a fifth time sequence, keeping the first switch closed and the first inversion switch open, and controlling the second inversion switch to open so as to enable IL1=0, and UC1= U2, execute sixth timing;
in a sixth time sequence, keeping the first inversion switch off and the second inversion switch off, and controlling the first switch to be switched off so as to enable IL1=0, and UC1= U0, and causes the inverter circuit to return to the original stateState; wherein, U0 is the initial voltage value of the resonance unit when the inverter circuit is in the initial state.
In an embodiment, the driving method of the inverter circuit further includes an initial timing sequence;
in the initial time sequence, the first switch, the first inversion switch and the second inversion switch are controlled to be disconnected, so that the inversion circuit is in an initial state, and the first time sequence is executed.
In one embodiment, the driving method of the inverter circuit further includes maintaining a timing sequence;
in the third time sequence, when IL1=0, and UC1=U3（-E<U3<0) And performing a sustain sequence in which the first switch is kept disconnected from the first inverter switch and the second inverter switch is kept closed to maintain the resonant current at 0 and the resonant voltage at U3, and then performing a fourth sequence.
Referring to fig. 3, fig. 3 is a schematic flow chart of a driving method of an inverter circuit according to an embodiment of the present application, where the method is used to drive the inverter circuit 100 shown in fig. 1 or fig. 2. The method comprises the following steps:
step 301: and in a first time sequence, controlling the first switch to be closed, and controlling the first inverter switch and the second inverter switch of the bridge arm unit to be disconnected.
In one embodiment, the inverter circuit 100 starts to operate from an initial state. Please refer to fig. 4a and fig. 5 together, wherein fig. 4a is a schematic diagram of a first control state in a period according to an embodiment of the present disclosure, and fig. 5 is a waveform diagram of each control signal in a control process according to an embodiment of the present disclosure. In FIG. 5, LQ2A switching signal representing an IGBT switching tube Q2; l isQ1A switching signal representing an IGBT switching tube Q1; u shapeC1Represents the voltage across the resonant capacitor C1, i.e. the resonant voltage in the resonant cell 30; i isL1Representing the current flowing through the resonant inductor L1, i.e. the resonant current in the resonant cell 30.
Meanwhile, in this embodiment, the first switch corresponds to IGBT switching tube Q1 in fig. 2, the first inverter switch of the arm unit corresponds to IGBT switching tube Q2 in fig. 2, and the second inverter switch of the arm unit corresponds to IGBT switching tube Q3 in fig. 2, for example, the description will be given.
As can be seen from fig. 5, at the initial timing, corresponding to a period of time from 0 to t1, the control unit 50 controls both the IGBT Q1 and the IGBT Q2 to be turned off, so that the inverter circuit 100 is in the initial state. At this time, as shown in fig. 4a, a load current I0 (not shown) passes through the body diode D of the IGBT switching tube Q2Q2Follow current, then IL1=0, and UC1=U0（0<U0<E) Where E is the voltage value of the dc power supply 200, and U0 is the initial voltage value at both ends of the resonant capacitor when the inverter circuit is in the initial state. Then, a first timing sequence may be performed.
In the first timing (time period t1 to t 2), as shown in fig. 4b, the control unit 50 controls the IGBT switching tube Q1 to be closed and keeps the IGBT switching tube Q2 disconnected from the IGBT switching tube Q3. During the time period t1 to t 2: since the resonant inductor L1 reduces the rate of rise of the current flowing through itself, the resonant inductor L1 enables zero current soft-on of the IGBT switching tube Q1. After the IGBT switching tube Q1 is closed, the resonance inductor L1 and the resonance capacitor C1 start to resonate, the resonance inductor L1 and the resonance capacitor C1 are charged simultaneously, and IL1Heel UC1All increase gradually and flow through the body diode DQ2Gradually decreases. Until time t2, IL1To I0 (i.e. I)L1= I0), and UC1And increased to U1, the second timing sequence is started.
Step 302: and in a second time sequence, keeping the first switch closed and the first inversion switch open, and controlling the second inversion switch to be closed.
In the second timing (time period t2 to t 3), as can be seen from fig. 4c, the control unit 50 controls the IGBT switching tube Q3 to be closed, and keeps the IGBT switching tube Q1 closed and the IGBT switching tube Q2 open. Since the load current I0 flows through the resonant inductor L1 at the beginning of the second timing sequence, the current of the IGBT switch Q3 is zero, and the IGBT switch Q3 realizes zero current and zero voltage turn-on. During the time period t2 to t 3: the resonant inductor L1 charges the resonant capacitor C1, UC1Continued increase of IL1Initially reduced, flowing through the IGBT switchThe current of tube Q3 begins to increase, its rate of increase and IL1The rate of reduction is the same. Until time t3, IL1Reduced to zero, UC1Increase to a positive maximum U2, i.e. IL1=0, and UC1=U2（U2>E) Where U2 is the maximum value of the voltage across the resonant capacitor, at this time, the third timing sequence is started.
Step 303: and in a third time sequence, keeping the first inversion switch open and the second inversion switch closed, and controlling the first switch to be open.
In the third timing (time period t3 to t 5), as shown in fig. 4d, the control unit 50 controls the IGBT switching tube Q1 to be turned off, and keeps the IGBT switching tube Q3 closed and the IGBT switching tube Q2 turned off. During the time period t3 to t 4: when the second diode D2 starts to conduct, the IGBT transistor Q1 is short-circuited, and the current flowing through the IGBT transistor Q1 is zero, the IGBT transistor Q1 is turned off at the time when the third timing sequence starts, and the IGBT transistor Q1 can realize zero-current soft turn-off. From time t3, the circuit continues to resonate, resonant capacitor C1 charges resonant inductor L1 in reverse, and UC1Start to decrease, IL1And increases in the opposite direction. When U is turnedC1Reduced to zero, IL1And increases in the reverse direction to the maximum value, at which the value of the current flowing through the second diode D2 is at the maximum value. Thereafter, the resonant inductor L1 reversely charges the resonant capacitor C1.
In this embodiment, by turning off the IGBT switch Q1 during the time that the second diode D2 turns on the freewheeling, the IGBT switch Q1 may achieve zero current turn-off.
Until time t4, IL1Reverse direction decreases to zero, UC1Increasing to an inverted maximum. At this time, as shown in connection with FIG. 4e, during the time period t4 to t 5: i isL1The reverse direction decreases to zero, the second diode D2 turns off naturally, the first diode D1 starts to conduct, the resonant capacitor C1 charges the resonant inductor L1, UC1Decrease of IL1And is increased. When U is turnedC1When the voltage is decreased to be equal to the bus voltage (i.e., the voltage value E of the DC power supply 200), IL1The maximum value is reached, and at this time, the value of the current flowing through the first diode D1 becomes maximum. Thereafter, IL1The decrease is started.
Further onIn one embodiment, referring to FIG. 5, at time t5, IL1Decreases to zero again and UC1Increase to U3, i.e. IL1=0, and UC1=U3（-E<U3<0). At this time, the sustain timing is started.
In the maintenance timing (i.e., the time period t5-t 6), the control unit 50 controls the IGBT switching tube Q1 to remain open from the IGBT switching tube Q2, and controls the IGBT switching tube Q3 to remain closed. As can be seen from fig. 4f, the first diode D1 is naturally turned off, the load current I0 is all freewheeling via the IGBT transistor Q3, and the resonant current I is made to followL1Is maintained at 0, and the resonant voltage U is setC1Maintained as U3. The duration of the maintenance sequence may be set according to actual needs, and the fourth sequence may be started at the time when the maintenance sequence ends.
Step 304: and in the fourth time sequence, keeping the first inversion switch open and the second inversion switch closed, and controlling the first switch to be closed.
In the fourth timing (i.e., the time period from t6 to t 7), as shown in fig. 4g, the control unit 50 controls the IGBT switching tube Q1 to be closed, and keeps the IGBT switching tube Q3 closed and the IGBT switching tube Q2 open. Because resonant inductor L1 reduces the rate of rise of current through IGBT switch Q1, IGBT switch Q1 achieves zero current soft-on. During the time period t6 to t 7: after the IGBT switching tube Q1 is closed, the resonant inductor L1 and the resonant capacitor C1 start to resonate, the resonant capacitor C1 charges the resonant inductor L1, and IL1Increase, UC1Decreases and the current through the IGBT switch Q3 begins to decrease, at a rate corresponding to IL1The rate of increase is the same. Until time t7, IL1When increasing to equal load current I0, UC1Decreases to U4, and the current through IGBT switch tube Q3 decreases to zero, i.e. IL1= I0, and UC1=U4（-E<U3<U4<0) At this time, the fifth timing is started.
Step 305: and in a fifth time sequence, keeping the first switch closed and the first inversion switch open, and controlling the second inversion switch to be open.
In a fifth timing (i.e., time period t7-t 10), as shown in connection with FIG. 4h, the control unit 50 controls the IGBT switchTube Q3 opens and keeps IGBT switch tube Q1 closed and IGBT switch tube Q2 open. Body diode D of IGBT switching tube Q3Q3And starting to conduct freewheeling, and turning off the IGBT switching tube Q3 at the moment, so that the IGBT switching tube Q3 can realize zero-voltage zero-current soft turn-off. During the time period t7 to t 8: the resonant capacitor C1 continues to charge the resonant inductor L1, IL1Continue to increase as UC1Decreasing the reverse direction to zero, IL1The current value flowing through the IGBT switching tube Q1 becomes maximum at this time. Thereafter, the resonant inductor L1 discharges and the resonant capacitor C1 charges.
Until time t8, IL1To I0. As shown in connection with FIG. 4i, during the time period t8 to t 9: the second diode D2 turns off naturally, at this time, because the IGBT switch Q2 is in the off state, the load current I0 charges the resonant capacitor C1, because the load current I0 is constant, the end voltage of the resonant inductor L1 is zero, and U is zeroC1And gradually increases.
Until time t9, UC1Increasing to equal the bus voltage E. As shown in connection with FIG. 4j, during the time period t9 to t 10: body diode D of IGBT switching tube Q2Q2The follow current is conducted, the resonant inductor L1 and the resonant capacitor C1 resonate again, the resonant inductor L1 discharges, the resonant capacitor C1 charges, and therefore IL1Decrease of UC1And is increased. Until time t10, IL1Reduced to zero, UC1Increase to a maximum value U2, i.e. IL1=0, and UC1= U2, at this time, the load current I0 all freewheels through the first diode D1, and the sixth timing starts to be executed.
Step 306: and in the sixth time sequence, the first inversion switch is kept disconnected and the second inversion switch is kept disconnected, and the first switch is controlled to be disconnected.
In the sixth timing (i.e. the time period from t10 to t 11), as shown in fig. 4k, the control unit 50 controls the IGBT switching tube Q1 to turn off, and keeps the IGBT switching tube Q2 and the IGBT switching tube Q3 to turn off. At the beginning of the sixth timing sequence, the load current I0 passes through the body diode D of the IGBT switch tube Q2Q2And the IGBT switching tube Q1 can realize zero current soft turn-off after freewheeling. During the time period t10 to t 11: resonant capacitor C1 reversely charges resonant inductor L1, IL1Increase in the reverse direction, UC1Decreasing, the current through the second diode D2 gradually increases, and the current through the first diode D1 gradually decreases at a rate corresponding to IL1The rate of reverse increase is the same. When U is turnedC1When reduced to E, IL1Reaches a maximum, after which the resonant inductor L1 discharges, IL1Decrease of UC1The decrease continues.
Until time t11, IL1Decreasing to zero, the second diode D2 turns off naturally. At this time UC1Reduced to U0, the load current I0 passes through the body diode D of the IGBT switch tube Q2Q2Free wheeling, i.e. IL1=0, and UC1= U0. Thus, the inverter circuit 100 starts to enter the initial state again.
The above embodiment describes a complete control process of the driving method in one PWM period, and by continuously repeating the above process, the direct current input by the direct current power supply 200 can be continuously converted into the alternating current for output.
In addition, when the first switch in the inverter circuit 100 needs to be switched, the resonant action of the resonant unit 30 can make the current change rate of the first switch at the switching-on moment smaller than the allowable current change rate thereof, which is beneficial to the first switch to realize zero current switching-on within the full load range, thereby achieving the purpose of reducing the switching loss. It should be understood that when the rate of change of the current of the first switch at the moment of turning on is less than the rate of change of the current allowed by the first switch, the current of the first switch at the moment of turning on can be approximately considered to be zero.
Next, as is clear from the above embodiment, the second switch is turned off during the freewheeling period of the body diode of the second switch, and zero-current turn-off of the second switch can be achieved; the third switch is turned off during freewheeling of the body diode of the third switch, enabling zero current turn-off of the third switch. In one embodiment, when the second switch or the third switch is turned off, the maximum value Ipmax of the resonance current in the resonance unit satisfies: i0max is less than or equal to Ipmax is less than or equal to 2I0max, wherein I0max is the maximum value of the load current, so that the second switch or the third switch can realize zero current disconnection in a full load range, and the switching loss can be further reduced.
Meanwhile, the structure of the inverter circuit 100 is simple, which is beneficial to simplifying a control strategy, and the size of an inverter including the inverter circuit 100 can be reduced, and the cost of the inverter including the inverter circuit 100 can be reduced.
In the above embodiment, the first inverter switch and the second inverter switch in the arm unit 40 correspond to the second switch (IGBT switch tube Q2) and the third switch (IGBT switch tube Q3), respectively, as an example. In another embodiment, the first inverter switch and the second inverter switch in the bridge arm unit 40 may respectively correspond to the third switch (IGBT switch tube Q3) and the second switch (IGBT switch tube Q2), and the working process thereof is similar to that of the above embodiment, which is within the scope easily understood by those skilled in the art and will not be described herein again.
Next, in this embodiment, the IGBT switching tube Q2 is kept turned off in one PWM cycle, and then, in the next PWM cycle, the IGBT switching tube Q3 is kept turned off. That is, in the embodiment of the present application, if the first inverter switch in arm cell 40 is kept off in any one PWM period, the second inverter switch in arm cell 40 should be kept off in a PWM period adjacent to the PWM period.
Fig. 6 is a schematic structural diagram of a driving apparatus 600 according to an embodiment of the present disclosure, where the driving apparatus 600 is used for driving the inverter circuit 100 shown in fig. 1 or fig. 2. As shown in fig. 6, the driving apparatus 600 includes a first switch control unit 601, a second switch control unit 602, a third switch control unit 603, a fourth switch control unit 604, a fifth switch control unit 605, and a sixth switch control unit 606.
The first switch control unit 601 is used for controlling the first switch to be closed and the first inverter switch and the second inverter switch of the bridge arm unit to be opened in the first timing sequence, so as to enable the first switch and the second switch to be connected in seriesL1= I0, perform second timing; wherein, IL1I0 is the load current, which is the resonant current in the resonant cell. The second switch control unit 602 is configured to keep the first switch closed and the first inverter switch open in the second timing sequence, and control the second switchThe inverter switch is closed to make IL1=0，UC1= U2, perform third timing; wherein, UC1U2 is the maximum forward voltage of the resonant cell, which is the resonant voltage in the resonant cell. The third switch control unit 603 is configured to, in a third timing sequence, keep the first inverter switch open and the second inverter switch closed, and control the first switch to open so that IL1=0, and UC1=U3（-E<U3<0) Executing the fourth timing; wherein E is a voltage value of the dc power supply. The fourth switch control unit 604 is configured to keep the first inverter switch open and the second inverter switch closed in the fourth timing, and control the first switch to be closed, so that IL1= I0, the fifth timing is performed. The fifth switch control unit 605 is configured to keep the first switch closed and the first inverter switch open, and control the second inverter switch to open in the fifth timing sequence, so as to enable IL1=0, and UC1= U2, sixth timing is performed. The sixth switch control unit 606 is configured to keep the first inverter switch off and the second inverter switch off in the sixth timing sequence, and control the first switch to be turned off, so that IL1=0, and UC1= U0, and returns the inverter circuit to the initial state; wherein, U0 is the initial voltage value of the resonance unit when the inverter circuit is in the initial state.
Since the apparatus embodiment and the method embodiment are based on the same concept, the contents of the apparatus embodiment may refer to the method embodiment on the premise that the contents do not conflict with each other, and are not described herein again.
Embodiments of the present application also provide a non-transitory computer-readable storage medium, which stores computer-executable instructions, and when the computer-executable instructions are executed by a processor, the processor is caused to execute the driving method in any of the above embodiments.
Embodiments of the present application further provide a computer program product, which includes a computer program stored on a computer-readable storage medium, where the computer program includes program instructions, and when the program instructions are executed by a computer, the computer executes the driving method in any of the above embodiments.
The embodiment of the application also provides a multi-phase inverter circuit, which comprises at least two inverter circuits in any one of the above embodiments. One end of the first switch in each inverter circuit is connected with the negative electrode of the direct current power supply, and two ends of the follow current unit in each inverter circuit are respectively connected with two ends of the direct current power supply.
Referring to fig. 7, fig. 7 illustrates a three-way inverter circuit as an example.
As shown in fig. 7, one of the paths is an inverter circuit 100 a. The sources of the IGBT Q11 of the first inverter circuit 100a, the IGBT Q12 of the second inverter circuit, and the IGBT Q13 of the third inverter circuit are all connected to the negative electrode of the dc power supply 200. The first end of the follow current unit of the first-path inverter circuit, the first end of the follow current unit of the second-path inverter circuit and the first end of the follow current unit of the third-path inverter circuit are connected with the positive electrode of the direct-current power supply 200 at a first connection point P1, and the second end of the follow current unit of the first-path inverter circuit, the second end of the follow current unit of the second-path inverter circuit and the second end of the follow current unit of the third-path inverter circuit are connected with the negative electrode of the direct-current power supply 200 at a second connection point P2.
In one embodiment, each of the inverter circuits can be driven by any of the driving methods described in the above embodiments. For example, when the inverter circuit 100a is driven through step 301 in the driving method, that is, in the first timing, the control unit 50 controls the IGBT switching tube Q11 to be closed and controls the IGBT switching tube Q21 and the IGBT switching tube Q31 to be opened, so that the current flowing through the inductor L11 is 0, and the second timing is performed.
The embodiment of the present application further provides an inverter, which includes the inverter circuit in any one of the above embodiments, or includes the inverter circuit in any one of the above embodiments and the driving method in any one of the above embodiments, or includes the multi-phase inverter circuit in any one of the above embodiments.
Finally, it should be noted that: the above embodiments are only used to illustrate the technical solutions of the present application, and not to limit the same; within the context of the present application, where technical features in the above embodiments or in different embodiments can also be combined, the steps can be implemented in any order and there are many other variations of the different aspects of the present application as described above, which are not provided in detail for the sake of brevity; although the present application has been described in detail with reference to the foregoing embodiments, it should be understood by those of ordinary skill in the art that: the technical solutions described in the foregoing embodiments may still be modified, or some technical features may be equivalently replaced; and the modifications or the substitutions do not make the essence of the corresponding technical solutions depart from the scope of the technical solutions of the embodiments of the present application.

Claims (9)

1. An inverter circuit, comprising:
the device comprises a first switch, a follow current unit, a resonance unit, a bridge arm unit and a control unit;
the first switch is respectively connected with the midpoint of the follow current unit and the DC power supply, the resonance unit is respectively connected with the midpoint of the follow current unit and the midpoint of the bridge arm unit, the midpoint of the bridge arm unit is also used for being connected with a load, the follow current unit is connected with the bridge arm unit in parallel, and the follow current unit and the bridge arm unit are both connected with the DC power supply;
the bridge arm unit comprises a first inversion switch and a second inversion switch;
the second end of the first inverter switch and the third end of the second inverter switch are both connected with the resonance unit, the third end of the first inverter switch is connected with the positive electrode of the direct-current power supply, and the second end of the second inverter switch is connected with the negative electrode of the direct-current power supply;
the control unit is respectively connected with the first end of the first switch, the first end of the first inversion switch and the first end of the second inversion switch, and the control unit is used for:
in a first time sequence, a first inversion switch and a second inversion switch of the bridge arm unit are controlled to be switched off, and the first switch is controlled to be switched on at the moment when the first time sequence starts, so that IL1= I0, perform second timing; wherein, IL1For resonant electricity in said resonant cellsI0 is the load current;
in the second time sequence, keeping the first switch closed and the first inversion switch open, and controlling the second inversion switch to be closed at the beginning time of the second time sequence so as to enable IL1=0，UC1= U2, perform third timing; wherein, UC1Is the resonance voltage in the resonance unit, U2 is the maximum value of the forward voltage of the resonance unit;
in the third time sequence, keeping the first inversion switch open and the second inversion switch closed, and controlling the first switch to be open at the beginning of the third time sequence so as to enable IL1=0, and UC1= U3, execute fourth timing; wherein-E<U3<0 and E are voltage values of the direct current power supply;
in the fourth time sequence, keeping the first inversion switch open and the second inversion switch closed, and controlling the first switch to be closed at the beginning of the fourth time sequence so as to enable IL1= I0, perform fifth timing;
in the fifth time sequence, keeping the first switch closed and the first inversion switch open, and controlling the second inversion switch to open at the time when the fifth time sequence starts so as to enable IL1=0, and UC1= U2, execute sixth timing;
in the sixth time sequence, keeping the first inversion switch and the second inversion switch off, and controlling the first switch to be switched off at the beginning of the sixth time sequence so as to enable IL1=0, and UC1= U0, and causes the inverter circuit to recover to an initial state; u0 is the initial voltage value of the resonance unit when the inverter circuit is in the initial state.
2. The inverter circuit according to claim 1,
the resonance unit comprises a resonance inductor and a resonance capacitor;
the resonance inductor is connected with the resonance capacitor in series, the non-series end of the resonance inductor is connected with the midpoint of the follow current unit, and the non-series end of the resonance capacitor is connected with the midpoint of the bridge arm unit.
3. The inverter circuit according to any one of claims 1 to 2,
the follow current unit comprises a first diode and a second diode;
the cathode of the first diode is connected with the anode of the direct current power supply, the anode of the first diode is connected with the cathode of the second diode, and the anode of the second diode is connected with the cathode of the direct current power supply;
and the connection point between the first diode and the second diode is the midpoint of the free-wheeling unit.
4. A driving method of an inverter circuit for driving the inverter circuit according to any one of claims 1 to 3, the driving method comprising:
in a first time sequence, a first inversion switch and a second inversion switch of the bridge arm unit are controlled to be switched off, and the first switch is controlled to be switched on at the moment when the first time sequence starts, so that IL1= I0, perform second timing; wherein, IL1Is the resonance current in the resonance unit, I0 is the load current;
in the second time sequence, keeping the first switch closed and the first inversion switch open, and controlling the second inversion switch to be closed at the beginning time of the second time sequence so as to enable IL1=0，UC1= U2, perform third timing; wherein, UC1Is the resonance voltage in the resonance unit, U2 is the maximum value of the forward voltage of the resonance unit;
in the third time sequence, keeping the first inversion switch open and the second inversion switch closed, and controlling the first switch to be open at the beginning of the third time sequence so as to enable IL1=0, and UC1= U3, execute fourth timing; wherein-E<U3<0 and E are voltage values of the direct current power supply;
in the fourth time sequence, keeping the first inversion switch open and the second inversion switch closed, and controlling the first switch to be closed at the beginning of the fourth time sequence so as to enable IL1= I0, perform fifth timing;
in the fifth time sequence, keeping the first switch closed and the first inversion switch open, and controlling the second inversion switch to open at the time when the fifth time sequence starts so as to enable IL1=0, and UC1= U2, execute sixth timing;
in the sixth time sequence, keeping the first inversion switch and the second inversion switch off, and controlling the first switch to be switched off at the beginning of the sixth time sequence so as to enable IL1=0, and UC1= U0, and causes the inverter circuit to recover to an initial state; u0 is the initial voltage value of the resonance unit when the inverter circuit is in the initial state.
5. The driving method of the inverter circuit according to claim 4, further comprising an initial timing;
and in the initial time sequence, controlling the first switch, the first inverter switch and the second inverter switch to be disconnected so as to enable the inverter circuit to be in the initial state, and executing the first time sequence.
6. The driving method of the inverter circuit according to claim 4 or 5, further comprising maintaining a timing;
in the third sequence, when the IL1=0, and UC1= U3, the maintaining timing is performed in which the fourth timing is performed after keeping the first switch and the first inversion switch open and the second inversion switch closed to maintain the resonance current to 0 and the resonance voltage to U3.
7. A multiphase inverter circuit comprising at least two inverter circuits according to any one of claims 1 to 3;
one end of the first switch in each inverter circuit is used for being connected with the negative electrode of the direct current power supply, and two ends of the follow current unit in each inverter circuit are respectively connected with two ends of the direct current power supply.
8. The multiphase inverter circuit of claim 7,
any one of the inverter circuits is driven by the driving method according to any one of claims 4 to 6.
9. An inverter comprising the inverter circuit according to any one of claims 1 to 3;
or, comprising the inverter circuit according to any one of claims 1 to 3 and the driving method according to any one of claims 4 to 6;
or, comprising a multi-phase inverter circuit according to any of claims 7-8.
CN202110938748.6A 2021-08-16 2021-08-16 Inverter circuit, driving method thereof, multiphase inverter circuit and inverter Active CN113395005B (en)

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