CN113346758B - Double-active-bridge four-degree-of-freedom optimal modulation control method - Google Patents

Double-active-bridge four-degree-of-freedom optimal modulation control method Download PDF

Info

Publication number
CN113346758B
CN113346758B CN202110717411.2A CN202110717411A CN113346758B CN 113346758 B CN113346758 B CN 113346758B CN 202110717411 A CN202110717411 A CN 202110717411A CN 113346758 B CN113346758 B CN 113346758B
Authority
CN
China
Prior art keywords
active
double
bridge converter
modulation
modulation mode
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
CN202110717411.2A
Other languages
Chinese (zh)
Other versions
CN113346758A (en
Inventor
王弥新
潘三博
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Shanghai Dianji University
Original Assignee
Shanghai Dianji University
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Shanghai Dianji University filed Critical Shanghai Dianji University
Priority to CN202110717411.2A priority Critical patent/CN113346758B/en
Publication of CN113346758A publication Critical patent/CN113346758A/en
Application granted granted Critical
Publication of CN113346758B publication Critical patent/CN113346758B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33584—Bidirectional converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention relates to a double-active-bridge four-degree-of-freedom optimal modulation control method, wherein an internal phase shift angle is additionally arranged between a first primary side switching tube and a fourth primary side switching tube of a double-active-bridge converter, and the control method specifically comprises the following steps: s1, calculating to obtain an inductive current peak value and a transmission power of the modulation mode through time domain analysis according to 2 preset modulation modes and the reference power and the reference current of the double-active-bridge converter; s2, based on the KKT condition, calculating to obtain an optimal solution of the modulation mode by taking the peak-to-peak value of the inductive current of the modulation mode as an optimization target and the transmission power as a constraint condition; and S3, obtaining the global optimal solution by comparing the peak value of the inductive current of the optimal solution of the modulation mode, taking the modulation mode with the minimum peak value of the inductive current of each power section, and controlling the switching tube of the double-active-bridge converter according to the global optimal solution. Compared with the prior art, the invention has the advantages of improving the flexibility of controlling voltage conversion, improving the soft switching performance under light load and the like.

Description

Double-active-bridge four-degree-of-freedom optimal modulation control method
Technical Field
The invention relates to the technical field of power electronic converters, in particular to a double-active-bridge four-degree-of-freedom optimal modulation control method.
Background
For a Dual Active Bridge converter (DAB), when the voltage gain deviates from 1, a large return power is generated at light load by using a conventional Single Phase Shift (SPS), which causes a sharp increase in current stress and a reduction in efficiency. In recent years, to solve this problem, many researchers have proposed modulation strategies such as Double Phase Shift (DPS), Extended Phase Shift (EPS), Triple Phase Shift (TPS) to optimize the efficiency of the Dual active bridge converter, so that the converter can keep high efficiency operation even under light load without increasing the complexity of the circuit topology, but most of these modulation strategies use the stress of the inductor current or the effective value of the inductor current as the optimization target, which makes the soft switching performance of the DAB converter still worse under light load. The common property of these modulation strategies is that all switching tubes are turned on at 50% duty cycle, which is called symmetric duty ratio air conditioning strategy, and this kind of modulation strategy only contains 3 degrees of freedom at most.
Disclosure of Invention
The invention aims to provide a double-active-bridge four-degree-of-freedom optimal modulation control method for overcoming the defects of poor soft switching performance under light load and poor flexibility during modulation caused by insufficient control degree of freedom in the prior art.
The purpose of the invention can be realized by the following technical scheme:
a double-active-bridge four-degree-of-freedom optimal modulation control method is based on a double-active-bridge converter, the double-active-bridge converter comprises two H bridges consisting of 8 switching tubes, two voltage-stabilizing filter capacitors, a high-frequency transformer and an auxiliary inductor, each H bridge comprises 4 switching tubes, the H bridge with the auxiliary inductor is the primary side of the double-active-bridge converter, the other H bridge is the secondary side of the double-active-bridge converter, the 4 switching tubes on the primary side of the double-active-bridge converter operate at a duty ratio of not 50%, the 4 switching tubes on the secondary side of the double-active-bridge converter operate at a duty ratio of 50%, the primary side of the double-active-bridge converter comprises a first primary side switching tube, a second primary side switching tube, a third primary side switching tube and a fourth primary side switching tube, an internal phase shift angle is additionally arranged between the first primary side switching tube and the fourth primary side switching tube, and the control method specifically comprises the following steps:
s1, calculating inductance current peak values and transmission power of 2 modulation modes through time domain analysis according to the preset 2 modulation modes and the reference power and the reference current of the double-active-bridge converter;
s2, based on the KKT condition, calculating to obtain an optimal solution of 2 modulation modes by taking the peak-to-peak value of the inductive current of the modulation modes as an optimization target and the transmission power as a constraint condition;
s3, comparing the peak value of the inductive current of the optimal solution of the 2 modulation modes, taking the modulation mode with the minimum peak value of the inductive current of each power section, calculating to obtain the global optimal solution of the whole power section, and controlling the switching tube of the double-active-bridge converter according to the global optimal solution.
The calculation formula of the reference power of the double-active-bridge converter is as follows:
Figure BDA0003135411960000021
wherein P is the reference power of the double active bridge converter, V 1 Is the input voltage of the primary side, L is the inductance of the auxiliary inductor, f s The switching frequency of the dual active bridge converter.
The calculation formula of the reference current of the double-active-bridge converter is as follows:
Figure BDA0003135411960000022
wherein, I is the reference current of the double active bridge converter.
The 2 modulation modes are set according to the constraint conditions of the phase shift angles of the primary side and the secondary side of the double-active-bridge converter and comprise a first modulation mode and a second modulation mode.
Further, the secondary side of the dual-active bridge converter comprises a first secondary side switching tube, a second secondary side switching tube, a third secondary side switching tube and a fourth secondary side switching tube, and the constraint conditions of the first modulation mode are as follows:
Figure BDA0003135411960000023
the constraints of the second modulation mode are as follows:
Figure BDA0003135411960000031
wherein D is 1 Is the ratio of the time of the primary side high level in one period of the double active bridge converter to one period, D 2 The ratio of the time of the high level of the secondary side in one period to one period, D 3 The ratio of the phase-staggered time of the first primary side switch tube and the fourth secondary side switch tube in one period, D 4 The internal phase shift angle is additionally arranged between the first primary side switching tube and the fourth primary side switching tube, and specifically is the ratio of the phase-staggered time of the first primary side switching tube and the fourth primary side switching tube in one period.
Further, the calculation formulas of the peak-to-peak inductor current value and the transmission power of the first modulation mode are as follows:
I pp1 ＝4(2D 1 +(-2D 1 +2D 2 +4D 3 -2D 4 -1)M)
Figure BDA0003135411960000032
wherein, I pp1 Peak to peak inductor current, P, for the first modulation mode 1 M is a voltage conversion ratio for the transmission power of the first modulation mode;
the calculation formulas of the peak-to-peak value of the inductor current and the transmission power of the second modulation mode are as follows:
I pp2 ＝4(2D 1 +(-2D 1 +2D 2 +4D 3 -2D 4 -1)M)
Figure BDA0003135411960000033
wherein, I pp2 Peak-to-peak inductor current, P, for the second modulation mode 2 The transmission power of the second modulation mode.
The calculation formula of the voltage conversion ratio is as follows:
Figure BDA0003135411960000034
wherein, V 1 Is the input voltage, V, of a dual active bridge converter 2 The output voltage of the double-active-bridge converter is obtained, and n is the transformation ratio of the transformer.
Further, the optimal solution of the first modulation mode is specifically as follows:
Figure BDA0003135411960000041
the optimal solution of the second modulation mode is specifically as follows:
Figure BDA0003135411960000042
wherein D is 1,op Is D 1 Optimal solution in the corresponding modulation mode, D 2,op Is D 2 Optimal solution in the corresponding modulation mode, D 3,op Is D 3 Optimal solution in the corresponding modulation mode, D 4,op Is D 4 Optimal solution, P, in the respective modulation mode c Is the critical power point.
The calculation formula of the critical power point is specifically as follows:
P c ＝-2M 3 +2M 2
wherein, P c Is the critical power point of the dual active bridge converter.
The calculation formula of the global optimal solution is as follows:
Figure BDA0003135411960000051
Figure BDA0003135411960000052
wherein D is 1,op1 Is D 1 Global optimal solution of, D 2,op2 Is D 2 Global optimal solution of, D 3,op3 Is D 3 Global optimal solution of, D 4,op4 Is D 4 The global optimum solution of (2).
Compared with the prior art, the invention has the following beneficial effects:
1. according to the invention, an internal shift phase angle is additionally arranged between the first primary side switching tube and the fourth primary side switching tube, and the double-active-bridge converter is controlled through a modulation mode with 4 control degrees of freedom, so that the flexibility of controlling voltage conversion is effectively improved, and the processing efficiency of the double-active-bridge converter in the face of various voltage requirements is improved.
2. According to the invention, the primary side of the double-active-bridge converter is operated at a duty ratio of not 50%, the secondary side of the double-active-bridge converter is operated at a duty ratio of 50%, and through time domain analysis, the lowest peak value of the inductive current is realized in a full power range, so that the conduction loss is greatly reduced, and meanwhile, the soft switching performance under light load is also greatly improved.
Drawings
FIG. 1 is a schematic diagram of a dual active bridge converter according to the present invention;
FIG. 2 is a waveform diagram illustrating a first modulation mode according to the present invention;
FIG. 3 is a waveform diagram illustrating a second modulation mode according to the present invention;
FIG. 4 is a control block diagram of a global optimal solution in an embodiment of the present invention;
fig. 5 is a schematic structural diagram of a driving module according to an embodiment of the present invention.
Detailed Description
The invention is described in detail below with reference to the figures and specific embodiments. The present embodiment is implemented on the premise of the technical solution of the present invention, and a detailed implementation manner and a specific operation process are given, but the scope of the present invention is not limited to the following embodiments.
Examples
As shown in figure 1, the double-active-bridge four-degree-of-freedom optimal modulation control method improves the flexibility of voltage conversion control and soft switching performance in light load, and is based on a double-active-bridge converter which comprises 8 switching tubes (S) 1 -S 4 And Q 1 -Q 4 ) Two H-bridges and two voltage-stabilizing filter capacitors C 1 And C 2 A high-frequency transformer T and auxiliary inductors L, each H-bridge comprising 4 switching tubes, an H-bridge with auxiliary inductors (S) 1 -S 4 ) Is the primary side of a double active bridge converter, the other H-bridge (Q) 1 -Q 4 ) The control method specifically comprises the following steps of:
s1, calculating inductance current peak values and transmission power of 2 modulation modes through time domain analysis according to the preset 2 modulation modes and the reference power and the reference current of the double-active-bridge converter;
s2, based on the KKT condition, calculating to obtain an optimal solution of 2 modulation modes by taking the peak-to-peak value of the inductive current of the modulation modes as an optimization target and the transmission power as a constraint condition;
and S3, comparing the peak value of the inductive current of the optimal solution of the 2 modulation modes, taking the modulation mode with the minimum peak value of the inductive current of each power section, calculating to obtain the global optimal solution of the whole power section, and controlling the switching tube of the double-active-bridge converter according to the global optimal solution.
The calculation formula of the reference power of the dual-active-bridge converter is as follows:
Figure BDA0003135411960000071
wherein P is the reference power of the double active bridge converter, V 1 Is the input voltage of the primary side, L is the inductance of the auxiliary inductor, f s The switching frequency of the dual active bridge converter.
The calculation formula of the reference current of the double-active-bridge converter is as follows:
Figure BDA0003135411960000072
wherein, I is the reference current of the double active bridge converter.
As shown in fig. 2 and 3, 2 modulation modes are set according to the constraint condition of the phase shift angle of the primary side and the secondary side of the dual active bridge converter, including a first modulation mode and a second modulation mode, where T is s The duration of one cycle of the dual active bridge converter.
The secondary side of the double-active-bridge converter comprises a first secondary side switching tube, a second secondary side switching tube, a third secondary side switching tube and a fourth secondary side switching tube, and the constraint conditions of a first modulation mode are as follows:
Figure BDA0003135411960000073
the constraints of the second modulation mode are as follows:
Figure BDA0003135411960000074
wherein D is 1 Is the ratio of the time of the primary side high level in one period of the double active bridge converter to one period, D 2 The ratio of the time of the high level of the secondary side in one period to one period, D 3 The ratio of the phase-staggered time of the first primary side switch tube and the fourth secondary side switch tube in one period, D 4 The internal phase shift angle is additionally arranged between the first primary side switching tube and the fourth primary side switching tube, and specifically is the ratio of the phase-staggered time of the first primary side switching tube and the fourth primary side switching tube in one period.
The calculation formula of the peak-to-peak inductor current value and the transmission power in the first modulation mode is as follows:
I pp1 ＝4(2D 1 +(-2D 1 +2D 2 +4D 3 -2D 4 -1)M)
Figure BDA0003135411960000081
wherein, I pp1 Peak-to-peak inductor current, P, for the first modulation mode 1 M is a voltage conversion ratio for the transmission power of the first modulation mode;
the calculation formulas of the peak-to-peak inductor current value and the transmission power in the second modulation mode are as follows:
I pp2 ＝4(2D 1 +(-2D 1 +2D 2 +4D 3 -2D 4 -1)M)
Figure BDA0003135411960000082
wherein, I pp2 Peak-to-peak inductor current, P, for the second modulation mode 2 The transmission power of the second modulation mode.
The calculation formula of the voltage conversion ratio is as follows:
Figure BDA0003135411960000083
wherein, V 1 Is the input voltage, V, of a dual active bridge converter 2 The voltage is the output voltage of the double-active-bridge converter, and n is the transformation ratio of the transformer.
The optimal solution for the first modulation mode is specifically as follows:
Figure BDA0003135411960000084
the optimal solution for the second modulation mode is specifically as follows:
Figure BDA0003135411960000091
wherein D is 1,op Is D 1 Optimal solution in the corresponding modulation mode, D 2,op Is D 2 Optimal solution in the corresponding modulation mode, D 3,op Is D 3 Optimal solution in the corresponding modulation mode, D 4,op Is D 4 Optimal solution, P, in the corresponding modulation mode c Is the critical power point.
The calculation formula of the critical power point is specifically as follows:
P c ＝-2M 3 +2M 2
wherein, P c Is the critical power point of the dual active bridge converter.
The calculation formula of the global optimal solution is as follows:
Figure BDA0003135411960000092
Figure BDA0003135411960000101
wherein D is 1,op1 Is D 1 Global optimal solution of, D 2,op2 Is D 2 Global optimal solution of, D 3,op3 Is D 3 Global optimal solution of, D 4,op4 Is D 4 The global optimum solution of (2).
In specific implementation, as shown in FIG. 4, a given output voltage V is provided ref With the actual output voltage V 2 Inputting the difference into a PI controller, obtaining real-time reference power P through the PI controller, simultaneously calculating to obtain a real-time voltage conversion ratio M, and finally obtaining D 1 、D 2 、D 3 And D 4 To drive the 8 switching tubes of the DAB-converter.
In this embodiment, based on Matlab/Simulink, a DAB converter simulation platform based on a four-degree-of-freedom modulation strategy and conventional single phase shift modulation is established, and simulation parameters are shown in table 1:
TABLE 1DAB converter simulation platform parameters
Input voltage V 1 200V
Output voltage V 2 30-100V
Transformer transformation ratio n 2:1
Auxiliary inductor L 238μH
Switching frequency f s 50K
Maximum transmission power P b 420W
For the DAB converter based on the four-degree-of-freedom modulation strategy, the DAB converter comprises a main circuit module, a driving module, a waveform observing module and an efficiency measuring module, as shown in fig. 5, the driving module is divided into calculation of degrees of freedom and generation of driving waveforms, and the driving waveforms of the switching tubes are obtained by comparing the combination of the four degrees of freedom with triangular waves with amplitude of 1 and frequency of 50K.
For the simulation method of the single phase-shift modulation strategy, the main circuit parameters, the test module and the efficiency model of the simulation method are all consistent with the simulation parameters of the four-degree-of-freedom modulation strategy, and only the configuration of the driving module is changed, which is similar to the driving module of the four-degree-of-freedom modulation control method.
The method ensures that the working conditions of the strategy provided by the invention are consistent with the working conditions of a single phase-shifting modulation strategy by giving the same group of reference power P and a voltage conversion ratio M, and respectively measures the peak value of the inductive current, the effective value of the inductive current and the efficiency of the two modulation strategies under different powers when M is 0.3, M is 0.5 and M is 0.8 through simulation. Where the expression for efficiency is as follows:
Figure BDA0003135411960000111
wherein, P out To average output power, P in Is the average input power.
Magnetic loss of the transformer is ignored in simulation, line loss in an actual circuit and loss of auxiliary power supplies for the driving circuit and the sampling circuit are also ignored, so that the efficiencies of two modulation strategies in simulation results are higher than those in the actual process, and the final simulation results are shown in table 2:
table 2 simulation data of the present invention and conventional modulation strategies
Figure BDA0003135411960000112
Based on the simulation results of table 2, it is shown that the peak-to-peak value and the effective value of the inductive current in the simulation results based on the invention are both lower than those of the traditional single phase-shift modulation strategy, and the efficiency is obviously improved, especially when the voltage conversion ratio is very small and the effect is most obvious at light load.
Furthermore, it should be noted that the specific embodiments described in this specification may have different names, and the above description is only an illustration of the structure of the present invention. All equivalent or simple changes in the structure, characteristics and principles of the invention are included in the protection scope of the invention. Various modifications or additions may be made to the described embodiments or methods may be similarly employed by those skilled in the art without departing from the scope of the invention as defined in the appending claims.

Claims (6)

1. A double-active bridge four-freedom-degree optimal modulation control method is based on a double-active bridge converter, the double-active-bridge converter comprises two H bridges consisting of 8 switching tubes, two voltage-stabilizing filter capacitors, a high-frequency transformer and auxiliary inductors, each H bridge comprises 4 switching tubes, the H bridge with the auxiliary inductors is the primary side of the double-active-bridge converter, the other H bridge is the secondary side of the double-active-bridge converter, it is characterized in that 4 switching tubes on the primary side of the double-active-bridge converter operate at a non-50% duty ratio, 4 switching tubes on the secondary side of the double-active-bridge converter operate at a 50% duty ratio, the primary side of the double-active-bridge converter comprises a first primary side switching tube, a second primary side switching tube, a third primary side switching tube and a fourth primary side switching tube, an internal phase shift angle is additionally arranged between the first primary side switching tube and the fourth primary side switching tube, and the control method specifically comprises the following steps:
s1, calculating inductance current peak values and transmission power of 2 modulation modes through time domain analysis according to the preset 2 modulation modes and the reference power and the reference current of the double-active-bridge converter;
s2, based on the KKT condition, calculating to obtain an optimal solution of 2 modulation modes by taking the peak-to-peak value of the inductive current of the modulation modes as an optimization target and the transmission power as a constraint condition;
s3, comparing the peak value of the inductive current of the optimal solution of the 2 modulation modes, taking the modulation mode with the minimum peak value of the inductive current of each power section, calculating to obtain the global optimal solution of the whole power section, and controlling the switching tube of the double-active-bridge converter according to the global optimal solution;
the calculation formula of the reference power of the double-active-bridge converter is as follows:
Figure FDA0003614872520000011
wherein P is the reference power of the double active bridge converter, V 1 Is the input voltage of the primary side, L is the inductance of the auxiliary inductor, f s The switching frequency of the double active bridge converter;
the 2 modulation modes are set according to the constraint conditions of the phase shifting angles of the primary side and the secondary side of the double-active-bridge converter and comprise a first modulation mode and a second modulation mode;
the secondary side of the double-active-bridge converter comprises a first secondary side switching tube, a second secondary side switching tube, a third secondary side switching tube and a fourth secondary side switching tube, and the constraint conditions of the first modulation mode are as follows:
Figure FDA0003614872520000021
the constraints of the second modulation mode are as follows:
Figure FDA0003614872520000022
wherein D is 1 Is the ratio of the time of the primary side high level in one period of the double active bridge converter to one period, D 2 The ratio of the time of the high level of the secondary side in one period to one period, D 3 The ratio of the phase-staggered time of the first primary side switch tube and the fourth secondary side switch tube in one period, D 4 An internal phase shift angle is additionally arranged between the first primary side switching tube and the fourth primary side switching tube, and specifically is the ratio of the phase-staggered time of the first primary side switching tube and the fourth primary side switching tube to one period;
the calculation formulas of the peak-to-peak value of the inductor current and the transmission power of the first modulation mode are as follows:
I pp1 ＝4(2D 1 +(-2D 1 +2D 2 +4D 3 -2D 4 -1)M)
Figure FDA0003614872520000023
wherein, I pp1 Peak-to-peak inductor current, P, for the first modulation mode 1 M is a voltage conversion ratio for the transmission power of the first modulation mode;
the calculation formulas of the peak-to-peak value of the inductor current and the transmission power of the second modulation mode are as follows:
I pp2 ＝4(2D 1 +(-2D 1 +2D 2 +4D 3 -2D 4 -1)M)
Figure FDA0003614872520000024
wherein, I pp2 Peak-to-peak inductor current, P, for the second modulation mode 2 The transmission power of the second modulation mode.
2. The dual-active-bridge four-degree-of-freedom optimal modulation control method according to claim 1, wherein a calculation formula of the reference current of the dual-active-bridge converter is as follows:
Figure FDA0003614872520000031
wherein, I is the reference current of the double active bridge converter.
3. The dual-active-bridge four-degree-of-freedom optimal modulation control method according to claim 1, wherein the voltage conversion ratio is calculated as follows:
Figure FDA0003614872520000032
wherein, V 1 Is the input voltage, V, of a dual active bridge converter 2 The voltage is the output voltage of the double-active-bridge converter, and n is the transformation ratio of the transformer.
4. The dual-active-bridge four-degree-of-freedom optimal modulation control method according to claim 1, wherein the optimal solution of the first modulation mode is specifically as follows:
Figure FDA0003614872520000033
the optimal solution of the second modulation mode is specifically as follows:
Figure FDA0003614872520000041
wherein D is 1,op Is D 1 Optimal solution in the corresponding modulation mode, D 2,op Is D 2 Optimal solution in the corresponding modulation mode, D 3,op Is D 3 Optimal solution in the corresponding modulation mode, D 4,op Is D 4 Optimisation under corresponding modulation modesSolution of P c Is the critical power point.
5. The dual-active-bridge four-degree-of-freedom optimal modulation control method according to claim 4, wherein the calculation formula of the critical power point is specifically as follows:
P c ＝-2M 3 +2M 2
wherein, P c Is the critical power point of the dual active bridge converter.
6. The dual-active-bridge four-degree-of-freedom optimal modulation control method according to claim 4, wherein the calculation formula of the global optimal solution is as follows:
Figure FDA0003614872520000051
Figure FDA0003614872520000052
wherein D is 1,op1 Is D 1 Global optimal solution of, D 2,op2 Is D 2 Global optimal solution of, D 3,op3 Is D 3 Global optimal solution of, D 4,op4 Is D 4 The global optimum solution of (2).
CN202110717411.2A 2021-06-28 2021-06-28 Double-active-bridge four-degree-of-freedom optimal modulation control method Active CN113346758B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN202110717411.2A CN113346758B (en) 2021-06-28 2021-06-28 Double-active-bridge four-degree-of-freedom optimal modulation control method

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202110717411.2A CN113346758B (en) 2021-06-28 2021-06-28 Double-active-bridge four-degree-of-freedom optimal modulation control method

Publications (2)

Publication Number Publication Date
CN113346758A CN113346758A (en) 2021-09-03
CN113346758B true CN113346758B (en) 2022-08-16

Family

ID=77479090

Family Applications (1)

Application Number Title Priority Date Filing Date
CN202110717411.2A Active CN113346758B (en) 2021-06-28 2021-06-28 Double-active-bridge four-degree-of-freedom optimal modulation control method

Country Status (1)

Country Link
CN (1) CN113346758B (en)

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115149818B (en) * 2022-07-27 2024-05-03 山东大学 Current-free bias magnetic quick start control method and system based on expansion phase shift modulation
CN115498892B (en) * 2022-11-14 2023-02-28 西南交通大学 Single-side expansion asymmetric phase-shift modulation method and circuit of double active bridges
CN115498893B (en) * 2022-11-17 2023-02-28 西南交通大学 Symmetric-asymmetric phase shift modulation method and circuit of double-active-bridge converter

Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN112910271A (en) * 2021-04-12 2021-06-04 中国矿业大学 Expanded phase-shift controlled double-active-bridge converter current stress optimization control method

Family Cites Families (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN109742968B (en) * 2019-01-31 2020-12-04 上海交通大学 Diode clamping hybrid three-level double-active full-bridge converter and control method thereof
CN112054693B (en) * 2020-09-14 2022-03-08 重庆大学 Double-active-bridge asymmetric duty ratio optimization modulation method
CN112910264B (en) * 2021-01-25 2022-03-11 深圳市斯康达电子有限公司 Five-degree-of-freedom modulation method of double-active bridge type DC-DC converter

Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN112910271A (en) * 2021-04-12 2021-06-04 中国矿业大学 Expanded phase-shift controlled double-active-bridge converter current stress optimization control method

Also Published As

Publication number Publication date
CN113346758A (en) 2021-09-03

Similar Documents

Publication Publication Date Title
CN113346758B (en) Double-active-bridge four-degree-of-freedom optimal modulation control method
CN113364300B (en) Dual-active-bridge asymmetric-symmetric duty ratio hybrid optimization modulation control method
US10673343B1 (en) Diode clamp mixed three-level dual active full-bridge converter and control method thereof
CN110138225B (en) Control method for current source type double-transformer bidirectional DC-DC converter
CN108039822A (en) A kind of transient current control method of double active full-bridge direct current converters
CN108880268B (en) Multi-mode control method of voltage source type semi-active bridge DC-DC converter
CN106655781A (en) LCC resonant converter PWM phase shift mixed control and efficiency optimization method
CN112202322B (en) Method for inhibiting secondary ripple current based on equivalent zero impedance of active negative capacitor
CN113507214B (en) Three-active-bridge converter power decoupling phase-shifting control and current effective value optimization method
CN104242664A (en) Modulation method of three-phase isolation type bidirectional direct-current converter under double PWM (pulse width modulation)
CN114825968A (en) Asymmetric duty ratio and internal phase shift hybrid control method
CN106787757A (en) A kind of CLTCL resonance DCs converter
CN112910271A (en) Expanded phase-shift controlled double-active-bridge converter current stress optimization control method
CN111064371B (en) Mixed five-level bidirectional DC/DC converter and voltage matching modulation method thereof
CN114884318A (en) Control method of bidirectional buck-boost direct current converter based on duty ratio compensation
CN112311222A (en) Improved bridgeless DBPFC converter based on composite prediction current control and control method
CN110611444B (en) Bridgeless integrated AC-DC (alternating current-direct current) rectifying circuit and rectifying method
CN115549485A (en) Modular direct-current transformer topology and control method thereof
CN109921650B (en) Bidirectional full-bridge unilateral three-level DC-DC converter optimization control method
CN112953245B (en) Double-active bridge converter full-load range soft switch control method
CN105226986A (en) A kind of inverter and control method thereof eliminating the pulsation of input side secondary power
CN109980941A (en) The switch control unit and converter of the dcdc converter of LCC resonance
CN116667638B (en) Linear-nonlinear peak current control strategy based on ZVS four-switch Buck-Boost circuit
CN115955122B (en) Reflux-free modulation method and system for double-bridge series resonant converter
CN112685951B (en) Energy consumption optimization method for double-active half-bridge direct current converter

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant