CN113300110B - Quasi-coaxial crack feed back cavity antenna - Google Patents
Quasi-coaxial crack feed back cavity antenna Download PDFInfo
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- CN113300110B CN113300110B CN202110447821.XA CN202110447821A CN113300110B CN 113300110 B CN113300110 B CN 113300110B CN 202110447821 A CN202110447821 A CN 202110447821A CN 113300110 B CN113300110 B CN 113300110B
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
- H01Q13/10—Resonant slot antennas
- H01Q13/18—Resonant slot antennas the slot being backed by, or formed in boundary wall of, a resonant cavity ; Open cavity antennas
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/12—Supports; Mounting means
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/42—Housings not intimately mechanically associated with radiating elements, e.g. radome
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
- H01Q15/14—Reflecting surfaces; Equivalent structures
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
- H01Q5/10—Resonant antennas
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
- H01Q5/20—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements characterised by the operating wavebands
- H01Q5/28—Arrangements for establishing polarisation or beam width over two or more different wavebands
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
- H01Q5/30—Arrangements for providing operation on different wavebands
- H01Q5/307—Individual or coupled radiating elements, each element being fed in an unspecified way
- H01Q5/314—Individual or coupled radiating elements, each element being fed in an unspecified way using frequency dependent circuits or components, e.g. trap circuits or capacitors
- H01Q5/335—Individual or coupled radiating elements, each element being fed in an unspecified way using frequency dependent circuits or components, e.g. trap circuits or capacitors at the feed, e.g. for impedance matching
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
- H01Q5/50—Feeding or matching arrangements for broad-band or multi-band operation
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Abstract
The invention relates to the field of cavity backed antennas, and discloses a quasi-coaxial crack feed cavity backed antenna which comprises a step structure type symmetrical vibrator, an impedance converter, a dielectric antenna housing, a quasi-coaxial crack balancer, a foam layer and a circular reflection cavity; the medium antenna housing is assembled on the circular reflection cavity, the symmetrical vibrators are assembled on the quasi-coaxial crack balancer, and the foam layer is arranged between the step structure type symmetrical vibrators and the medium antenna housing and used for fixing the relative distance between the symmetrical vibrators and the medium antenna housing. The back cavity antenna provided by the invention adopts a quasi-coaxial crack balanced feed structure, combines the advantages of the traditional coaxial crack balanced feed and the double-line balanced feed, integrates impedance transformation and the coaxial crack structure, and achieves the purposes of eliminating directional diagram distortion, structural reliability under the high-strength condition, power capacity improvement and bandwidth not less than 3 in the current popular broadband back cavity antenna form: 1, in the step (b).
Description
Technical Field
The invention relates to the field of cavity-backed antennas, in particular to a quasi-coaxial slot feed cavity-backed antenna.
Background
The cavity-backed antenna excited by the oscillator mainly adopts several forms such as a symmetrical oscillator, a bowtie oscillator and an open sleeve dipole, and the typical feed mode is double-line balanced feed.
The radiation pattern of the broadband cavity-backed antenna excited by the bowtie oscillator is easy to distort at the high end of the frequency; the cavity-backed antenna excited by the open sleeve oscillator has a complex structure and is easy to damage under the high-strength vibration condition. The traditional dipole excited cavity-backed antenna has the greatest advantages of simple structure and low cross polarization level, and has the defects of limited self bandwidth, and the bandwidth of the standing wave coefficient is usually 1.5: within 1.
Meanwhile, the directional diagram distortion is easy to occur at the high-frequency end. The existing double-wire balancer has a simple structure and a wide bandwidth, but is limited by a cross-wire connection structure (equivalent distributed inductance) between the anode and the cathode of the oscillator, so that the high-frequency performance (small directional diagram distortion and power capacity) of the antenna is limited.
Disclosure of Invention
The technical problem to be solved by the invention is as follows: aiming at the existing problems, the quasi-coaxial slot feed back cavity antenna is provided, and is used for eliminating the directional diagram distortion, the structural reliability under the high-intensity condition, the power capacity improvement (the C wave band is not less than 1000W) and the frequency bandwidth width which are existed in the current popular broadband back cavity antenna mode and are not less than 3:1, in the event of a failure.
The technical scheme adopted by the invention is as follows: a quasi-coaxial crack feed back cavity antenna comprises a symmetrical oscillator, a dielectric antenna housing, a quasi-coaxial crack balancer and a reflection back cavity; the dielectric radome is assembled on the reflection back cavity, the symmetrical oscillator is assembled on the quasi-coaxial crack balancer, an impedance converter is assembled in a crack of the quasi-coaxial crack balancer, and the impedance converter is connected to the symmetrical oscillator.
Wherein the dipole is a ladder-structured dipole; when the high-frequency working is carried out, the distance between the lower surface of the symmetrical oscillator and the bottom surface of the reflection cavity is less than 0.35 wavelength, the wavelength is the wavelength of a high-end wave band of a resonant frequency, the length of the symmetrical oscillator is 0.25-0.3 wavelength, and the wavelength is the wavelength of a low-end wave band of the resonant frequency, so that the problem of cracking distortion caused by reverse superposition of a high-frequency directional diagram is solved, and the bandwidth of the directional diagram is ensured to reach 3:1 or more.
The impedance transformer improves the traditional quarter-wavelength stepped impedance transformer, and specifically comprises the following steps: the equivalent characteristic impedance of the impedance converter is 25-30 omega; high-impedance stubs are connected in series at positions 1/4 to 1/2 of an impedance conversion section of the impedance converter, and low-impedance stubs are connected in series at the ends of the impedance converter. Therefore, the method can be equivalent to loading of distributed inductance/distributed capacitance, impedance change positions are equivalent to hopping capacitance, the problem of bandwidth limitation of single-stage impedance transformation is solved, and the impedance transformation bandwidth is guaranteed to reach 3: 1.
the dielectric radome is a low-loss dielectric with a dielectric constant of 3.0-3.5, the thickness of the dielectric radome is selected from a range of 0.005-0.025 wavelength, the wavelength is the wavelength of the high-end waveband of the resonant frequency, the distance between the dielectric radome and the symmetrical vibrator is selected from a range of 0.005-0.025 wavelength, and the wavelength is the wavelength of the high-end waveband of the resonant frequency; the dielectric antenna housing has a loading function, the radiation impedance of the antenna is gentle along with the frequency change due to the loading function of the dielectric antenna housing, and the in-band standing wave characteristic of the antenna is improved.
The quasi-coaxial crack balancer adopts a square shell, and the crack width and length of the quasi-coaxial crack balancer are selected to be related to an impedance transformer assembled in the crack of the quasi-coaxial crack balancer; the crack length is selected within the range of 0.25-0.4 wavelength, the wavelength is the wavelength of the high-end wave band of the resonance frequency, and the equivalent impedance of the transmission line formed by the cracks is selected within the range of 75-100 omega.
The reflecting back cavity is a circular reflecting cavity; the diameter of the material is selected from 0.45-0.55 wavelengths, and the wavelength is the wavelength of the low-end waveband of the resonance frequency; the depth of the cavity is selected to be 0.5-0.6 wavelength, the wavelength is the wavelength of the high-end wave band of the resonant frequency, and the in-band standing wave characteristic of the antenna is improved through controlling the depth of the cavity and the diameter of the cavity.
Furthermore, the characteristic impedance of the high-impedance stub is selected from 40-50 omega, the length is selected from 0.001-0.025 wavelength, and the wavelength is the wavelength of the high-end waveband of the resonant frequency.
Furthermore, the characteristic impedance of the low-impedance stub is selected from 20-25 omega, the length is selected from the range of 0.001-0.025 wavelength, and the wavelength is the wavelength of the high-end waveband of the resonant frequency.
Furthermore, a foam layer used for supporting is arranged between the dielectric radome and the stepped structure type symmetrical vibrator, and the foam layer is made of PMI materials with a self-closed structure, so that the relative distance between the radome and the vibrator is fixed, and the problem of standing wave coefficient deterioration caused by overlarge relative position change is avoided.
Compared with the prior art, the beneficial effects of adopting the technical scheme are as follows:
1. dipole (ladder structure): the problem of cracking distortion of a high-frequency directional diagram due to reverse phase superposition is solved, and the bandwidth of the directional diagram is ensured to reach 3:1 or more;
2. impedance transformers increase the high/low impedance stub transmission line: the equivalent is distributed inductance/distributed capacitance loading, the impedance change part is equivalent to a jump capacitance, the problem of bandwidth limitation of single-stage impedance transformation is solved, and the impedance transformation bandwidth is ensured to reach 3: 1;
3. dielectric radome (loading): the loading effect of the dielectric antenna housing enables the radiation impedance of the antenna to smoothly change along with the frequency, and improves the in-band standing wave characteristic of the antenna;
4. foam supporting: the PMI material with a self-sealing (closed pore structure) is selected, so that the relative distance between the antenna housing and the vibrator is ensured to be fixed, and the problem of standing wave coefficient deterioration caused by overlarge relative position change is avoided;
5. and (3) fusing quasi-coaxial crack balanced feed and impedance transformation: the antenna feed structure is simple;
6. a reflective back cavity: the in-band standing wave characteristic of the antenna is improved by controlling the depth and the diameter of the cavity.
Drawings
Fig. 1 is a H-plane cross-sectional view (along the direction of the symmetric array) of a quasi-coaxial slot fed cavity-backed antenna provided by the present invention.
Fig. 2 is a top sectional view of a quasi-coaxial slot fed cavity-backed antenna provided by the present invention (with the radome and foam layers removed).
Fig. 3 is a partial cross-sectional view (along one side of the dipole) of the H-plane of a quasi-coaxial slot fed cavity-backed antenna provided by the present invention.
Fig. 4 shows an example of the standing wave coefficients (F2/F1: 3:1) of the quasi-coaxial slot-fed cavity-backed antenna provided by the present invention.
Fig. 5 is an example of the radiation pattern (F1, 0 °/45 °/90 ° cross section) of a quasi-coaxial slot fed cavity-backed antenna provided by the present invention.
Fig. 6 is an example of the radiation pattern (F0, 0 °/45 °/90 ° cross section) of a quasi-coaxial slot fed cavity-backed antenna provided by the present invention.
Fig. 7 is an example of the radiation pattern (F2, 0 °/45 °/90 ° cross section) of a quasi-coaxial slot fed cavity-backed antenna provided by the present invention.
Reference numerals: the antenna comprises a dielectric antenna housing 1, a circular reflection cavity 2, a step structure type symmetrical vibrator 3, a quasi-coaxial crack balancer 4, an impedance transformer 5, a high-impedance stub 6, a low-impedance stub 7, a foam layer 8, an inner conductor short-circuit point 9 and an outer conductor short-circuit point 10.
Detailed Description
In order to make the objects, technical solutions and advantages of the embodiments of the present invention clearer, the technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are some, but not all, embodiments of the present invention. The components of embodiments of the present invention generally described and illustrated in the figures herein may be arranged and designed in a wide variety of different configurations.
Thus, the following detailed description of the embodiments of the present invention, presented in the figures, is not intended to limit the scope of the invention, as claimed, but is merely representative of selected embodiments of the invention. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
It should be noted that the embodiments and features of the embodiments may be combined with each other without conflict.
It should be noted that: like reference numbers and letters refer to like items in the following figures, and thus, once an item is defined in one figure, it need not be further defined and explained in subsequent figures.
In the description of the embodiments of the present invention, it should be noted that the indication of the orientation or the positional relationship is based on the orientation or the positional relationship shown in the drawings, or the orientation or the positional relationship which is usually placed when the product of the present invention is used, or the orientation or the positional relationship which is usually understood by those skilled in the art, or the orientation or the positional relationship which is usually placed when the product of the present invention is used, and is only for the convenience of describing the present invention and simplifying the description, but does not indicate or imply that the indicated device or element must have a specific orientation, be constructed in a specific orientation, and be operated, and therefore, cannot be understood as limiting the present invention. Furthermore, the terms "first" and "second" are used merely to distinguish one description from another, and are not to be construed as indicating or implying relative importance.
In the description of the embodiments of the present invention, it should be further noted that the terms "disposed" and "connected" are to be interpreted broadly, and may be, for example, fixedly connected, detachably connected, or integrally connected, unless explicitly stated or limited otherwise; may be directly connected or indirectly connected through an intermediate. The specific meanings of the above terms in the present invention can be understood in specific cases by those skilled in the art; the drawings in the embodiments are used for clearly and completely describing the technical scheme in the embodiments of the invention, and obviously, the described embodiments are a part of the embodiments of the invention, but not all of the embodiments. The components of embodiments of the present invention generally described and illustrated in the figures herein may be arranged and designed in a wide variety of different configurations.
The invention is further described below with reference to the accompanying drawings.
Example 1
The embodiment specifically provides a quasi-coaxial slot feed cavity backed antenna, and compared with the existing cavity backed antenna, the improvement is that the working bandwidth of the oscillator excitation cavity backed antenna is expanded through the combination of the quasi-coaxial slot balanced feed and the dielectric loading technology. The whole structure of the antenna is shown in fig. 1, and the antenna comprises a symmetrical oscillator, an impedance converter, a dielectric antenna cover, a quasi-coaxial crack balancer, a foam layer and a reflecting back cavity; the medium antenna house assembly is in on the reflection back of the body chamber, the dipole is installed on accurate coaxial crack equalizer, impedance converter assembly is in the crack of accurate coaxial crack equalizer, just impedance converter still connects on the dipole, and the foam layer that shows sets up between dipole and medium antenna house for the relative distance between fixed dipole and the medium antenna house.
In this embodiment, as shown in fig. 1, the dipoles are ladder dipoles; when high frequency work, the distance between ladder structural formula symmetry oscillator lower surface and the reflection cavity bottom surface is less than 0.35 wavelength, and this wavelength is the wavelength of resonant frequency high end wave band, and 0.25 wavelength is got to ladder structural formula symmetry oscillator's length, and this wavelength is the wavelength of resonant frequency low end wave band to solve high frequency directional diagram and because of reverse stack fracture distortion problem appears, guarantee directional diagram bandwidth reaches 3:1 or more.
In this embodiment, the impedance transformer is an improvement of a conventional quarter-wavelength stepped impedance transformer, and the specific design parameters are as follows: the equivalent characteristic impedance of the impedance converter is 25 omega; as shown in fig. 1, a high impedance stub is connected in series at 1/4 of the impedance conversion section of the impedance converter, and a low impedance stub is connected in series at the end of the impedance converter. Therefore, the method can be equivalent to loading of distributed inductance/distributed capacitance, impedance change positions are equivalent to hopping capacitance, the problem of bandwidth limitation of single-stage impedance transformation is solved, and the impedance transformation bandwidth is guaranteed to reach 3: 1.
the characteristic impedance of the high-impedance stub is 40 omega, the length of the high-impedance stub is 0.001 wavelength, and the wavelength is the wavelength of a high-end waveband of the resonant frequency.
The characteristic impedance of the low-impedance stub is 20 Ω, and the length is 0.001 wavelength, which is the wavelength of the high-end band of the resonance frequency.
In this embodiment, the dielectric radome is a low-loss dielectric with a dielectric constant of 3.0, the thickness of the dielectric radome is 0.005 wavelength, the wavelength is the wavelength of the high-end band of the resonant frequency, and the distance between the dielectric radome and the stepped structure type symmetrical oscillator is 0.005 wavelength, the wavelength is the wavelength of the high-end band of the resonant frequency; the dielectric antenna housing has a loading function, the radiation impedance of the antenna is gentle along with the frequency change due to the loading function of the dielectric antenna housing, and the in-band standing wave characteristic of the antenna is improved.
In the present embodiment, as shown in fig. 2, the reflective back cavity is a circular reflective cavity; the diameter of the resonant cavity is 0.45 wavelength which is the wavelength of the lower end wave band of the resonant frequency; the depth of the cavity is 0.5 wavelength which is the wavelength of the high-end wave band of the resonant frequency, and the in-band standing wave characteristic of the antenna is improved by controlling the depth of the cavity and the diameter of the cavity.
In the present embodiment, as shown in fig. 3, the quasi-coaxial crack balancer uses a square housing, and the crack width and length are selected to be related to the characteristic impedance of the short-circuit transmission line formed by the crack; the length of the crack is 0.25 wavelength which is the wavelength of the high-end wave band of the resonance frequency, and the equivalent impedance of the transmission line formed by the crack is 75 omega.
The working principle of the cavity-backed antenna provided by the embodiment in operation is as follows:
the electromagnetic signal passes through the transmission line adapter plate and excites oscillation current on the step structure type symmetrical vibrator through the embedded impedance balancer. One part of microwave signals are directly radiated to the external space, the other part of energy is radiated to the external space after being reflected by the back cavity, and the two parts of electromagnetic signals are subjected to vector synthesis in the external space.
By adopting the S/C frequency band cavity-backed antenna provided by the embodiment, the standing wave coefficient bandwidth (the standing wave coefficient is better than 2.5) reaches 3:1 or more. In the following 3:1, the radiation pattern is symmetrical within the working bandwidth. Typical performance is shown in fig. 4-7.
Example 2
The quasi-coaxial split feed back cavity antenna provided by the embodiment has the same design idea and working principle as those of the embodiment 1, and is different only in specific parameters, and comprises a symmetrical oscillator, an impedance converter, a dielectric radome, a quasi-coaxial split balancer, a foam layer and a reflection back cavity; the medium antenna house assembly is in on the reflection back of the body chamber, the dipole is installed on accurate coaxial crack equalizer, impedance converter assembly is in the crack of accurate coaxial crack equalizer, just impedance converter still connects on the dipole, and the foam layer that shows sets up between dipole and medium antenna house for the relative distance between fixed dipole and the medium antenna house.
In this embodiment, as shown in fig. 1, the dipoles are ladder dipoles; when high frequency work, the distance between ladder structural formula symmetry oscillator lower surface and the reflection cavity bottom surface is less than 0.35 wavelength, and this wavelength is the wavelength of resonant frequency high end wave band, and 0.27 wavelength is got to ladder structural formula symmetry oscillator's length, and this wavelength is the wavelength of resonant frequency low end wave band to solve high frequency directional diagram and because of reverse stack fracture distortion problem appears, guarantee directional diagram bandwidth reaches 3:1 or more.
In this embodiment, the impedance transformer is an improvement of a conventional quarter-wavelength stepped impedance transformer, and the specific design parameters are as follows: the equivalent characteristic impedance of the impedance converter is 27 omega; as shown in fig. 1, a high-impedance stub is connected in series at the position of the impedance conversion section 1/3 of the impedance converter, and a low-impedance stub is connected in series at the end of the impedance converter. Therefore, the method can be equivalent to loading of distributed inductance/distributed capacitance, impedance change positions are equivalent to hopping capacitance, the problem of bandwidth limitation of single-stage impedance transformation is solved, and the impedance transformation bandwidth is guaranteed to reach 3: 1.
wherein, the characteristic impedance of the high impedance stub is selected to be 45 omega, the length is selected to be 0.015 wavelength, and the wavelength is the wavelength of the high-end wave band of the resonance frequency.
The characteristic impedance of the low-impedance stub is 22 Ω, and the length is 0.015 wavelength, which is the wavelength of the high-end band of the resonance frequency.
In this embodiment, the dielectric radome is a low-loss dielectric with a dielectric constant of 3.3, the thickness of the dielectric radome is 0.015 wavelength, the wavelength is the wavelength of the high-end waveband of the resonant frequency, and the distance between the dielectric radome and the stepped structure type symmetrical vibrator is 0.015 wavelength, the wavelength is the wavelength of the high-end waveband of the resonant frequency; the dielectric antenna housing has a loading function, the radiation impedance of the antenna is gentle along with the frequency change due to the loading function of the dielectric antenna housing, and the in-band standing wave characteristic of the antenna is improved.
In the present embodiment, as shown in fig. 2, the reflective back cavity is a circular reflective cavity; the diameter of the resonant cavity is 0.5 wavelength which is the wavelength of the low-end wave band of the resonant frequency; the depth of the cavity is selected to be 0.55 wavelength which is the wavelength of the high-end wave band of the resonant frequency, and the in-band standing wave characteristic of the antenna is improved by controlling the depth of the cavity and the diameter of the cavity.
In the present embodiment, as shown in fig. 3, the quasi-coaxial crack balancer uses a square housing, and the crack width and length are selected to be related to the characteristic impedance of the short-circuit transmission line formed by the crack; the length of the crack is 0.3 wavelength which is the wavelength of the high-end wave band of the resonance frequency, and the equivalent impedance of the transmission line formed by the crack is 85 omega.
Example 3
The quasi-coaxial split feed back cavity antenna provided by the embodiment has the same design idea and working principle as those of the embodiment 1, and is different only in specific parameters, and comprises a symmetrical oscillator, an impedance converter, a dielectric radome, a quasi-coaxial split balancer, a foam layer and a reflection back cavity; the medium antenna house assembly is in on the reflection back of the body chamber, the dipole is installed on accurate coaxial crack equalizer, impedance converter assembly is in the crack of accurate coaxial crack equalizer, just impedance converter still connects on the dipole, and the foam layer that shows sets up between dipole and medium antenna house for the relative distance between fixed dipole and the medium antenna house.
In this embodiment, as shown in fig. 1, the dipoles are ladder dipoles; when high frequency work, the distance between ladder structural formula symmetry oscillator lower surface and the reflection cavity bottom surface is less than 0.35 wavelength, and this wavelength is the wavelength of resonant frequency high end wave band, and 0.3 wavelength is got to ladder structural formula symmetry oscillator's length, and this wavelength is the wavelength of resonant frequency low end wave band to solve the high frequency directional diagram and because of reverse stack fracture distortion problem that appears, guarantee directional diagram bandwidth reaches 3:1 or more.
In this embodiment, the impedance transformer is an improvement of a conventional quarter-wavelength stepped impedance transformer, and the specific design parameters are as follows: selecting the equivalent characteristic impedance of the impedance converter to be 30 omega; as shown in fig. 1, a high-impedance stub is connected in series at the position of the impedance conversion section 1/2 of the impedance converter, and a low-impedance stub is connected in series at the end of the impedance converter. Therefore, the method can be equivalent to loading of distributed inductance/distributed capacitance, impedance change positions are equivalent to hopping capacitance, the problem of bandwidth limitation of single-stage impedance transformation is solved, and the impedance transformation bandwidth is guaranteed to reach 3: 1.
wherein, the characteristic impedance of the high impedance stub is selected to be 50 Ω, and the length is selected to be 0.025 wavelength, which is the wavelength of the high-end waveband of the resonance frequency.
The characteristic impedance of the low impedance stub is 25 Ω, and the length is 0.025 wavelength, which is the wavelength of the high end band of the resonance frequency.
In this embodiment, the dielectric radome is a low-loss dielectric with a dielectric constant of 3.5, the thickness of the dielectric radome is 0.025 wavelength, the wavelength is the wavelength of the high-end band of the resonant frequency, and the distance between the dielectric radome and the stepped structure type symmetrical oscillator is 0.025 wavelength, the wavelength is the wavelength of the high-end band of the resonant frequency; the dielectric antenna housing has a loading function, the radiation impedance of the antenna is gentle along with the frequency change due to the loading function of the dielectric antenna housing, and the in-band standing wave characteristic of the antenna is improved.
In the present embodiment, as shown in fig. 2, the reflective back cavity is a circular reflective cavity; the diameter of the resonant cavity is 0.55 wavelength which is the wavelength of the lower end wave band of the resonant frequency; the depth of the cavity is selected to be 0.6 wavelength which is the wavelength of the high-end wave band of the resonant frequency, and the in-band standing wave characteristic of the antenna is improved by controlling the depth of the cavity and the diameter of the cavity.
In the present embodiment, as shown in fig. 3, the quasi-coaxial crack balancer uses a square housing, and the crack width and length are selected to be related to the characteristic impedance of the short-circuit transmission line formed by the crack; the length of the crack is 0.4 wavelength, the wavelength is the wavelength of the high-end wave band of the resonance frequency, and the equivalent impedance of the transmission line formed by the crack is 100 omega.
The invention is not limited to the foregoing embodiments. The invention extends to any novel feature or any novel combination of features disclosed in this specification and any novel method or process steps or any novel combination of features disclosed. Those skilled in the art to which the invention pertains will appreciate that insubstantial changes or modifications can be made without departing from the spirit of the invention as defined by the appended claims.
Claims (10)
1. The utility model provides a quasi-coaxial crack feed cavity backed antenna which characterized in that: the antenna comprises a symmetrical oscillator, a quasi-coaxial crack balancer, a dielectric antenna housing and a reflecting back cavity, wherein the dielectric antenna housing is assembled on the reflecting back cavity, and the symmetrical oscillator is assembled on the quasi-coaxial crack balancer; an impedance converter is assembled in the crack of the quasi-coaxial crack balancer; the impedance converter is connected to the dipole; the symmetrical vibrators adopt a stepped structure type, and the stepped structure is arranged along the thickness direction of the symmetrical vibrators; high-impedance stubs are connected in series at the positions 1/4 to 1/2 of the impedance transformation section of the impedance transformer, and low-impedance stubs are connected in series at the ends of the impedance transformer; the quasi-coaxial crack balancer adopts a square shell; the reflecting back cavity adopts a circular reflecting cavity.
2. The cavity-backed quasi-coaxial split-feed antenna as claimed in claim 1, wherein the high-impedance stub has a characteristic impedance of 40-50 Ω and a length of 0.001-0.025 wavelength, which is a wavelength in the high-end band of the resonant frequency.
3. The cavity-backed quasi-coaxial slot feed antenna of claim 1, wherein the characteristic impedance of the low impedance stub is selected to be 20-25 Ω, and the length is selected to be in the range of 0.001-0.025 wavelength, which is the wavelength in the high end band of the resonant frequency.
4. The cavity-backed quasi-coaxial split-feed antenna as claimed in claim 1, wherein the distance between the bottom surface of said stepped dipole and the bottom surface of said circular cavity is less than 0.35 wavelength, which is the wavelength of the high end band of the resonant frequency, when said antenna is operated at high frequency.
5. The cavity-backed quasi-coaxial slot feed antenna as claimed in claim 1, wherein the length of said ladder dipole is 0.25-0.3 wavelength, which is the wavelength of the lower band of the resonant frequency.
6. The quasi-coaxial slot fed cavity-backed antenna of claim 1, wherein the slot length of the quasi-coaxial slot balancer is selected from a range of 0.25-0.4 wavelengths, which is the wavelength of the high-end band of the resonant frequency, and the transmission line equivalent impedance formed by the slot is selected from a range of 75-100 Ω.
7. The cavity-backed quasi-coaxial slot feed antenna of claim 1, wherein the diameter of said circular reflective cavity is selected from the range of 0.45-0.55 wavelength, and the wavelength is the wavelength of the lower band of the resonant frequency; the depth of the cavity of the circular reflecting cavity is selected from a range of 0.5-0.6 wavelength, and the wavelength is the wavelength of a high-end waveband of the resonant frequency.
8. The quasi-coaxial slot feed cavity-backed antenna according to claim 1, wherein a foam layer for supporting is installed between the dielectric radome and the ladder structure type dipole, and the foam layer is made of a PMI material with a self-closed structure.
9. The quasi-coaxial slot fed cavity-backed antenna of claim 1, wherein the distance between the dielectric radome and the dipole is selected from the range of 0.005-0.025 wavelengths, which is the wavelength of the high end band of the resonant frequency.
10. The quasi-coaxial slot fed cavity-backed antenna of claim 1, wherein the dielectric radome has a thickness selected over the range of 0.005-0.025 wavelength, which is the wavelength of the upper band of the resonant frequency.
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202110447821.XA CN113300110B (en) | 2021-04-25 | 2021-04-25 | Quasi-coaxial crack feed back cavity antenna |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
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