CN113098365A - Method and system for suppressing network side current harmonic of motor driving system without electrolytic capacitor - Google Patents

Method and system for suppressing network side current harmonic of motor driving system without electrolytic capacitor Download PDF

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CN113098365A
CN113098365A CN202110322288.4A CN202110322288A CN113098365A CN 113098365 A CN113098365 A CN 113098365A CN 202110322288 A CN202110322288 A CN 202110322288A CN 113098365 A CN113098365 A CN 113098365A
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inverter
voltage
input power
power
network side
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CN113098365B (en
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丁文
刘兆国
李阳阳
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Xian Jiaotong University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P29/00—Arrangements for regulating or controlling electric motors, appropriate for both AC and DC motors
    • H02P29/50—Reduction of harmonics
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/0003—Control strategies in general, e.g. linear type, e.g. P, PI, PID, using robust control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/022—Synchronous motors
    • H02P25/024—Synchronous motors controlled by supply frequency
    • H02P25/026—Synchronous motors controlled by supply frequency thereby detecting the rotor position
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P2207/00—Indexing scheme relating to controlling arrangements characterised by the type of motor
    • H02P2207/05—Synchronous machines, e.g. with permanent magnets or DC excitation
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E40/00—Technologies for an efficient electrical power generation, transmission or distribution
    • Y02E40/40—Arrangements for reducing harmonics

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  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)

Abstract

A method and a system for suppressing network side current harmonic waves of a motor driving system without electrolytic capacitors belong to the field of variable frequency driving. Comprises the following steps: processing the network side current signal, extracting a network side current harmonic component, and generating an inverter input power waveform correction quantity after 0 and the current harmonic component are subjected to difference adjustment and absolute value conversion through a PI (proportional integral) regulator; II, secondly: obtaining phase information of network side voltage through a phase-locked loop, processing to obtain an initial amount of an inverter input power waveform with a frequency doubled to a voltage waveform of a power grid, and obtaining an actual amount of the inverter input power waveform after the initial amount of the inverter input power waveform is differed from the correction amount of the inverter input power waveform in the first step; thirdly, the method comprises the following steps: the rotating speed ring is regulated and output by the PI regulator and then multiplied by the actual power waveform quantity in the step two to obtain the given power quantity of the inverter; fourthly, the method comprises the following steps: the given quantity of the inverter power and the feedback quantity of the inverter power are subjected to difference adjustment through a PR regulator to obtain the given quantity of the q-axis current; fifthly: the remaining control method is the same as the conventional motor vector control method.

Description

Method and system for suppressing network side current harmonic of motor driving system without electrolytic capacitor
Technical Field
The invention belongs to the field of variable frequency driving, and particularly relates to a method and a system for suppressing network side current harmonic waves of a motor driving system without electrolytic capacitors.
Background
With the increasing prominence of energy and environmental problems, the variable frequency driving scheme of single-phase alternating current input has great advantages in energy saving, and is widely applied to household appliances such as air conditioners, refrigerators, washing machines and the like. The permanent magnet synchronous motor has the characteristics of higher efficiency, simple structure, large overload capacity, small rotational inertia, small torque pulsation and the like, and is very suitable for a driving system of household appliances.
In a conventional permanent magnet synchronous motor driving system, a large-capacity electrolytic capacitor is generally used to maintain a constant bus voltage, and a Power Factor Correction (PFC) circuit is introduced to adjust a grid-side power factor. However, the electrolytic capacitor is greatly affected by temperature, and is easily damaged in severe environment and environment with large temperature change, so that the whole motor driving system is in failure. In order to solve the problem, a thin film capacitor with small volume, long service life and small capacitance value can be used for replacing an electrolytic capacitor with large volume, short service life and large capacitance value, so that the service life of the whole driving system is prolonged. Because the direct current bus capacitor plays the effect of stabilizing the bus voltage and reducing the voltage ripple, when the capacitance value of the bus capacitor is reduced, the stored energy at the direct current side is reduced, so that the fluctuation amount of the bus voltage is increased, the conduction angle of the rectifying circuit is increased, the input power factor of the system is increased, a power factor correction circuit can be omitted, the cost is saved, and the size of a driving system is reduced.
However, the bus capacitance is small, so that the voltage fluctuation of the bus is large, and the removal of a Power Factor Correction (PFC) circuit also causes an LC resonance phenomenon between a filter reactor on the grid side and a dc bus capacitance, which all causes a large harmonic of the input current on the grid side, a low power factor, and pollution to the current of the power grid.
At present, a method for improving the power factor of a driving system of a non-electrolytic capacitor permanent magnet synchronous motor mainly adopts an inverter power control strategy, but the control strategy is not obvious in improving the network side power factor of the driving system of a low-power motor, and the network side current harmonic is still larger.
Disclosure of Invention
The invention aims to provide a method and a system for suppressing network side current harmonics of a motor driving system without electrolytic capacitors, so as to solve the problems.
In order to achieve the purpose, the invention adopts the following technical scheme:
a method for suppressing network side current harmonics of a motor driving system without electrolytic capacitors comprises the following steps:
step 1: performing PI regulation on the difference value between the given rotating speed and the feedback rotating speed of the motor to generate a power constant
Figure BDA0002993269260000024
Step 2: to the real-time voltage u of the power gridgPhase locking is carried out to obtain the grid voltage phase angle information, and the grid voltage phase angle information is processed to obtain the initial waveform quantity k of the input power of the inverter*(t)；
And step 3: collecting a network side input current signal, extracting a network side current harmonic component, carrying out PI regulation on a difference value between a numerical value 0 and the network side current harmonic component, and carrying out absolute value conversion on the output quantity of a PI regulator to obtain an inverter input power waveform correction quantity t*(t), initial value k of inverter input power waveform in step 2*(t) correction of inverter input power waveform*(t) obtaining the actual waveform quantity k (t) of the input power of the inverter after difference;
step 4, according to the power constant in the step 1
Figure BDA0002993269260000021
And calculating the given power p of the inverter by using the actual value k (t) of the waveform of the input power of the inverterinv *Inverter power given pinv *And inverter power feedback pinvThe error between is controlled by a proportional resonant controller PR, the output of which is a given q-axis current command iq *Given d-axis current command id *Is 0;
and 5: according to d and q axis current commands id *、iq *Collecting real-time d and q axis current id、iqProportional and integral calculation is carried out on the error to obtain d and q axis voltage commands ud、uq. D, q axis voltage command ud、uqAnd motor cross decoupling voltage udf、uqfAdding the voltage values and performing coordinate transformation to obtain a static coordinate system voltage uαf、uβfAccording to the stationary frame voltage uαf、uβfAnd bus voltage udcAnd controlling the inverter and the motor by utilizing space vector modulation.
Further, the initial value k of the input power waveform of the inverter in step 2*The functional expression of (t) is:
Figure BDA0002993269260000022
wherein, ω isgFor the angular frequency of the voltage of the power grid,
Figure BDA0002993269260000023
is the initial phase angle of the network voltage.
Further, in step 3, the functional expression of the actual value k (t) of the inverter input power waveform is:
Figure BDA0002993269260000031
further, the obtaining of the harmonic component of the current on the network side in step 3 specifically includes: dividing the collected network side input current into two paths of signals, keeping the network side input current unchanged by the line 1 signal, carrying out low-pass filtering on the line 2, and subtracting the output signal of the line 2 after low-pass filtering from the output signal of the line 1 to obtain the network side current harmonic component.
Further, the step 4 of calculating the inverter input power error specifically includes: neglecting the power consumed by the thin film capacitor, the power constant in step 1
Figure BDA0002993269260000032
And the waveform of the input power of the inverter in the step 3Multiplying the k (t) value by the given inverter input power pinv *。
Further, in step 4, the inverter input power p is fed back by neglecting the inverter power lossinvThe functional expression of (a) is:
pinv＝1.5*(ud *id+uq *iq) (3)
wherein u isd *、idIs d-axis voltage, d-axis current, where uq *、iqQ-axis voltage, q-axis current.
Further, in step 5, the motor cross-decoupling voltage udf、uqfThe calculation formula of (2) is as follows:
udf＝-Lqiqωe (4)
Figure BDA0002993269260000033
wherein L isd、LqRespectively represent the d-axis inductance and the q-axis inductance of the motor,
Figure BDA0002993269260000034
representing the permanent magnet flux linkage, omegaeRepresenting the electrical angular velocity of the motor.
Further, a no electrolytic capacitor motor drive system net side current harmonic suppression system includes:
constant of power
Figure BDA0002993269260000035
The generation module is used for carrying out PI regulation on the difference value between the given rotating speed and the feedback rotating speed of the motor to generate a power constant
Figure BDA0002993269260000036
Initial value k of input power waveform of inverter*(t) the acquisition module is used for acquiring the real-time voltage u of the power gridgPhase locking is carried out to obtain the phase angle information of the voltage of the power grid,processing the grid voltage phase angle information to obtain the initial waveform quantity k of the inverter input power*(t)；
Inverter input power waveform correction t*(t) the acquisition module is used for acquiring a network side input current signal to obtain a network side current harmonic component, carrying out PI (proportional integral) adjustment on a difference value between the numerical value 0 and the network side current harmonic component, and then carrying out absolute value conversion on the output quantity of the PI adjuster to obtain an inverter input power waveform correction quantity t*(t)；
The inverter input power error obtaining module is used for obtaining the power constant according to the step 1
Figure BDA0002993269260000037
To be multiplied by the actual quantity k (t) of the waveform of the input power of the inverter to obtain the given power p of the input power of the inverterinv *Given inverter input power pinv *And feedback inverter input power pinvIs the inverter input power error, this error is controlled by the proportional resonant controller PR, the output of which is a given q-axis current command iq *. Given d-axis current command id *Is 0;
the inverter and the motor control module are used for commanding current i of d and q axesd *、iq *And collecting real-time d and q axis currents id、iqCarrying out proportional and integral operation on the error to obtain d and q axis voltage commands ud、uq. D, q axis voltage command ud、uqAnd motor cross decoupling voltage udf、uqfAdding the voltage values and performing coordinate transformation to obtain a static coordinate system voltage uαf、uβfAccording to the stationary frame voltage uαf、uβfAnd bus voltage udcAnd controlling the inverter and the motor by utilizing space vector modulation.
Compared with the prior art, the invention has the following technical effects:
the method is improved on the basis of the traditional inverter input power control strategy of the electrolytic capacitor-free permanent magnet synchronous motor, a network side current harmonic suppression control strategy is added to the traditional inverter input power control strategy, an inverter input power waveform correction component is generated through the network side current harmonic suppression control strategy to correct the inverter input power waveform, and the network side current harmonic component can be directly controlled by adjusting a PI regulator in the network side current harmonic suppression control strategy.
Drawings
FIG. 1 is a block diagram of a driving system of a conventional permanent magnet synchronous motor without an electrolytic capacitor
FIG. 2 is an overall control block diagram of the driving system of the electrolytic capacitor-free permanent magnet synchronous motor of the present invention
Fig. 3 is a waveform diagram of the change of the grid-side current before and after the grid-side current harmonic suppression method is added. In the figure, the network side current waveform adopting the traditional inverter power control strategy is shown before 3s, and the network side current waveform added with the network side current harmonic suppression control strategy is shown after 3 s.
Fig. 4 is a graph of power factor change before and after the grid-side current harmonic suppression method is added. In the figure, the power factor situation before 3s is the power factor situation adopting the power control strategy of the traditional inverter, and the power factor situation after 3s is the power factor situation after the network side current harmonic suppression strategy is added.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and do not limit the invention.
As shown in fig. 1, the single-phase input electrolytic capacitor-less motor driving system includes: single-phase power supply ugRectifier and thin film capacitor CdcA motor M and an inverter; the single-phase power supply is used for providing single-phase alternating current for the rectifier; the rectifier is a single-phase uncontrolled rectifier and is used for rectifying single-phase alternating current into direct current and supplying power to the inverter; two ends of the thin film capacitor are respectively connected with two ends of the output end of the rectifier, and the thin film capacitor is used for absorbingReceiving higher harmonics generated by the switching of the inverter switching tube; the inverter is a three-phase voltage type inverter and is used for receiving a bridge arm conduction pulse signal sent by a single-phase input electrolytic capacitor-free air conditioner compressor driving system and controlling the motor according to the pulse signal.
Based on the driving system, the invention provides a method for suppressing the current harmonic wave at the network side of the driving system of the permanent magnet synchronous motor without the electrolytic capacitor, which is shown in fig. 2 and comprises the following steps:
the method comprises the following steps: performing PI regulation on the difference value between the given rotating speed and the feedback rotating speed of the motor to generate a power constant
Figure BDA0002993269260000051
Step two: to the real-time voltage u of the power gridgPhase locking is carried out to obtain the grid voltage phase angle information, and the grid voltage phase angle information is processed to obtain the initial waveform quantity k of the input power of the inverter*(t) the functional expression of which is:
Figure BDA0002993269260000052
wherein, ω isgFor the angular frequency of the voltage of the power grid,
Figure BDA0002993269260000053
is the initial phase angle of the network voltage.
Step three: acquiring a network side input current signal, dividing the network side input current signal into two paths of signals, keeping the network side input current unchanged by a line 1 signal, obtaining a network side current harmonic component by subtracting an output signal of a line 2 after low-pass filtering from an output signal of the line 1 through low-pass filtering by a line 2, carrying out PI (proportional integral) regulation on a difference value between a value 0 and the network side current harmonic component, and carrying out absolute value conversion on an output quantity of a PI regulator to obtain an inverter input power waveform correction quantity t*(t)。
Further, the initial value k of the input power waveform of the inverter in the step two*(t) correction of inverter input power waveform*(t) obtaining the inverter by differencingThe input power waveform actual quantity k (t) is expressed as:
k(t)＝k*(t)-t*(t)
and fourthly, because the power consumed by the thin film capacitor is small and the average power is zero in one period, the power consumed by the thin film capacitor can be ignored. The power constant in the first step
Figure BDA0002993269260000061
Multiplying the actual value k (t) of the input power waveform of the inverter in the step three to obtain the given input power p of the inverterinv *Feedback of the inverter input power pinvThe expression of (a) is:
pinv＝1.5*(ud *id+uq *iq)
wherein u isd *、idIs d-axis voltage, d-axis current, where uq *、iqQ-axis voltage, q-axis current.
Further, given the inverter input power pinv *And feedback inverter input power pinvThe difference of (a) is the inverter input power error. This error is controlled by a proportional resonant controller (PR) with a transfer function of:
Figure BDA0002993269260000062
wherein KpIs a proportionality coefficient, KRIs the resonance coefficient, omega0At the resonant frequency, which is the same as the inverter power waveform frequency, ωcIs the cut-off frequency.
PR controller outputs a given q-axis current command iq *Given d-axis current command id *Is 0.
Step five: for d and q axis current command id *、iq *And collecting real-time d and q axis currents id、iqThe error is subjected to proportional and integral operation to obtain d and q axesVoltage command ud、uq。
Further, d-and q-axis voltages are commanded to ud、uqAnd motor cross decoupling voltage udf、uqfAdding the voltage values and performing coordinate transformation to obtain a static coordinate system voltage uαf、uβfAccording to the stationary frame voltage uαf、uβfAnd bus voltage udcAnd controlling the inverter and the motor by utilizing space vector modulation.
In particular, the motor cross-decoupling voltage udf、uqfThe calculation formula of (2) is as follows:
udf＝-Lqiqωe
Figure BDA0002993269260000063
wherein L isd、LqRespectively represent the d-axis inductance and the q-axis inductance of the motor,
Figure BDA0002993269260000064
representing the permanent magnet flux linkage, omegaeRepresenting the angular velocity of the motor.
Fig. 3 is a waveform diagram of the change of the grid-side current before and after the grid-side current harmonic suppression method is added. In the figure, the network side current waveform adopting the traditional inverter power control strategy is shown before 3s, and the network side current waveform added with the network side current harmonic suppression strategy is shown after 3 s. It can be seen that the net side current harmonics are significantly reduced after the net side current harmonics suppression strategy is added.
Fig. 4 is a graph of the power factor change at the grid side before and after the grid side current harmonic suppression method is added. In the figure, the power factor situation before 3s is the power factor situation of the traditional inverter power control strategy, and the power factor situation after 3s is the network side power factor situation after the network side current harmonic suppression strategy is added. It can be seen that the power factor of the network side is obviously improved after the network side current harmonic suppression strategy is added.

Claims (8)

1. A method for suppressing network side current harmonics of a motor driving system without electrolytic capacitors is characterized by comprising the following steps:
step 1: performing PI regulation on the difference value between the given rotating speed and the feedback rotating speed of the motor to generate a power constant
Figure FDA0002993269250000011
Step 2: to the real-time voltage u of the power gridgPhase locking is carried out to obtain the grid voltage phase angle information, and the grid voltage phase angle information is processed to obtain the initial waveform quantity k of the input power of the inverter*(t)；
And step 3: collecting a network side input current signal, extracting a network side current harmonic component, carrying out PI regulation on a difference value between a numerical value 0 and the network side current harmonic component, and carrying out absolute value conversion on the output quantity of a PI regulator to obtain an inverter input power waveform correction quantity t*(t), initial value k of inverter input power waveform in step 2*(t) correction of inverter input power waveform*(t) obtaining the actual waveform quantity k (t) of the input power of the inverter after difference;
step 4, according to the power constant in the step 1
Figure FDA0002993269250000012
And calculating the given power p of the inverter by using the actual value k (t) of the waveform of the input power of the inverterinv *Inverter power given pinv *And inverter power feedback pinvThe error between is controlled by a proportional resonant controller PR, the output of which is a given q-axis current command iq *Given d-axis current command id *Is 0;
and 5: according to d and q axis current commands id *、iq *Collecting real-time d and q axis current id、iqProportional and integral calculation is carried out on the error to obtain d and q axis voltage commands ud、uq(ii) a D, q axis voltage command ud、uqAnd motor cross decoupling voltage udf、uqfAdding the voltage values and performing coordinate transformation to obtain a static coordinate system voltage uαf、uβfAccording toStationary frame voltage uαf、uβfAnd bus voltage udcAnd controlling the inverter and the motor by utilizing space vector modulation.
2. The method for suppressing the grid-side current harmonics of an electrolytic capacitor-free motor drive system according to claim 1, wherein the initial value k of the inverter input power waveform in step 2*The functional expression of (t) is:
Figure FDA0002993269250000013
wherein, ω isgFor the angular frequency of the voltage of the power grid,
Figure FDA0002993269250000014
is the initial phase angle of the network voltage.
3. The method for suppressing the grid-side current harmonics of the electrolytic capacitor-free motor driving system according to claim 1, wherein the functional expression of the actual inverter input power waveform k (t) in step 3 is as follows:
Figure FDA0002993269250000015
4. the method for suppressing the network side current harmonic of the electrolytic capacitor-free motor driving system according to claim 1, wherein the obtaining of the network side current harmonic component in the step 3 specifically comprises: dividing the collected network side input current into two paths of signals, keeping the network side input current unchanged by the line 1 signal, carrying out low-pass filtering on the line 2, and subtracting the output signal of the line 2 after low-pass filtering from the output signal of the line 1 to obtain the network side current harmonic component.
5. The electrolytic capacitor-free motor drive system grid of claim 1The side current harmonic suppression method is characterized in that the step 4 of calculating the inverter input power error specifically comprises the following steps: neglecting the power consumed by the thin film capacitor, the power constant in step 1
Figure FDA0002993269250000021
Multiplying the actual quantity k (t) of the inverter input power waveform in the step 3 to obtain the given inverter input power pinv *。
6. The method for suppressing the network side current harmonic of the electrolytic capacitor-free motor driving system according to claim 1, wherein in the step 4, the inverter input power p is fed back by neglecting the inverter power lossinvThe functional expression of (a) is:
pinv＝1.5*(ud *id+uq *iq) (3)
wherein u isd *、idIs d-axis voltage, d-axis current, where uq *、iqQ-axis voltage, q-axis current.
7. The method for suppressing the network side current harmonics of the motor driving system without the electrolytic capacitor as claimed in claim 1, wherein in step 5, the motor cross-decoupling voltage u isdf、uqfThe calculation formula of (2) is as follows:
udf＝-Lqiqωe (4)
Figure FDA0002993269250000022
wherein L isd、LqRespectively represent the d-axis inductance and the q-axis inductance of the motor,
Figure FDA0002993269250000023
representing the permanent magnet flux linkage, omegaeRepresenting the electrical angular velocity of the motor.
8. A grid-side current harmonic suppression system of a motor driving system without electrolytic capacitor is characterized in that the grid-side current harmonic suppression method of the motor driving system without electrolytic capacitor is based on any one of claims 1 to 7 and comprises the following steps:
constant of power
Figure FDA0002993269250000024
The generation module is used for carrying out PI regulation on the difference value between the given rotating speed and the feedback rotating speed of the motor to generate a power constant
Figure FDA0002993269250000025
Initial value k of input power waveform of inverter*(t) the acquisition module is used for acquiring the real-time voltage u of the power gridgPhase locking is carried out to obtain the grid voltage phase angle information, and the grid voltage phase angle information is processed to obtain the initial waveform quantity k of the input power of the inverter*(t)；
Inverter input power waveform correction t*(t) the acquisition module is used for acquiring a network side input current signal to obtain a network side current harmonic component, carrying out PI (proportional integral) adjustment on a difference value between the numerical value 0 and the network side current harmonic component, and then carrying out absolute value conversion on the output quantity of the PI adjuster to obtain an inverter input power waveform correction quantity t*(t)；
The inverter input power error obtaining module is used for obtaining the power constant according to the step 1
Figure FDA0002993269250000026
To be multiplied by the actual quantity k (t) of the waveform of the input power of the inverter to obtain the given power p of the input power of the inverterinv *Given inverter input power pinv *And feedback inverter input power pinvIs the inverter input power error, this error is controlled by the proportional resonant controller PR, the output of which is a given q-axis current command iq *(ii) a Given d-axis current command id *Is 0;
inverter with a voltage regulatorAnd the motor control module is used for commanding current i of d and q axesd *、iq *And collecting real-time d and q axis currents id、iqCarrying out proportional and integral operation on the error to obtain d and q axis voltage commands ud、uq(ii) a D, q axis voltage command ud、uqAnd motor cross decoupling voltage udf、uqfAdding the voltage values and performing coordinate transformation to obtain a static coordinate system voltage uαf、uβfAccording to the stationary frame voltage uαf、uβfAnd bus voltage udcAnd controlling the inverter and the motor by utilizing space vector modulation.
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CN113992116A (en) * 2021-10-08 2022-01-28 浙江大学 Method for suppressing harmonic current at power grid side of compressor controller without electrolytic capacitor
CN113992116B (en) * 2021-10-08 2022-06-17 浙江大学 Method for suppressing harmonic current at power grid side of compressor controller without electrolytic capacitor
CN113991673A (en) * 2021-11-02 2022-01-28 国网山东省电力公司电力科学研究院 Multi-port common high-frequency electric energy router control method and system
CN113991673B (en) * 2021-11-02 2023-09-08 国网山东省电力公司电力科学研究院 Multi-port common high frequency electric energy router control method and system
WO2023077564A1 (en) * 2021-11-05 2023-05-11 株洲中车时代电气股份有限公司 Method, apparatus, and device for suppressing harmonic of input current of converter and storage medium
CN115313950A (en) * 2022-08-19 2022-11-08 南通帝孚工具科技有限公司 Driving system of servo motor
CN115313950B (en) * 2022-08-19 2023-12-26 中山市瑞思科传动科技有限公司 Driving system of servo motor
CN115378332A (en) * 2022-09-29 2022-11-22 南通大学 Control method for electrolytic capacitor-free permanent magnet synchronous motor
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CN116094416A (en) * 2023-02-17 2023-05-09 哈尔滨工业大学 Electrolytic capacitor-free permanent magnet synchronous motor harmonic suppression method based on steady-state point adaptation
CN116094416B (en) * 2023-02-17 2023-08-29 哈尔滨工业大学 Electrolytic capacitor-free permanent magnet synchronous motor harmonic suppression method based on steady-state point adaptation

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