CN112838766A - High-voltage-reduction-ratio three-level LLC resonant converter and control method thereof - Google Patents

High-voltage-reduction-ratio three-level LLC resonant converter and control method thereof Download PDF

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Publication number
CN112838766A
CN112838766A CN202110015461.6A CN202110015461A CN112838766A CN 112838766 A CN112838766 A CN 112838766A CN 202110015461 A CN202110015461 A CN 202110015461A CN 112838766 A CN112838766 A CN 112838766A
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switch tube
source electrode
resonant
converter
voltage
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CN202110015461.6A
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马红波
卢松
邵志航
易俊宏
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Southwest Jiaotong University
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Southwest Jiaotong University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

The invention discloses a high-buck-ratio three-level LLC resonant converter and a control method thereof. The converter comprises a three-level bridge arm; the three-level bridge arm comprises a first switch tube, a second switch tube, a third switch tube and a fourth switch tube which are sequentially connected in series, and further comprises a first flying capacitor bridged between the source electrode of the first switch tube and the source electrode of the third switch tube and a second flying capacitor bridged between the source electrode of the second switch tube and the source electrode of the fourth switch tube, wherein the drain electrode of the first switch tube is connected to the positive electrode of a power supply, and the source electrode of the fourth switch tube is connected to the negative electrode of the power supply; the device also comprises a resonant network, an isolation transformer and a rectifying and filtering circuit which are connected in sequence; and the positive input end of the resonant network is connected to the source electrode of the third switching tube, and the negative input end of the resonant network is connected to the source electrode of the fourth switching tube. The invention has the advantages that the number of devices is small and the control method is simple; the step-down ratio capacity of the converter is improved, the number of turns of the transformer is small, the efficiency is high, and the method is more suitable for the scene of high step-down ratio application.

Description

High-voltage-reduction-ratio three-level LLC resonant converter and control method thereof
Technical Field
The invention relates to the technical field of resonant converters, in particular to a high-voltage-reduction-ratio three-level LLC resonant converter and a control method thereof.
Background
With the increasing severity of the world energy crisis, the LLC converter can realize zero-voltage conduction of the inverter-side switching tube and zero-current turn-off of the rectifier-side diode (or switching tube) without an auxiliary circuit due to the simple topology, thereby significantly improving the efficiency and power density of the converter, and thus has received extensive attention from the industrial and academic circles. The three-level converter can obviously reduce the stress of a switching tube due to the increase of the number of switches, thereby reducing the switching loss, being considered as an ideal topology of high-voltage input and high-voltage-reduction ratio application occasions, and being widely applied in the application scenes.
Fig. 1a, 1b, 1c and 1d show four current half-bridge three-level LLC resonant converter topologies widely used in industry and industry, and fig. 2a and 2b show the modulation control strategy widely adopted by these four topologies, each switch of which is controlled by a driving signal with 50% duty cycle.
Fig. 1a shows a conventional diode-clamped three-level resonant converter, fig. 1b shows a flying capacitor-clamped three-level resonant converter, fig. 1c shows a diode-and-flying capacitor-clamped three-level resonant converter, and fig. 1d shows a bridge arm series full-bridge three-level resonant converter. The four converters are composed of a voltage-dividing capacitor circuit, a switching inverter bridge arm circuit, a clamping circuit, a resonant network, a transformer, a rectifying circuit and the like, and the voltage-dividing capacitor circuit, the switching inverter bridge arm circuit, the resonant circuit, the transformer and the rectifying circuit in the four topologies have the same functions. Voltage dividing capacitor circuit (C)d1、Cd2) Dividing the input voltage equally to generate two voltage sources which are only half of the input voltage; the switching inverter bridge arm circuit is composed of four switching tubes Q1、Q2、Q3、Q4The series connection is used for inverting the direct current voltage into a square wave; the clamping circuit and the resonant circuit help to realize the soft switching characteristic of the switching tube; the transformer and the rectifying circuit are used for transmitting energy to a load end.
The four topologies differ in that: FIG. 1d shows a topology without a clamping circuit, wherein the clamping circuit in the topology of FIG. 1a is a diode, the clamping circuit in the topology of FIG. 1b is a capacitor, and the clamping circuit in the topology of FIG. 1c is a diode and a capacitor; FIG. 1a, FIG. 1b, FIG. 1c topologiesTwo ends of the middle resonance circuit are respectively connected with the middle point between the two voltage-dividing capacitors and the second switch tube (Q) in the inverter bridge arm2) After the voltage dividing capacitor midpoint in the topology of fig. 1d is short-circuited with the source electrode of the second switching tube in the inverter bridge arm, the resonant circuits are respectively connected with the first switching tube (Q) in the inverter bridge arm1) Source and third switching tube (Q) in inverter bridge arm3) Of the substrate.
The control strategies for four half-bridge three-level LLC resonant converter topologies are shown in fig. 2a and 2 b. Wherein the switching tube Q in the topology shown in FIG. 1a, FIG. 1b, FIG. 1c1、Q2Driven by a set of control signals with the same 50% duty cycle, and a switching tube Q3、Q4Driven by another set of complementary 50% duty ratio control signals, and the peak-to-peak value of the resonant cavity input voltage inverted by a three-level bridge arm is equal to the input voltage VIN(ii) a Switching tube Q in the topology shown in FIG. 1d1、Q4Driven by a set of control signals with the same 50% duty cycle, and a switching tube Q2、Q3Driven by another set of complementary 50% duty ratio control signals, the peak-to-peak value of the resonant cavity input voltage inverted by a three-level bridge arm is also equal to the input voltage VIN. Obviously, when four half-bridge three-level LLC resonant converters adopt a 50% duty ratio control strategy, the peak-to-peak values of the input voltages of the resonant cavities are all input voltages VIN。
However, due to the rapid development of high voltage input applications in the industry, such as three-phase ac power systems, fuel cell systems, ship distribution systems, and high voltage charging systems, the input voltage level of the systems is also increasing. At this time, the disadvantage of insufficient voltage reduction capability of the four widely used half-bridge three-level LLC is more obvious, and the direct consequence is that the transformer must meet the requirement of the voltage reduction capability of the converter with a higher primary-secondary turn ratio, that is, the transformation ratio of the transformer is improved by increasing the number of turns of the primary side, but the increase and the large volume of the transformer loss are simultaneously implied, which is not beneficial to improving the efficiency and the power density of the converter.
Disclosure of Invention
The invention aims to provide a high step-down ratio three-level LLC resonant converter and a control method thereof.
The technical scheme for realizing the purpose of the invention is as follows:
a high step-down ratio three-level LLC resonant converter comprises a three-level bridge arm; the three-level bridge arm comprises a first switch tube, a second switch tube, a third switch tube and a fourth switch tube which are sequentially connected in series, and further comprises a first flying capacitor bridged between the source electrode of the first switch tube and the source electrode of the third switch tube and a second flying capacitor bridged between the source electrode of the second switch tube and the source electrode of the fourth switch tube, wherein the drain electrode of the first switch tube is connected to the positive electrode of a power supply, and the source electrode of the fourth switch tube is connected to the negative electrode of the power supply; the device also comprises a resonant network, an isolation transformer and a rectifying and filtering circuit which are connected in sequence; and the positive input end of the resonant network is connected to the source electrode of the third switching tube, and the negative input end of the resonant network is connected to the source electrode of the fourth switching tube.
According to the control method of the high step-down ratio three-level LLC resonant converter, a first group of driving signals with 50% duty ratio are simultaneously applied to a first switching tube and a third switching tube, and a second group of driving signals with 50% duty ratio are simultaneously applied to a second switching tube and a fourth switching tube; the first set of drive signals and the second set of drive signals are complementary; a dead time is provided between the first set of drive signals and the second set of drive signals.
The invention has the beneficial effects that: (1) the number of devices is small, and the control method is simple; (2) the step-down ratio capacity of the converter is improved, and the converter is more suitable for a scene of high step-down ratio application; (3) compared with the existing half-bridge three-level LLC resonant converter, under the same input and output level, the number of turns of the primary side of the isolation transformer is reduced by half, the loss is reduced, and the efficiency and the power density of the converter are improved.
Drawings
Fig. 1a shows a conventional diode clamped (topology one) half bridge three level LLC converter.
Fig. 1b shows a flying capacitor clamped (topology two) half-bridge three-level LLC converter.
Fig. 1c shows a diode and flying capacitor clamped (topology three) half-bridge three-level LLC converter.
Fig. 1d shows a bridge arm series (topology four) half bridge three level LLC converter.
Fig. 2a is a schematic diagram of a topology one, topology two, and topology three-purpose half-bridge three-level LLC control strategy.
Fig. 2b is a schematic diagram of a topology four-purpose half-bridge three-level LLC control strategy.
Fig. 3 is a block diagram of a high buck ratio half bridge three level LLC converter of an embodiment.
Fig. 4 is a waveform diagram of steady-state operation of the high buck ratio half-bridge three-level LLC converter of the embodiment.
FIG. 5a is an equivalent circuit diagram of the embodiment in the operating state I.
Fig. 5b is an equivalent circuit diagram of the embodiment in the operating state II.
Fig. 5c is an equivalent circuit diagram of the embodiment in the operating state III.
Fig. 5d is an equivalent circuit diagram of the embodiment in the operating state IV.
Labeled as: input power supply voltage VINInput voltage-dividing capacitor Cd1、Cd2Switching tube Q1、Q2、Q3、Q4Parasitic capacitance C of switch tubeQ1、CQ2、CQ3、CQ4Diode D of switch tube bodyQ1、DQ2、DQ3、DQ4Flying capacitor CFLY、CMIDResonant inductance LrExcitation inductance LmResonant capacitor CrIsolation transformer TR, secondary rectifier diode D1、D2Output filter capacitor C0Load RLOutput voltage V0Voltage V between points A and BAB(i.e., resonant network input voltage), four switching tube drive waveform Vgs_Q1、Vgs_Q2、Vgs_Q3、Vgs_Q4Voltage waveform V between drain and source when four switching tubes are workingds_Q1、Vds_Q2、Vds_Q3、Vds_Q4Resonant cavity resonant current waveform iLrSecondary side rectifier diode current waveform iD1、iD2。
Detailed Description
The invention is further described below with reference to the accompanying drawings.
Referring to FIG. 3, the circuit of the embodiment is composed of a flying capacitor CFLYThree-level bridge arm and flying capacitor CMIDThe circuit comprises a resonant network, an isolation transformer and a rectifying and filtering circuit. Wherein the flying capacitor CFLYAnd flying capacitor CMIDThe capacitance values of (a) are very large and equal, and the steady-state operating voltages of the (b) are half of the input voltage. The secondary side of the isolation transformer can adopt a full-wave rectification or full-bridge rectification mode. Here, taking full-wave rectification as an example, D1、D2Are two rectifier diodes. The resonant circuit is composed of a resonant capacitor CrResonant inductor LrAnd an excitation inductance LmThe resonant network is used for realizing zero voltage switching of the switching tube and zero current switching of the rectifier diode. Wherein the resonant capacitor CrAnd a resonant inductor LrResonant frequency at frRepresents the vibration capacitance CrResonant inductor LrAnd an excitation inductance LmResonant frequency of the three, in fmIs shown, and fr>fm。
The control method of the circuit is as shown in FIG. 4: for the first switch tube Q1And a third switching tube Q3Applying a set of driving signals with 50% duty ratio to the second switching tube Q2And a fourth switching tube Q4Another set of complementary 50% duty cycle drive signals is applied with a dead band between the two sets of drive signals. In line with conventional LLC converters, the converter regulates the output voltage by varying the frequency of the switching tube control signal.
Due to the magnitude relationship between the switching frequency fs and the resonant frequency fr, the operation modes of the converter are divided into three types, namely, a under-resonant mode (fs < fr), a quasi-resonant mode (fs ═ fr), and an over-resonant mode (fs > fr). The operation principle of the converter in different modes is slightly different, but the LLC converter has the highest efficiency when operating in a quasi-resonant mode (fs ═ fr). Therefore, the present description only deals with the case of fs ═ fr to analyze the working principle, and the other two analysis methods are similar.
In the quasi-resonant mode (fs ═ fr) mode, one switching period of the converter can be divided into 4 working modes, and in the steady-state operation, the waveforms of each key voltage and current are as shown in fig. 4.
The specific working principle is as follows:
(1) operating state I, as shown in fig. 5 a: t is t0<t<t1And (5) stage. At t0Time, Q1And Q3Zero voltage conduction, resonant cavity input voltage VABIs 0.5VIN，LrAnd CrAnd (4) series resonance. Resonant current forward resonance, secondary side rectifier diode D2On, the primary side voltage of the transformer is clamped to nV0Excitation current in nV from minimum value0/LmThe slope of (a) increases linearly. In this stage, the resonant current is always greater than the excitation current, and the difference between the two is transmitted to the load through the transformer. The source of the resonant current is divided into two parts, half of the resonant current is from the input, and the current flows through the flying capacitor CFLYAnd to flying capacitor CFLYCharging, the other half of resonant current is driven by flying capacitor CMIDProviding, i.e. flying capacitors CMIDAnd (4) discharging.
(2) Operating state II, as shown in fig. 5 b: t is t1<t<t2And (5) stage. At t1Time, Q1And Q3And simultaneously, the current of the secondary side rectifier diode is turned off, the current of the secondary side rectifier diode just resonates to 0, the primary side resonant current is equal to the maximum value of the exciting current, and the input voltage of the resonant cavity is controlled to be 0.5VINThe commutation is started. In this stage, Lr、Lm、CrThe three elements resonate together, and since the resonant periods of the three elements are long, the resonant current in the dead time may remain approximately constant. The resonant current giving Q due to hysteresis of the resonant current3Output capacitor CQ3Charging while supplying Q4Output capacitor CQ4And (4) discharging. Input continues to flying capacitor CFLYCharging with charging current for Q1Output capacitor CQ1Charging and Q2Output capacitor CQ2And (4) discharging.
(3) Operating state III, as shown in fig. 5 c: t is t2<t<t3And (5) stage. At t2Time of day, Vds_Q1And Vds_Q3Has been charged to 0.5VIN，Vds_Q2And Vds_Q4Is discharged to 0, at which time Q2And Q4Zero voltage conduction, resonant cavity input voltage has been reversed to 0, LrAnd CrAnd (4) series resonance. At this time, the secondary side rectifier diode D1On, the primary side voltage of the transformer is clamped to-nV0The excitation current starting from a maximum value is at-nV0/LmThe slope of (a) decreases linearly. In this stage, the resonant current is always larger than the exciting current, the difference between the two is used for transferring energy to the load through the transformer, but the load energy at the moment is provided by the bias voltage on the resonant capacitor. It is noteworthy that, ideally, CFLYCapacitance and CMIDThe capacitor voltage is 0.5VINHowever, during actual steady state, Q2The conduction of the switch tube leads the two flying capacitors to be directly connected in parallel, so that the two capacitors directly have a voltage-sharing process of transient capacitor voltage, but the steady-state average voltage of the two flying capacitor voltages is always 0.5VIN。
(4) Operating state IV, as shown in fig. 5 d: t is t3<t<t4And (5) stage. At t3Time, Q2And Q4Off, secondary side D1The middle resonance current just resonates to 0 in the positive direction, the load energy is provided by the output capacitor, and the primary side resonance current is equal to the exciting current. Similar to operating state II, at this time, Lr、Lm、CrThe three elements resonate together, with the excitation current equal to the resonant current, and during this phase Q is supplied2And Q4Output capacitor CQ2、CQ4Charging, Q1And Q3Output capacitor CQ1、CQ3And (4) discharging. At t4Time of day, Vds_Q2And Vds_Q4Has been charged to 0.5VIN，Vds_Q1And Vds_Q3To 0, thereby realizing Q1And Q3Zero voltage conduction, resonant cavity input voltage has been reversed to 0.5VIN。
In summary, the novel half-bridge three-level LLC resonant converter provided by the present invention retains the zero-voltage turn-on and zero-current turn-off characteristics of the conventional LLC resonant converter, and at the same time, has the following advantages compared with the conventional half-bridge three-level LLC resonant converter:
1. compared with the four traditional half-bridge three-level LLC resonant converters, the half-bridge three-level LLC resonant converter omits a half-bridge input voltage-dividing capacitor and adds one flying capacitor, so the total number of the components is equivalent to that of the traditional bridge arm series half-bridge three-level LLC topology, but is still superior to other three types of half-bridge three-level LLC topologies.
2. Compared with the existing four traditional half-bridge three-level LLC resonant converters, the four switching tubes in the invention are still driven by control signals with 50% duty ratio, but have higher voltage reduction capability. This is reflected in the fact that the peak-to-peak value of the input voltage of the resonant cavity inverted by the three-level bridge arm is equal to the input voltage VINThe peak-to-peak value of the resonant cavity input voltage inverted by the three-level bridge arm of the four types of traditional half-bridge three-level LLC is equal to the input voltage VIN。
3. Compared with the four traditional half-bridge three-level LLC resonant converters, the half-bridge three-level LLC resonant converter has the advantages that the flying capacitor connection mode and the resonant circuit connection mode are changed, so that the performance of the converter is improved, and the zero-voltage conduction of a primary side switch tube and the zero-current turn-off characteristic of a secondary side rectifier diode of the LLC resonant converter are reserved.
4. Compared with the existing four traditional half-bridge three-level LLC resonant converters, the half-bridge three-level LLC resonant converter has the advantages that the number of turns of the transformer under the same input and output level can be reduced by half, the transformer loss is reduced, and the efficiency and the power density of the converter are improved.

Claims (2)

1. A high step-down ratio three-level LLC resonant converter is characterized by comprising a three-level bridge arm; the three-level bridge arm comprises a first switch tube, a second switch tube, a third switch tube and a fourth switch tube which are sequentially connected in series, and further comprises a first flying capacitor bridged between the source electrode of the first switch tube and the source electrode of the third switch tube and a second flying capacitor bridged between the source electrode of the second switch tube and the source electrode of the fourth switch tube, wherein the drain electrode of the first switch tube is connected to the positive electrode of a power supply, and the source electrode of the fourth switch tube is connected to the negative electrode of the power supply; the device also comprises a resonant network, an isolation transformer and a rectifying and filtering circuit which are connected in sequence; and the positive input end of the resonant network is connected to the source electrode of the third switching tube, and the negative input end of the resonant network is connected to the source electrode of the fourth switching tube.
2. The method for controlling the high step-down ratio three-level LLC resonant converter as claimed in claim 1, wherein a first set of 50% duty cycle drive signals is applied simultaneously to the first switching tube and the third switching tube, and a second set of 50% duty cycle drive signals is applied simultaneously to the second switching tube and the fourth switching tube; the first set of drive signals and the second set of drive signals are complementary; a dead time is provided between the first set of drive signals and the second set of drive signals.
CN202110015461.6A 2021-01-06 2021-01-06 High-voltage-reduction-ratio three-level LLC resonant converter and control method thereof Pending CN112838766A (en)

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Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN113315381A (en) * 2021-05-26 2021-08-27 江苏京创先进电子科技有限公司 Novel LCLCL resonant converter and high-efficiency resonant driving method thereof
CN113315372A (en) * 2021-05-26 2021-08-27 南京矽力微电子技术有限公司 Power converter
CN113541502A (en) * 2021-07-26 2021-10-22 西南交通大学 Half-bridge three-level resonant converter and control method thereof
CN113708627A (en) * 2021-07-26 2021-11-26 苏州浪潮智能科技有限公司 Resonant converter

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CN106026665A (en) * 2016-06-27 2016-10-12 特变电工西安电气科技有限公司 Novel three-level frequency multiplication LLC resonance converter
US20170353116A1 (en) * 2016-06-07 2017-12-07 Linear Technology Corporation Transformer-based hybrid power converters
US20180123451A1 (en) * 2016-11-03 2018-05-03 Gn Hearing A/S Switched capacitor dc-dc power converter
US20190199221A1 (en) * 2017-12-26 2019-06-27 Silergy Semiconductor Technology (Hangzhou) Ltd Direct current-direct current converter
DE102019002880A1 (en) * 2018-04-19 2019-10-24 Linear Technology Holding Llc Efficiency improvement at low load of a hybrid capacitor capacitor converter

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Publication number Priority date Publication date Assignee Title
US20170353116A1 (en) * 2016-06-07 2017-12-07 Linear Technology Corporation Transformer-based hybrid power converters
CN106026665A (en) * 2016-06-27 2016-10-12 特变电工西安电气科技有限公司 Novel three-level frequency multiplication LLC resonance converter
US20180123451A1 (en) * 2016-11-03 2018-05-03 Gn Hearing A/S Switched capacitor dc-dc power converter
US20190199221A1 (en) * 2017-12-26 2019-06-27 Silergy Semiconductor Technology (Hangzhou) Ltd Direct current-direct current converter
DE102019002880A1 (en) * 2018-04-19 2019-10-24 Linear Technology Holding Llc Efficiency improvement at low load of a hybrid capacitor capacitor converter

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN113315381A (en) * 2021-05-26 2021-08-27 江苏京创先进电子科技有限公司 Novel LCLCL resonant converter and high-efficiency resonant driving method thereof
CN113315372A (en) * 2021-05-26 2021-08-27 南京矽力微电子技术有限公司 Power converter
CN113541502A (en) * 2021-07-26 2021-10-22 西南交通大学 Half-bridge three-level resonant converter and control method thereof
CN113708627A (en) * 2021-07-26 2021-11-26 苏州浪潮智能科技有限公司 Resonant converter

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Application publication date: 20210525