CN112468051A - Multiphase permanent magnet motor high-frequency vibration rapid analysis method and suppression strategy thereof - Google Patents
Multiphase permanent magnet motor high-frequency vibration rapid analysis method and suppression strategy thereof Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P23/00—Arrangements or methods for the control of AC motors characterised by a control method other than vector control
- H02P23/04—Arrangements or methods for the control of AC motors characterised by a control method other than vector control specially adapted for damping motor oscillations, e.g. for reducing hunting
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P23/00—Arrangements or methods for the control of AC motors characterised by a control method other than vector control
- H02P23/0077—Characterised by the use of a particular software algorithm
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
- H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
- H02P25/16—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the circuit arrangement or by the kind of wiring
- H02P25/22—Multiple windings; Windings for more than three phases
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Abstract
The application discloses a high-frequency vibration rapid analysis method and a suppression strategy for a multiphase permanent magnet motor. The method comprises the following steps: s1, analyzing and calculating the current harmonic of the PWM inverter power supply multiphase permanent magnet motor; s2, calculating the electromagnetic force applied to each tooth of the motor stator by using a magnetic conductance distribution characteristic function method; s3, decomposing the electromagnetic force borne by the motor stator through two-dimensional Fourier, selecting the high-frequency component of the zero-order electromagnetic force as a reference quantity, and indirectly analyzing the high-frequency vibration of the motor. Compared with the existing circuit and electromagnetic field simulation analysis method, the multiphase permanent magnet motor high-frequency vibration rapid analysis method has clear and visual physical concept, high calculation efficiency and strong universality. By applying the high-frequency vibration rapid method of the multiphase permanent magnet motor, a high-frequency vibration suppression strategy based on carrier phase shift is determined, the cancellation of the high-frequency electromagnetic force of the motor introduced by PWM is realized, and the high-frequency electromagnetic vibration noise of the motor is suppressed.
Description
Technical Field
The application relates to the technical field of permanent magnet motors, in particular to a high-frequency vibration rapid analysis method and a suppression strategy for a multiphase permanent magnet motor.
Background
The permanent magnet motor has the advantages of high power density, high efficiency, simple structure, easy control and the like, and is widely applied to occasions with various power grades.
The multi-phase permanent magnet motor has more winding phases, and armature reaction magnetomotive force has higher sine degree, so compared with the traditional three-phase permanent magnet motor, the multi-phase permanent magnet motor has inherent advantages in the performances of torque pulsation, vibration noise and the like. And then the motor can have excellent low-frequency vibration noise characteristics by optimizing the structural design of the motor, improving a control algorithm and the like. Therefore, the multiphase permanent magnet motor is applied to the fields with higher requirements on vibration noise performance, such as naval vessel propulsion, high-precision servo systems, electrified traffic and the like.
However, as modern motors are mostly powered by PWM inverters, high frequency harmonics of the frequency multiplication of the switching frequency of the power electronic devices and the side frequency thereof exist in the current, and the high frequency current harmonics excite a high frequency magnetic field, thereby causing high frequency vibration noise, which becomes a key bottleneck problem that currently restricts the vibration noise performance of the high performance permanent magnet motor system. More specifically, for a large-capacity naval vessel propulsion motor system, the loss of power electronic devices is limited, the switching frequency of an inverter is generally low, so that the line spectrum of high-frequency vibration noise falls into a sonar sensitive detection frequency band or an auditory range frequency band of human ears, and bad influence is brought to the invisibility and comfort of the naval vessel.
In order to solve the problems, firstly, the high-frequency vibration needs to be analyzed and calculated accurately and quickly, and a suppression method can be proposed specifically. The motor high-frequency vibration analysis method can be divided into two major steps: and performing electromagnetic vibration source analysis calculation and structural vibration calculation analysis, wherein the electromagnetic vibration source calculation analysis can be subdivided into current harmonic calculation and high-frequency electromagnetic force calculation. The existing methods have certain defects.
In the aspect of current harmonic analysis and calculation, most of the existing methods rely on power electronic circuit simulation software such as PLECS and Matlab-simulink, and the method needs to spend a large amount of time to build and debug a model in the early stage. According to shannon's sampling theorem, if the high frequency harmonics are analyzed without distortion, the sampling frequency of the simulation model should be greater than 2 times of the analyzed frequency, resulting in a longer running time of the simulation model.
In the aspect of electromagnetic force analysis and calculation, the existing method mainly aims at low-frequency low-order electromagnetic force waves generated by interaction of motor fundamental wave current and low-order harmonic current with permanent magnet fundamental wave and low-order harmonic wave. Generally, finite element method or analytic method is adopted to firstly obtain the magnetic flux density distribution of the central line of the motor air gap or the inner circle line of the stator, and then electromagnetic force is obtained by Maxwell stress tensor method. The research shows that when the carrier phase shift technology is applied, the majority of the magnetic flux excited by the high-frequency current harmonic waves is stator slot leakage magnetic flux and tooth crest leakage magnetic flux, and the main magnetic flux passing through the air gap accounts for a small proportion. However, the conventional concept of using the air gap flux density as an analysis object in the study of low-frequency low-order electromagnetic force is still used in the conventional analysis and calculation method for high-frequency electromagnetic force, and the electromagnetic excitation force generated by the slot leakage flux is not considered, so that the high-frequency electromagnetic force cannot be accurately and quantitatively analyzed.
In the aspect of structural vibration analysis and calculation, a statistical energy method is a main method for the dynamics problem of a high-frequency sound vibration system, namely, the state of a subsystem is described by using energy, the interaction between coupling subsystems is described by using a power flow balance equation, and finally the required response is converted. The coupling loss factor and the internal loss factor of the motor subsystem need to be measured through a large number of experiments, and the experimental process is complicated. In addition, the actual motor system cannot completely meet the assumed limit conditions of the statistical energy method, and the improvement of the existing method needs to be further researched.
In the aspect of a high-frequency vibration suppression strategy, a carrier phase-shifting PWM technology is an effective technical route. The phase of the carrier wave is moved, so that the phase of the high-frequency harmonic current is changed, the high-frequency magnetic field of the motor is offset, and the electromagnetic vibration source of characteristic frequency is restrained. The carrier phase shift PWM technology has the side effects of increasing high-frequency current harmonic waves and increasing system loss. The existing strategy mainly comprises: two sets of windings arranged in the same slot are powered by two independent inverters, and the carrier of the two inverters is shifted by 90 degrees or 180 degrees according to a PWM modulation mode. However, other carrier phase shifting strategies for multi-phase machines in the form of windings are not clear.
In summary, the existing analysis and calculation methods cannot completely meet the requirement of calculation accuracy, and a large amount of preparation work is needed before calculation, so that accuracy and rapidity are difficult to be considered. The existing carrier phase shift strategy mainly aims at a special winding form that two sets of windings are arranged in the same slot, and the carrier phase shift strategy is not an optimal carrier phase shift strategy for a multi-phase motor.
Disclosure of Invention
In order to solve the above problem, embodiments of the present application provide a method for rapidly analyzing high-frequency vibration of a multiphase permanent magnet motor and a suppression strategy thereof.
In a first aspect, an embodiment of the present application provides a method for fast analyzing high-frequency vibration of a multiphase permanent magnet motor, where the method includes:
s1, analyzing and calculating the time domain waveform of the current of the PWM inverter power supply multiphase permanent magnet motor based on the carrier phase shift angle of each inversion unit and the motor working condition of the PWM inverter power supply multiphase permanent magnet motor;
s2, calculating to obtain the time domain waveform of the electromagnetic force applied to each tooth of the motor stator by using a magnetic conductance distribution characteristic function method based on the time domain waveform of the current;
s3, decomposing the time domain waveform of the electromagnetic force borne by the motor stator through two-dimensional Fourier, selecting the high-frequency component of the zero-order electromagnetic force as a reference, and indirectly analyzing the high-frequency vibration of the motor based on the reference.
Preferably, the step S1 includes:
s11, establishing a 3D mathematical model of the inverter output PWM pulse waveform, and establishing a voltage time domain waveform analysis expression;
s12, inputting the carrier phase shift angle of each inversion unit and the motor working condition of the multiphase permanent magnet motor powered by the PWM inverter into the expression to obtain the time domain waveform of the output voltage of the inverter;
and S13, introducing the time domain waveform of the output voltage of the inverter into a multi-phase permanent magnet motor state equation to obtain the time domain waveform of the current of the multi-phase permanent magnet motor supplied by the PWM inverter.
Preferably, the step S2 includes:
s21, calculating to obtain stator surface flux density distribution based on a flux guide distribution characteristic function and the time domain waveform of the multiphase permanent magnet motor current;
and S22, calculating the magnetic density distribution on the surface of the stator by using a Maxwell tensor method to obtain the time domain waveform of the electromagnetic force applied to the tooth part of the stator.
Preferably, the step S3 includes:
s31, performing two-dimensional Fourier decomposition on the time domain waveform of the electromagnetic force borne by the motor stator to obtain the frequency spectrum of each order of electromagnetic force;
and S32, selecting the high-frequency component of the zeroth-order electromagnetic force from the frequency spectrum of each-order electromagnetic force as a reference, and indirectly analyzing the high-frequency vibration based on the reference.
In a second aspect, the present application provides a polyphase permanent magnet motor dither suppression strategy, where the suppression strategy includes the following steps:
s4, setting carrier phase shift angles of all inversion units, calculating to obtain a zero-order electromagnetic force high-frequency component based on the multiphase permanent magnet motor high-frequency vibration rapid analysis method, and determining the carrier phase shift angle combination when the amplitude of the zero-order electromagnetic force high-frequency component is minimum as an optimal carrier phase shift strategy;
and S5, adjusting the PWM carrier phase angle of each phase inversion unit of the motor system to be the carrier phase shift angle combination corresponding to the optimal carrier phase shift strategy.
The invention has the beneficial effects that:
(1) the multiphase permanent magnet motor current harmonic wave analytic calculation method is based on a PWM pulse waveform 3-D mathematical model and a motor state equation, and the physical concept is clear and visual. Compared with the existing circuit simulation software, the method has the advantages of high calculation efficiency and strong universality, and is easy to combine with other models.
(2) The method can accurately and quantitatively calculate the space-time distribution of the high-frequency electromagnetic force on the physical surface of the motor stator under the condition that the high-frequency magnetic field of the air gap is seriously distorted after the carrier phase shift technology is adopted.
(3) The high-frequency vibration is indirectly analyzed by selecting the zero-order electromagnetic force high-frequency component, the structural dynamics calculation of a high-frequency acoustic vibration system is omitted, the calculation efficiency is improved, and the influence of carrier phase shift on the high-frequency vibration can still be correctly represented.
(4) The high-frequency vibration suppression strategy can realize the mutual cancellation of high-frequency electromagnetic force without additional hardware such as an additional filter and the like, and the problem of high-frequency vibration noise is solved.
Drawings
In order to more clearly illustrate the technical solutions in the embodiments of the present application, the drawings needed to be used in the embodiments will be briefly described below, and it is obvious that the drawings in the following description are only some embodiments of the present application, and it is obvious for those skilled in the art to obtain other drawings without creative efforts.
Fig. 1 is a schematic flowchart of a method for rapidly analyzing high-frequency vibration of a multiphase permanent magnet motor according to an embodiment of the present disclosure;
fig. 2 is an exemplary schematic diagram of a PWM pulse waveform 3D mathematical model provided in an embodiment of the present application;
FIG. 3 is a diagram illustrating an example of a flux guide distribution characteristic function provided in an embodiment of the present application;
fig. 4 is a schematic flowchart of a high-frequency vibration suppression strategy of a multiphase permanent magnet motor according to an embodiment of the present application;
fig. 5 is an exemplary schematic diagram of a twelve-phase permanent magnet motor winding structure and system framework provided in an embodiment of the present application;
FIG. 6 is a schematic diagram illustrating an example of carrier phase shift PWM provided in an embodiment of the present application;
fig. 7 is an exemplary schematic diagram of a variation trend of a carrier frequency component of a twelve-phase permanent magnet motor, which is 2 times of the zero-order electromagnetic force, along with a carrier phase shift angle according to an embodiment of the present application;
fig. 8 is an exemplary schematic diagram of a variation trend of a carrier frequency component of a twelve-phase permanent magnet motor foot vibration acceleration of 2 times with a carrier phase shift angle provided in an embodiment of the present application.
Detailed Description
The technical solutions in the embodiments of the present application will be clearly and completely described below with reference to the drawings in the embodiments of the present application.
In the following description, the terms "first" and "second" are used for descriptive purposes only and are not intended to indicate or imply relative importance. The following description provides embodiments of the present application, where different embodiments may be substituted or combined, and thus the present application is intended to include all possible combinations of the same and/or different embodiments described. Thus, if one embodiment includes feature A, B, C and another embodiment includes feature B, D, then this application should also be considered to include an embodiment that includes one or more of all other possible combinations of A, B, C, D, even though this embodiment may not be explicitly recited in text below.
The following description provides examples, and does not limit the scope, applicability, or examples set forth in the claims. Changes may be made in the function and arrangement of elements described without departing from the scope of the disclosure. Various examples may omit, substitute, or add various procedures or components as appropriate. For example, the described methods may be performed in an order different than the order described, and various steps may be added, omitted, or combined. Furthermore, features described with respect to some examples may be combined into other examples.
Referring to fig. 1, fig. 1 is a schematic flowchart of a method for fast analyzing high-frequency vibration of a multiphase permanent magnet motor according to an embodiment of the present application. In an embodiment of the present application, the method includes:
and S1, analyzing and calculating the time domain waveform of the current of the PWM inverter power supply multiphase permanent magnet motor based on the carrier phase shift angle of each inversion unit and the motor working condition of the PWM inverter power supply multiphase permanent magnet motor.
In one possible embodiment, step S1 includes:
s11, establishing a 3D mathematical model of the inverter output PWM pulse waveform, and establishing a voltage time domain waveform analysis expression;
s12, inputting the carrier phase shift angle of each inversion unit and the motor working condition of the multiphase permanent magnet motor powered by the PWM inverter into the expression to obtain the time domain waveform of the output voltage of the inverter;
and S13, introducing the time domain waveform of the output voltage of the inverter into a multi-phase permanent magnet motor state equation to obtain the time domain waveform of the current of the multi-phase permanent magnet motor supplied by the PWM inverter.
In the embodiment of the application, the PWM modulation is the root cause of the generation of the dither noise, so that the application first establishes a 3D mathematical model of the PWM pulse waveform, that is, establishes an analytic functional relation between the PWM modulation strategy, the motor operating parameters (such as modulation method, sampling strategy, carrier frequency, carrier phase, fundamental frequency, fundamental phase, etc.) and the inverter output voltage time-domain waveform, so as to analytically calculate the voltage time-domain waveform. And then, introducing the voltage time domain waveform into a motor state equation, and obtaining a current time domain waveform through numerical integration.
In the process of establishing the 3D mathematical model, the non-ideal factors of dead time are taken into account, namely, correction components introduced by the dead time are added into the output voltage expression, so that the PWM pulse waveform 3D mathematical model is more appropriate to an actual inversion unit.
Specifically, as shown in fig. 2, fig. 2 is an exemplary schematic diagram of a PWM pulse waveform 3D mathematical model provided in the embodiment of the present application, and this example is a three-level H-bridge topology and adopts a natural sampling SPWM modulation. The carrier wave is compared with the modulation wave to generate a driving signal, and the crossing point of the modulation wave and the carrier wave, namely the PWM waveform level switching moment. The carrier phase angle theta at the intersection varies with the modulation wave phase angle delta and defines an intersection phase angle function theta (delta), i.e., a sinusoidal curve interleaved in the theta-delta plane. As time progresses, the line P extends forward with a slope equal to the ratio of the modulated wave frequency to the carrier frequency. The point of intersection of P with the phase angle function, i.e. the moment of level change. In the 3D model, the PWM pulse waveform is set as a binary function F (theta, delta) of theta and delta, a plane P is intersected with a solid figure surrounded by an intersection phase angle function theta (delta), and a cross section is projected to the F (theta, delta) -theta plane to form the PWM pulse waveform.
And S2, calculating the electromagnetic force time domain waveform borne by each tooth of the motor stator by using a magnetic conductance distribution characteristic function method based on the time domain waveform of the current.
In one possible embodiment, step S2 includes:
s21, calculating to obtain stator surface flux density distribution based on a flux guide distribution characteristic function and the time domain waveform of the multiphase permanent magnet motor current;
and S22, calculating the magnetic density distribution on the surface of the stator by using a Maxwell tensor method to obtain the time domain waveform of the electromagnetic force applied to the tooth part of the stator.
In the embodiment of the application, the characteristic function of flux guide distribution is introduced because after the carrier phase shift technology is applied, most of the magnetic fluxes excited by high-frequency current harmonics are slot leakage flux and slot top leakage flux, the proportion of main magnetic flux passing through an air gap is small, and the air gap magnetic field cannot accurately represent the real flux density distribution of the actual physical surface of the motor stator. And the actual flux density distribution of the actual physical surface of the stator can be accurately described through the flux guide distribution characteristic function and the phase current. After physical quantity of magnetic density distribution of the actual surface of the stator is determined, the time-space distribution of radial electromagnetic force of the stator tooth part can be calculated by applying a Maxwell tensor method, and the electromagnetic force is determined.
Specifically, as shown in fig. 3, fig. 3 is an exemplary schematic diagram of a characteristic function of flux guide distribution provided in the embodiment of the present application. Firstly, magnetic density distribution of stator surfaces such as stator tooth tops, tooth walls and the like under excitation of single phase current is extracted in an off-line mode through a static magnetic field finite element, and then a matrix expression form of magnetic density of each boundary of a stator under the action of each phase current (including PWM high-frequency harmonic current) of an armature of a motor is established through a simple matrix expression form according to space symmetry and a magnetic field superposition principle. Next, the magnetic field distribution generated by the permanent magnet at the boundary is calculated, and the magnetic fields generated by the armature reaction and the permanent magnet at the stator boundary are superimposed to obtain the actual magnetic field distribution. And finally, calculating the electromagnetic force distribution of the surfaces of the stator teeth by respectively applying a Maxwell tensor method.
S3, decomposing the time domain waveform of the electromagnetic force borne by the motor stator through two-dimensional Fourier, selecting the high-frequency component of the zero-order electromagnetic force as a reference, and indirectly analyzing the high-frequency vibration of the motor based on the reference.
In one possible embodiment, step S3 includes:
s31, performing two-dimensional Fourier decomposition on the time domain waveform of the electromagnetic force borne by the motor stator to obtain the frequency spectrum of each order of electromagnetic force;
and S32, selecting the high-frequency component of the zeroth-order electromagnetic force from the frequency spectrum of each-order electromagnetic force as a reference, and indirectly analyzing the high-frequency vibration based on the reference.
In the embodiment of the application, according to the early-stage experimental results aiming at the zero-order electromagnetic force and the vibration acceleration of the machine leg, the amplitude values of the high-frequency characteristic points of the zero-order electromagnetic force and the machine leg are highly consistent with the change trend of the carrier phase shift angle, so that the high-frequency component of the zero-order electromagnetic force is selected as a research object, and the high-frequency vibration can be indirectly analyzed according to the analysis result of the high-frequency component of the zero-order.
Referring to fig. 4, fig. 4 is a schematic flowchart of a high-frequency vibration suppression strategy of a multiphase permanent magnet motor according to an embodiment of the present application. In an embodiment of the present application, the suppression strategy includes the following methods:
s4, setting carrier phase shifting angles of all inversion units, calculating to obtain zero-order electromagnetic force high-frequency components based on the multiphase permanent magnet motor high-frequency vibration rapid analysis method of claims 1-4, and determining the carrier phase shifting angle combination when the amplitude of the zero-order electromagnetic force high-frequency components is minimum as an optimal carrier phase shifting strategy;
and S5, adjusting the PWM carrier phase angle of each phase inversion unit of the motor system to be the carrier phase shift angle combination corresponding to the optimal carrier phase shift strategy.
Specifically, as shown in fig. 5, fig. 5 is an exemplary schematic diagram of a winding structure and a system frame of a twelve-phase permanent magnet motor according to an embodiment of the present application. The motor stator winding structure adopts lap windings, the coil pitch is equal to the pole pitch, the number of slots of each phase of each pole is 1, and each phase of winding is independently arranged in one stator slot. The twelve-phase winding can be divided into four sets of three-phase windings with mutual difference of 15 degrees in electrical angle. Two ends of each phase of winding are led out, power is supplied by an independent H-bridge inverter unit, and the inverter unit adopts an asymmetric regular sampling bipolar SPWM modulation strategy. Because each phase winding is supplied with power by the independent inversion unit, twelve carrier phase shift 'freedom' exists.
Specifically, as shown in fig. 6, fig. 6 is an exemplary schematic diagram of the carrier phase shift PWM provided in the embodiment of the present application. The carrier phase shift PWM technique utilizes a degree of freedom of "phase difference between carriers", and shifts the carriers of the two inverters by an angle θ, so that the phase of the voltage harmonic of a specific carrier frequency band is shifted by k θ (k is 1,2,3 …), and the phase of the phase current high-frequency harmonic is changed, where k depends on a specific PWM modulation method and a harmonic frequency.
Specifically, as shown in fig. 7, fig. 7 is an exemplary schematic diagram of a variation trend of a carrier frequency component of a twelve-phase permanent magnet motor, which is 2 times of the zero-order electromagnetic force, along with a carrier phase shift angle according to an embodiment of the present application. The high-frequency vibration rapid analysis method implemented by the invention respectively calculates the amplitude of 2 times carrier frequency component of zero-order electromagnetic force when the motor shown in figure 5 has different carrier phase shift angles in three carrier phase shift modes. Wherein, single phase means that only one of twelve phase windings is correspondingly phase-shifted by carrier wave, single set means that one set of applied carrier wave phase-shifted is provided for four sets of three-phase windings, and two sets of three-phase windings spaced by 30 degrees of electrical angle are applied to carrier wave phase-shifted. As can be seen, the three curves are axisymmetrical about the "carrier phase shift angle of 90 °" where the electromagnetic force amplitude takes a minimum value. Compared with carrier-free phase shifting, the electromagnetic force amplitudes of the three carrier phase shifting modes are respectively reduced by 16.7%, 50.1% and 99.9%. It can be seen from the above illustration that, two sets of mode carriers are selected to be 90 degrees as the optimal carrier phase shift strategy.
Specifically, as shown in fig. 8, fig. 8 is an exemplary schematic diagram of a variation trend of a carrier frequency component of a twelve-phase permanent magnet motor leg vibration acceleration 2 times with a carrier phase shift angle provided in the embodiment of the present application. As can be seen, the three curves are axisymmetrical about the "carrier phase shift angle of 90 °" where the vibration acceleration amplitude takes a minimum value. Compared with carrier-free phase shifting, the vibration acceleration amplitude is respectively reduced by 23.6%, 51.6% and 96.6%. The variation trends of the zero-order electromagnetic force and the vibration acceleration along with the carrier phase shift angle are highly consistent, the rationality of the high-frequency vibration indirect analysis by selecting the high-frequency component of the zero-order electromagnetic force provided by the application is proved, the correctness of the calculation results of the step S101 and the step S102 in the invention is indirectly proved, and the effectiveness of the optimal carrier phase shift strategy for inhibiting the high-frequency vibration is also proved.
The above description is only an exemplary embodiment of the present disclosure, and the scope of the present disclosure should not be limited thereby. That is, all equivalent changes and modifications made in accordance with the teachings of the present disclosure are intended to be included within the scope of the present disclosure. Embodiments of the present disclosure will be readily apparent to those skilled in the art from consideration of the specification and practice of the disclosure herein. This application is intended to cover any variations, uses, or adaptations of the disclosure following, in general, the principles of the disclosure and including such departures from the present disclosure as come within known or customary practice within the art to which the disclosure pertains. It is intended that the specification and examples be considered as exemplary only, with a true scope and spirit of the disclosure being indicated by the following claims.
Claims (5)
1. A method for rapidly analyzing high-frequency vibration of a multiphase permanent magnet motor is characterized by comprising the following steps:
s1, analyzing and calculating the time domain waveform of the current of the PWM inverter power supply multiphase permanent magnet motor based on the carrier phase shift angle of each inversion unit and the motor working condition of the PWM inverter power supply multiphase permanent magnet motor;
s2, calculating to obtain the time domain waveform of the electromagnetic force applied to each tooth of the motor stator by using a magnetic conductance distribution characteristic function method based on the time domain waveform of the current;
and S3, performing two-dimensional Fourier decomposition on the time domain waveform of the electromagnetic force borne by the motor stator, selecting the high-frequency component of the zero-order electromagnetic force as a reference quantity, and indirectly analyzing the high-frequency vibration of the motor based on the reference quantity.
2. The method according to claim 1, wherein the step S1 includes:
s11, establishing a 3D mathematical model of the inverter output PWM pulse waveform, and establishing a voltage time domain waveform analysis expression;
s12, inputting the carrier phase shift angle of each inversion unit and the motor working condition of the multiphase permanent magnet motor powered by the PWM inverter into the expression to obtain the time domain waveform of the output voltage of the inverter;
and S13, introducing the time domain waveform of the output voltage of the inverter into a multi-phase permanent magnet motor state equation to obtain the time domain waveform of the current of the multi-phase permanent magnet motor supplied by the PWM inverter.
3. The method according to claim 1, wherein the step S2 includes:
s21, calculating to obtain stator surface flux density distribution based on a flux guide distribution characteristic function and the time domain waveform of the multiphase permanent magnet motor current;
and S22, calculating the magnetic density distribution on the surface of the stator by using a Maxwell tensor method to obtain the time domain waveform of the electromagnetic force applied to the tooth part of the stator.
4. The method according to claim 1, wherein the step S3 includes:
s31, performing two-dimensional Fourier decomposition on the time domain waveform of the electromagnetic force borne by the motor stator to obtain the frequency spectrum of each order of electromagnetic force;
and S32, selecting the high-frequency component of the zeroth-order electromagnetic force from the frequency spectrum of each-order electromagnetic force as a reference, and indirectly analyzing the high-frequency vibration based on the reference.
5. A multi-phase permanent magnet motor dither suppression strategy, the suppression strategy comprising the following methods:
s4, setting carrier phase shifting angles of all inversion units, calculating to obtain zero-order electromagnetic force high-frequency components based on the multiphase permanent magnet motor high-frequency vibration rapid analysis method of claims 1-4, and determining the carrier phase shifting angle combination when the amplitude of the zero-order electromagnetic force high-frequency components is minimum as an optimal carrier phase shifting strategy;
and S5, adjusting the PWM carrier phase angle of each phase inversion unit of the motor system to be the carrier phase shift angle combination corresponding to the optimal carrier phase shift strategy.
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| CN113381670A (en) * | 2021-06-07 | 2021-09-10 | 华中科技大学 | Multi-three-phase permanent magnet synchronous motor high-frequency PWM vibration suppression method and system |
| CN114048649A (en) * | 2021-11-09 | 2022-02-15 | 华能澜沧江水电股份有限公司 | Method for weakening low-frequency vibration of stator of hydraulic generator |
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