CN112467989A - Quasi-single-stage high-power-factor alternating current-direct current converter - Google Patents

Quasi-single-stage high-power-factor alternating current-direct current converter Download PDF

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CN112467989A
CN112467989A CN202011181743.5A CN202011181743A CN112467989A CN 112467989 A CN112467989 A CN 112467989A CN 202011181743 A CN202011181743 A CN 202011181743A CN 112467989 A CN112467989 A CN 112467989A
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diode
capacitor
bus
circuit
switching tube
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CN112467989B (en
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谢小高
余岱玲
董汉菁
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Hangzhou Dianzi University
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Hangzhou Dianzi University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4233—Arrangements for improving power factor of AC input using a bridge converter comprising active switches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4241—Arrangements for improving power factor of AC input using a resonant converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Dc-Dc Converters (AREA)
  • Rectifiers (AREA)

Abstract

The invention discloses a quasi-single-stage high-power-factor alternating current-direct current converter, which comprises a Boost PFC circuit and an LLC resonant circuit; multiplexing switch tube S of Boost PFC circuit and LLC resonant circuit1And S2(ii) a The Boost PFC circuit comprises a filter, a rectifying circuit and a power factor correction unit, wherein the rectifying circuit comprises a rectifying bridge and an input capacitor CinThe rectifier bridge comprises four diodes D1～D4(ii) a The power factor correction unit comprises a boost inductor L1And L2Freewheel diode D5And D6And an energy storage capacitor CdSwitch tube S1And S2And bus capacitor Cbus(ii) a The LLC resonant circuit comprises a switching tube S multiplexed with a Boost PFC circuit1And S2Resonant inductor LrResonant vibrationCapacitor CrTransformer TR, output diode D7And D8And output capacitor Co. The bus capacitor of the converter is stable in potential, and the EMI problem can be effectively reduced.

Description

Quasi-single-stage high-power-factor alternating current-direct current converter
Technical Field
The invention belongs to the technical field of switching power supplies, and relates to a quasi-single-stage high-power-factor alternating current-direct current converter.
Background
Due to the existence of nonlinear elements, energy storage elements and the like in the power electronic device, severe pollution can be caused to a public power grid, so that the waveform of input current is severely distorted, and the input power factor at the grid side is low. In order to meet the requirements of the international electrotechnical commission harmonic standard IEC61000-3-2, Power Factor Correction (PFC) technology is applied to these Power electronic devices.
Fig. 1 shows a conventional two-stage Boost-LLC converter, which can achieve a high power factor and a precise bus voltage control, but has a complex overall structure and a large number of components, so that the cost and the design difficulty are increased accordingly.
In consideration of structural characteristics and overall cost, the PFC converter widely applied at present is mainly a quasi-single-stage Boost-LLC converter. As shown in fig. 2, the conventional quasi-single-stage Boost-LLC converter has the advantages of simple structure, less components, etc., but since the Boost circuit is in an open-loop state and the duty ratio is constant at 0.5, the bus voltage V is constantbusThe input voltage is 2 times larger than the peak value of the input voltage, so that the bus voltage is too high when the high voltage is input, the voltage stress of power devices such as a switching tube and the like is increased, the type selection of the power devices is difficult, and the cost is increased; fig. 3 shows another prior art quasi-single-stage Boost-LLC converter, which can reduce the problem of bus voltage being too high, but introduces a serious common mode interference problem due to floating ground at two ends of the bus capacitor.
Disclosure of Invention
In order to solve the problems, the technical scheme of the invention is as follows: a quasi-single-stage high-power-factor alternating current-direct current converter comprises a Boost PFC circuit and an LLC resonant circuit; multiplexing switch tube S of Boost PFC circuit and LLC resonant circuit1And S2(ii) a The Boost PFC circuit comprises a filter, a rectifying circuit and a power factor correction unit, wherein the rectifying circuit comprises a rectifying bridge and an input capacitor CinThe rectifier bridge comprises four diodes D1～D4(ii) a The power factor correction unit comprises a boost inductor L1And L2Freewheel diode D5And D6And an energy storage capacitor CdSwitch tube S1And S2And bus capacitor Cbus(ii) a The LLC resonant circuit comprises a switching tube S multiplexed with a BoostPFC circuit1And S2Resonant inductor LrResonant capacitor CrTransformer TR, output diode D7And D8And output capacitor Co。
Preferably, one input end of the filter is connected with an input alternating current source VacOne end of the input AC source V is connected with the other input end of the input AC sourceacThe other end of (a); one output end of the filter is connected with one input end of the rectifier bridge, and the other output end of the filter is connected with the other input end of the rectifier bridge; diode D1Cathode and diode D3Is connected to the input capacitance CinAs the positive output end of the rectifying circuit, and a diode D2And diode D4Is connected to the input capacitance C and is connected to the anode ofinAs the negative output terminal of the rectifier circuit, and a diode D1And diode D2Are connected together as an input of a rectifier bridge, to an output of a filter, and a diode D3And diode D4Are connected together as the other input terminal of the rectifier bridge and are connected to the other output terminal of the filter.
Preferably, the boost inductor L of the power factor correction unit1One end of the first diode is connected with the positive output end of the rectifying circuit, and the other end of the first diode is connected with a freewheeling diode D5Is connected to the anode of a freewheeling diode D5Is connected to the boost inductor L2One terminal of and an energy storage capacitor CdPositive electrode of (1), boost inductor L2Another terminal of (1) and a freewheeling diode D6Is connected to the anode of a freewheeling diode D6Is connected to the switching tube S1Drain electrode of (2) and bus capacitor CbusPositive electrode of (2), energy storage capacitor CdIs connected to the switching tube S1Source electrode of (1) and switching tube S2Drain electrode of (2), bus capacitor CbusNegative electrode of (2) and switching tube S2Are connected together and are connected to the negative output of the rectifier circuit.
Preferably, a resonant inductance L of the LLC resonant circuitrOne end of the first capacitor is connected to an energy storage capacitor C in the power factor correction unitdAnd the other end of the negative electrode is connected to a resonant capacitor CrOne terminal of (1), a resonance capacitor CrIs connected to one end of the primary side of a transformer TR, the other end of the primary side of the transformer TR being connected to a bus capacitor C in a power factor correction unitbusThe turn ratio of the primary side and the secondary side of the transformer TR is n: 1, wherein the winding method of the secondary side is a winding method with a center tap, and the different name ends at the tap are connected and connected to the output capacitor CoThe homonymous terminals of the two secondary windings are respectively connected to an output diode D7And D8Anode of (2), output diode D7And D8Are connected together to an output capacitor CoPositive electrode of (2), output capacitor CoBoth ends are connected with a load.
Preferably, the boost inductor L of the power factor correction unit1One end of the diode is connected with the negative output end of the rectifying circuit, and the other end of the diode is connected with a freewheeling diode D5Is connected to the cathode of a freewheeling diode D5Is connected to the boost inductor L2One terminal of and an energy storage capacitor CdNegative electrode of (1), boost inductor L2Another terminal of (1) and a freewheeling diode D6Is connected to the cathode of a freewheeling diode D6Is connected to the switching tube S2Source and bus capacitor CbusNegative electrode of (1), energy storage capacitor CdIs connected to the switching tube S1Source electrode of (1) and switching tube S2Drain electrode of (2), bus capacitor CbusAnode and switch tube S1Are connected together and are connected to the positive output terminal of the rectifier circuit.
Preferably, the power factor correction unit further comprises a two-winding coupling inductor TR1, the dotted terminal of the primary winding of the coupling inductor TR1 is connected to the positive output terminal of the rectification circuit, and the dotted terminal is connected to the freewheeling diode D5Is connected to the anode of the secondary winding of the coupling inductor TR1, the synonym terminal of the secondary winding of the coupling inductor TR1 is connected to the freewheeling diode D5Cathode and energy storage capacitor CdThe homonymous terminal of the secondary winding of the coupling inductor TR1 and the freewheeling diode D6Is connected to the anode of a freewheeling diode D6Is connected to the switching tube S1Drain electrode of (2) and bus capacitor CbusPositive electrode of (2), energy storage capacitor CdIs connected to the switching tube S1Source electrode of (1) and switching tube S2Drain electrode of (2), bus capacitor CbusNegative electrode of (2) and switching tube S2Are connected together and are connected to the negative output of the rectifier circuit.
Preferably, the power factor correction unit further comprises a two-winding coupling inductor TR1, the synonym terminal of the primary winding of the coupling inductor TR1 is connected with the negative output terminal of the rectification circuit, and the synonym terminal is connected with the freewheeling diode D5Is connected to the cathode of the secondary winding of the coupling inductor TR1, the dotted terminal of the secondary winding of the coupling inductor TR1 being connected to the freewheeling diode D5Anode and energy storage capacitor CdNegative electrode, alias terminal and freewheeling diode D6Is connected to the cathode of a freewheeling diode D6Is connected to the switching tube S2Source and bus capacitor CbusNegative electrode of (2), bus capacitor CbusPositive electrode of (2) and switching tube S1Are connected together to the positive output end of the rectifying circuit, and an energy storage capacitor CdIs connected to the switching tube S1Source electrode of (1) and switching tube S2The turn ratio of the primary side and the secondary side of the coupling inductor TR1 is m: 1.
compared with the prior art, the invention has the following beneficial effects:
the invention can effectively reduce the bus voltage to about half of that of the traditional quasi-single-stage Boost-LLC converter, reduce the voltage stress of a power device and a bus capacitor and reduce the circuit cost; compared with a quasi-single-stage Boost-LLC converter with low bus voltage in the prior art, the converter has the advantages that the bus capacitor potential is stable, and the EMI problem can be effectively reduced.
Drawings
FIG. 1 is a schematic diagram of a conventional two-stage Boost-LLC topology in the prior art;
FIG. 2 is a schematic diagram of a conventional quasi-single-stage Boost-LLC topology in the prior art;
FIG. 3 is a schematic diagram of a quasi-single-stage Boost-LLC topology of low bus voltage in the prior art;
fig. 4 is a schematic diagram of a topology of a quasi-single-stage high power factor ac-dc converter according to a first embodiment of the present invention;
fig. 5 is a schematic diagram of a topology of a quasi-single-stage high power factor ac-dc converter according to a second embodiment of the present invention;
fig. 6 is a schematic diagram of a topology of a quasi-single-stage high-power-factor ac-dc converter according to a third embodiment of the present invention;
fig. 7 is a schematic diagram of a topology of a quasi-single-stage high power factor ac-dc converter according to a fourth embodiment of the present invention;
FIG. 8 is a simplified equivalent circuit diagram of a quasi-single-stage high power factor AC/DC converter according to a first embodiment of the present invention;
fig. 9 is a partial key waveform diagram of a quasi-single-stage high power factor ac-dc converter according to a first embodiment of the present invention;
fig. 10 is a schematic diagram of an equivalent circuit of a quasi-single-stage high power factor ac-dc converter in a first operating mode according to a first embodiment of the present invention;
fig. 11 is a schematic diagram of an equivalent circuit of a quasi-single-stage high power factor ac-dc converter in a second operating mode according to a first embodiment of the present invention;
fig. 12 is a schematic diagram of an equivalent circuit of a quasi-single-stage high power factor ac-dc converter in a third operating mode according to a first embodiment of the present invention;
fig. 13 is a schematic diagram of an equivalent circuit of a quasi-single-stage high power factor ac-dc converter in a fourth operating mode according to a first embodiment of the present invention;
fig. 14 is an equivalent circuit diagram of a quasi-single-stage high power factor ac-dc converter according to a first embodiment of the present invention in a fifth operating mode;
fig. 15 is an equivalent circuit diagram of a quasi-single-stage high power factor ac-dc converter according to a first embodiment of the present invention in a sixth operating mode;
fig. 16 is an equivalent circuit diagram of a quasi-single-stage high power factor ac-dc converter according to a first embodiment of the present invention in a seventh operating mode;
fig. 17 is an equivalent circuit diagram of a quasi-single-stage high power factor ac-dc converter according to a first embodiment of the present invention in an eighth operating mode;
fig. 18 is a graph of a calculation of an ac input current within a power frequency period of a quasi-single-stage high power factor ac-dc converter according to a first embodiment of the present invention;
fig. 19 is a graph illustrating a relationship between a dc bus voltage and an effective value of an ac input voltage of a quasi-single-stage high power factor ac-dc converter according to an embodiment of the present invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention.
On the contrary, the invention is intended to cover alternatives, modifications, equivalents and alternatives which may be included within the spirit and scope of the invention as defined by the appended claims. Furthermore, in the following detailed description of the present invention, certain specific details are set forth in order to provide a better understanding of the present invention. It will be apparent to one skilled in the art that the present invention may be practiced without these specific details.
Example 1
Referring to fig. 4, the Boost PFC circuit and the LLC resonant circuit are included; multiplexing switch tube S of Boost PFC circuit and LLC resonant circuit1And S2(ii) a The Boost PFC circuit comprises a filter 11, a rectifying circuit and a power factor correction unit, wherein the rectifying circuit comprises a rectifying bridge and an input capacitor CinThe rectifier bridge comprises four diodes D1～D4(ii) a The power factor correction unit comprises a boost inductor L1And L2Freewheel diode D5And D6And an energy storage capacitor CdSwitch tube S1And S2And bus capacitor Cbus(ii) a The LLC resonant circuit comprises a switching tube S multiplexed with a Boost PFC circuit1And S2Resonant inductor LrResonant capacitor CrTransformer TR, output diode D7And D8And output capacitor Co。
One input end of the filter 11 is connected with the input alternating current source VacOne end of the input AC source V is connected with the other input end of the input AC sourceacThe other end of (a); one output end of the filter 11 is connected with one input end of the rectifier bridge, and the other output end is connected with the other input end of the rectifier bridge; diode D1Cathode and diode D3Is connected to the input capacitance CinAs the positive output end of the rectifying circuit, and a diode D2And diode D4Is connected to the input capacitance C and is connected to the anode ofinAs the negative output terminal of the rectifier circuit, and a diode D1And diode D2Are connected together as an input of a rectifier bridge, to an output of the filter 11, and a diode D3And diode D4Are connected together as the other input of the rectifier bridge and are connected to the other output of the filter 11.
Boost inductor L of power factor correction unit1One end of the first diode is connected with the positive output end of the rectifying circuit, and the other end of the first diode is connected with a freewheeling diode D5Is connected to the anode of a freewheeling diode D5Is connected to the boost inductor L2One terminal of and an energy storage capacitor CdPositive electrode of (1), boost inductor L2Another terminal of (1) and a freewheeling diode D6Is connected to the anode of a freewheeling diode D6Is connected to the switching tube S1Drain electrode of (2) and bus capacitor CbusPositive electrode of (2), energy storage capacitor CdIs connected to the switching tube S1Source electrode of (1) and switching tube S2Drain electrode of (2), bus capacitor CbusNegative electrode of (2) and switching tube S2Are connected together and are connected to the negative output of the rectifier circuit.
Resonant inductor L of LLC resonant circuitrOne end of the first capacitor is connected to an energy storage capacitor C in the power factor correction unitdAnd the other end of the negative electrode is connected to a resonant capacitor CrOne terminal of (1), a resonance capacitor CrIs connected to one end of the primary side of the transformer TR, and the other end of the primary side of the transformer TR is connected to workBus capacitor C in rate factor correction unitbusThe turn ratio of the primary side and the secondary side of the transformer TR is n: 1, wherein the winding method of the secondary side is a winding method with a center tap, and the different name ends at the tap are connected and connected to the output capacitor CoThe homonymous terminals of the two secondary windings are respectively connected to an output diode D7And D8Anode of (2), output diode D7And D8Are connected together to an output capacitor CoPositive electrode of (2), output capacitor CoBoth ends are connected with a load.
In order to make the purpose and effect of the present invention clearer, the analysis is performed in an equivalent circuit manner, and for simplicity of the analysis, the boost inductor L is used in this embodiment1And L2The sensitivity ratio m is set to 1.
FIG. 8 is a simplified equivalent circuit diagram of a first embodiment of the quasi-single-stage high power factor AC-DC converter shown in FIG. 4, wherein V isinRepresenting the output voltage of the rectifier circuit, irReplacing an LLC resonant circuit as an equivalent rear-stage load of the Boost PFC circuit, CD5And CD6Respectively, a freewheel diode D5And D6Parasitic capacitance of DS1And DS2Respectively representing switching tubes S1And S2Body diode of (C)S1And CS2Respectively representing switching tubes S1And S2The parasitic capacitance of (2);
FIG. 9 is a partial key waveform diagram of a quasi-single-stage high power factor AC-DC converter according to a first embodiment of the present invention, where Vgs1And Vgs2Respectively representing switching tubes S1And S2Gate voltage of iL1And iL2Respectively representing the current-through boost inductance L1And L2Current of (i)CdRepresenting the current flowing through the energy storage capacitor CdCurrent of (i)S1And iS2Respectively showing the current flowing through the switching tube S1And S2The current of (2).
FIG. 10 is a schematic diagram of a quasi-single-stage high power factor AC-DC converter according to a first operating mode of an equivalent circuit of the quasi-single-stage high power factor AC-DC converter, which corresponds to a part of keys of FIG. 9T in the waveform diagram0-t1A time period. In this operating state, the switching tube S2Off, current iS1Slave switch tube S1Body diode D ofS1By, for a switching tube S1The zero voltage of (1) is turned on to provide a condition, at this time, the current flows through the boost inductor L1Current i ofL1Falls while flowing through the boost inductor L2Current i ofL2Rising and boosting inductor L1Discharging and boosting inductor L2Charging and energy-storing capacitor CdCharging, the loop equation is:
Figure BDA0002750383970000071
wherein, VCdFor an energy-storage capacitor CdVoltage across, VbusIs a bus capacitor CbusThe voltage across the terminals.
Fig. 11 is a schematic diagram of an equivalent circuit of a quasi-single-stage high power factor ac-dc converter in a second operating mode according to an embodiment of the present invention, which corresponds to t in a part of a key waveform diagram of fig. 91-t2A time period. In this operating state, the switching tube S1Zero voltage on, S2Off, current iS1Flow through the switch tube S1In this phase, flows through the boost inductor L1Current i ofL1Falls to 0 while flowing through the boost inductor L2Current i ofL2Continuously rising and boosting inductor L1Discharging and boosting inductor L2Charging and energy-storing capacitor CdThe loop equation is the same as (1) after charging and then discharging.
Fig. 12 is a schematic diagram of an equivalent circuit of a quasi-single-stage high power factor ac-dc converter in a third operating mode according to an embodiment of the present invention, which corresponds to t in a part of a key waveform diagram of fig. 92-t3A time period. In this operating state, the switching tube S1Remains on, S2Off, current iS1Flow through the switch tube S1In this phase, the free-wheeling diode D5Parasitic capacitance C ofD5And a boost winding L1GeneratingSlight resonance, current-through boost inductor L1Current i ofL1 Remains 0 while flowing through the boost inductor L2Current i ofL2Up to a maximum value, boost the inductance L2Charging and energy-storing capacitor CdDischarge, the loop equation is:
Figure BDA0002750383970000081
fig. 13 is a schematic diagram of an equivalent circuit of a quasi-single-stage high power factor ac-dc converter in a fourth operating mode according to an embodiment of the present invention, which corresponds to t in a part of a key waveform diagram of fig. 93-t4A time period. In this operating state, the switching tube S1Off, S2Not yet turned on, current iS1And current iS2Respectively slave switch tube S1And S2Parasitic capacitance C ofS1And CS2Upper pass, to the capacitor CS1Charging and charging capacitor CS2Discharge, in this phase, through the step-up winding L1Current i ofL1Starts to rise and flows through the boost inductor L2Current i ofL2Beginning to fall, boost inductor L1Charging and boosting inductor L2Beginning to discharge, energy storage capacitor CdContinuing to discharge, the loop equation is:
Figure BDA0002750383970000082
fig. 14 is a schematic diagram of an equivalent circuit of a quasi-single-stage high power factor ac-dc converter in a fifth operating mode according to an embodiment of the present invention, which corresponds to t in a part of a key waveform diagram of fig. 94-t5A time period. In this operating state, the switching tube S1Off, current iS2Slave switch tube S2Body diode D ofS2Upper pass, is a switch tube S2The zero voltage of (1) is turned on to provide a condition, at this time, the current flows through the boost inductor L1Current i ofL1Continues to rise while flowing through the boost inductor L2Current i ofL2Continues to descendBoost inductor L1Maintaining the charged state, boosting the inductance L2Continuing to discharge, the energy storage capacitor CdContinuing to discharge, the loop equation is the same as (3).
Fig. 15 is a schematic diagram of an equivalent circuit of a quasi-single-stage high power factor ac-dc converter in a sixth operating mode according to an embodiment of the present invention, which corresponds to t in a part of a key waveform diagram of fig. 95-t6A time period. In this operating state, the switching tube S1Off, S2Zero voltage turn-on, current iS2Slave switch tube S2Flows through the boost winding L1Current i ofL1Continues to rise while flowing through the boost winding L2Current i ofL2Down to 0, boost winding L1Maintaining the state of charge, boosting the winding L2Continuing to discharge, the energy storage capacitor CdThe loop equation is the same as (3) for the transition from the discharged state to the charged state.
Fig. 16 is a schematic diagram of an equivalent circuit of a quasi-single-stage high power factor ac-dc converter in a seventh operating mode according to an embodiment of the present invention, which corresponds to t in a part of a key waveform diagram of fig. 96-t7A time period. In this operating state, the switching tube S1Off, S2Remains on, current iS2Slave switch tube S2In this phase, the free-wheeling diode D6Parasitic capacitance C ofD6And a boost winding L2Generates slight resonance and flows through the boosting winding L1Current i ofL1Rises to a maximum value and simultaneously flows through the boosting winding L2Current i ofL2Held at 0, the voltage-boosting winding L1Keeping the charging state, an energy storage capacitor CdThe state of charge is maintained, and the loop equation is:
Figure BDA0002750383970000091
fig. 17 is a schematic diagram of an equivalent circuit of a quasi-single-stage high power factor ac-dc converter in an eighth operating mode according to an embodiment of the present invention, which corresponds to t in a part of a key waveform diagram of fig. 97-t8A time period. In this operating state, the switching tube S2Off, S1Not yet turned on, current iS1And current iS2Respectively slave switch tube S1And S2Parasitic capacitance C ofS1And CS2Upper pass, to the capacitor CS1Discharge and to the capacitor CS2Charging, in this phase, through the step-up winding L1Current i ofL1Begins to fall while flowing through the boost winding L2Current i ofL2Start to rise, boost winding L1Starting discharge, boosting winding L2Beginning to charge, energy storage capacitor CdThe charging is continued, and the loop equation is the same as (1).
From the above circuit analysis, it can be known that the switch tube S is switched in the whole working period1And S2Zero voltage conduction can be realized, i.e. soft switching is realized.
According to the volt-second equilibrium law of inductance, one can obtain:
Figure BDA0002750383970000092
Figure BDA0002750383970000101
according to the fundamental wave equivalent analysis method, the gain expression of the LLC resonant circuit can be obtained as follows:
Figure BDA0002750383970000102
wherein, VoTo output a voltage, LnIs an excitation inductance LmAnd a resonant inductor LrRatio of (i.e. L)n＝Lm/Lr，frIs the resonant frequency, fsTo the operating frequency, QeIs the quality factor of the LLC resonant circuit.
According to equation (6) and the power conservation rule, it can be obtained:
Figure BDA0002750383970000103
wherein L isBoostFor the step-up winding L1And L2Inductance value of, PoIs the output power.
According to equations (5) and (6) and the inductance volt-second equilibrium rule, the expression of the input current can be obtained as follows:
Figure BDA0002750383970000104
according to the formula (9), an alternating input current i can be obtainedacAs shown in fig. 18. It can be seen that the ac input current waveform is very close to sinusoidal, with a very high power factor.
According to the equations (7) and (8) and the numerical solution, the expressions of the bus voltage and the input voltage can be obtained as follows:
Figure BDA0002750383970000105
from equation (10), the input voltage V can be obtainedinAnd bus voltage VbusFIG. 19 is a graph showing the relationship of (A) to (B). It can be seen that the bus voltage is much lower than 2 times the peak input voltage over the full voltage input range.
Example 2
Referring to fig. 5, the filter 11, the rectifying circuit and the LLC resonant circuit are the same as those in the previous embodiment, and are not described again. Boost inductor L of power factor correction unit1One end of the diode is connected with the negative output end of the rectifying circuit, and the other end of the diode is connected with a freewheeling diode D5Is connected to the cathode of a freewheeling diode D5Is connected to the boost inductor L2One terminal of and an energy storage capacitor CdNegative electrode of (1), boost inductor L2Another terminal of (1) and a freewheeling diode D6Is connected to the cathode of a freewheeling diode D6Is connected to the switching tube S2OfElectrode and bus capacitor CbusNegative electrode of (1), energy storage capacitor CdIs connected to the switching tube S1Source electrode of (1) and switching tube S2Drain electrode of (2), bus capacitor CbusAnode and switch tube S1Are connected together and are connected to the positive output terminal of the rectifier circuit.
Example 3
Referring to fig. 6, the filter 11, the rectifying circuit and the LLC resonant circuit are the same as those in the previous embodiment, and are not described again. The power factor correction unit also comprises a two-winding coupling inductor TR1, the homonymous terminal of the primary winding of the coupling inductor TR1 is connected with the positive output terminal of the rectification circuit, and the synonym terminal is connected with a freewheeling diode D5Is connected to the anode of the secondary winding of the coupling inductor TR1, the synonym terminal of the secondary winding of the coupling inductor TR1 is connected to the freewheeling diode D5Cathode and energy storage capacitor CdThe homonymous terminal of the secondary winding of the coupling inductor TR1 and the freewheeling diode D6Is connected to the anode of a freewheeling diode D6Is connected to the switching tube S1Drain electrode of (2) and bus capacitor CbusPositive electrode of (2), energy storage capacitor CdIs connected to the switching tube S1Source electrode of (1) and switching tube S2Drain electrode of (2), bus capacitor CbusNegative electrode of (2) and switching tube S2Are connected together and are connected to the negative output of the rectifier circuit.
Example 4
Referring to fig. 7, the filter 11, the rectifying circuit and the LLC resonant circuit are the same as those in the previous embodiment, and are not described again. The power factor correction unit also comprises a two-winding coupling inductor TR1, the different name end of the primary winding of the coupling inductor TR1 is connected with the negative output end of the rectification circuit, the same name end is connected with a freewheeling diode D5Is connected to the cathode of the secondary winding of the coupling inductor TR1, the dotted terminal of the secondary winding of the coupling inductor TR1 being connected to the freewheeling diode D5Anode and energy storage capacitor CdNegative electrode, alias terminal and freewheeling diode D6Is connected to the cathode of a freewheeling diode D6Is connected to the switching tube S2Source and bus capacitor CbusNegative electrode of (2), bus capacitor CbusPositive electrode of (2) and switching tube S1Are connected together to the positive input of the rectifier circuitOutput terminal, energy storage capacitor CdIs connected to the switching tube S1Source electrode of (1) and switching tube S2The turn ratio of the primary side and the secondary side of the coupling inductor TR1 is m: 1.
the invention includes specific modules that can be implemented in a variety of ways or in various combinations to form different embodiments without departing from the spirit of those skilled in the art, and will not be described in detail herein.
However, that no matter how detailed the foregoing appears, or how many embodiments of the invention may be practiced, the present invention is described in detail as illustrative embodiments thereof. All equivalent changes and modifications made according to the spirit of the present invention should be covered within the protection scope of the present invention.
The foregoing detailed description of the embodiments of the invention is not intended to be exhaustive or to limit the invention to the precise form disclosed. While specific embodiments of, and examples for, the invention are described above for illustrative purposes, various equivalent modifications are possible within the scope of the invention, as those skilled in the relevant art will recognize.
While the above description describes certain embodiments of the invention and describes the best mode contemplated, no matter how detailed the above appears in text, the invention can be practiced in many ways. The details of the above-described circuit configuration and manner of controlling the same may vary considerably in its implementation details, yet still be encompassed by the invention disclosed herein.
As noted above, it should be noted that the use of particular terminology when describing certain features or aspects of the invention should not be taken to imply that the terminology is being re-defined herein to be restricted to certain specific characteristics, features, or aspects of the invention with which that terminology is associated. In general, the terms used in the following claims should not be construed to limit the invention to the specific embodiments disclosed in the specification, unless the above detailed description section explicitly defines such terms. Accordingly, the actual scope of the invention encompasses not only the disclosed embodiments, but also all equivalent ways of practicing or implementing the invention under the claims.
The above description is only for the purpose of illustrating the preferred embodiments of the present invention and is not to be construed as limiting the invention, and any modifications, equivalents and improvements made within the spirit and principle of the present invention are intended to be included within the scope of the present invention.

Claims (7)

1. A quasi-single-stage high-power-factor AC-DC converter is characterized by comprising a Boost PFC circuit and an LLC resonant circuit; multiplexing switch tube S of Boost PFC circuit and LLC resonant circuit1And S2(ii) a The Boost PFC circuit comprises a filter, a rectifying circuit and a power factor correction unit, wherein the rectifying circuit comprises a rectifying bridge and an input capacitor CinThe rectifier bridge comprises four diodes D1～D4(ii) a The power factor correction unit comprises a boost inductor L1And L2Freewheel diode D5And D6And an energy storage capacitor CdSwitch tube S1And S2And bus capacitor Cbus(ii) a The LLC resonant circuit comprises a switching tube S multiplexed with a Boost PFC circuit1And S2Resonant inductor LrResonant capacitor CrTransformer TR, output diode D7And D8And output capacitor Co。
2. The quasi-single stage high power factor ac-dc converter according to claim 1, wherein an input of the filter is connected to an input ac source VacOne end of the input AC source V is connected with the other input end of the input AC sourceacThe other end of (a); one output end of the filter is connected with one input end of the rectifier bridge, and the other output end of the filter is connected with the other input end of the rectifier bridge; diode D1Cathode and diode D3Is connected to the input capacitance CinAs the positive output end of the rectifying circuit, and a diode D2And diode D4Is connected to the input capacitance C and is connected to the anode ofinAs the negative output terminal of the rectifier circuit, and a diode D1And diode D2The cathode of the anode is connected with the cathode of the cathode,a diode D connected to an output terminal of the filter and serving as an input terminal of the rectifier bridge3And diode D4Are connected together as the other input terminal of the rectifier bridge and are connected to the other output terminal of the filter.
3. The quasi-single-stage high power factor ac-dc converter according to claim 2, wherein the boost inductor L of the pfc unit1One end of the first diode is connected with the positive output end of the rectifying circuit, and the other end of the first diode is connected with a freewheeling diode D5Is connected to the anode of a freewheeling diode D5Is connected to the boost inductor L2One terminal of and an energy storage capacitor CdPositive electrode of (1), boost inductor L2Another terminal of (1) and a freewheeling diode D6Is connected to the anode of a freewheeling diode D6Is connected to the switching tube S1Drain electrode of (2) and bus capacitor CbusPositive electrode of (2), energy storage capacitor CdIs connected to the switching tube S1Source electrode of (1) and switching tube S2Drain electrode of (2), bus capacitor CbusNegative electrode of (2) and switching tube S2Are connected together and are connected to the negative output of the rectifier circuit.
4. The quasi-single-stage high power factor AC-DC converter according to claim 3, wherein the resonant inductor L of the LLC resonant circuitrOne end of the first capacitor is connected to an energy storage capacitor C in the power factor correction unitdAnd the other end of the negative electrode is connected to a resonant capacitor CrOne terminal of (1), a resonance capacitor CrIs connected to one end of the primary side of a transformer TR, the other end of the primary side of the transformer TR being connected to a bus capacitor C in a power factor correction unitbusThe turn ratio of the primary side and the secondary side of the transformer TR is n: 1, wherein the winding method of the secondary side is a winding method with a center tap, and the different name ends at the tap are connected and connected to the output capacitor CoThe homonymous terminals of the two secondary windings are respectively connected to an output diode D7And D8Anode of (2), output diode D7And D8Are connected together to an outputCapacitor CoPositive electrode of (2), output capacitor CoBoth ends are connected with a load.
5. The quasi-single-stage high power factor ac-dc converter according to claim 2, wherein the boost inductor L of the pfc unit1One end of the diode is connected with the negative output end of the rectifying circuit, and the other end of the diode is connected with a freewheeling diode D5Is connected to the cathode of a freewheeling diode D5Is connected to the boost inductor L2One terminal of and an energy storage capacitor CdNegative electrode of (1), boost inductor L2Another terminal of (1) and a freewheeling diode D6Is connected to the cathode of a freewheeling diode D6Is connected to the switching tube S2Source and bus capacitor CbusNegative electrode of (1), energy storage capacitor CdIs connected to the switching tube S1Source electrode of (1) and switching tube S2Drain electrode of (2), bus capacitor CbusAnode and switch tube S1Are connected together and are connected to the positive output terminal of the rectifier circuit.
6. The quasi-single-stage high power factor AC-DC converter according to claim 2, wherein the power factor correction unit further comprises a two-winding coupling inductor TR1, the dotted terminal of the primary winding of the coupling inductor TR1 is connected to the positive output terminal of the rectification circuit, and the dotted terminal is connected to a freewheeling diode D5Is connected to the anode of the secondary winding of the coupling inductor TR1, the synonym terminal of the secondary winding of the coupling inductor TR1 is connected to the freewheeling diode D5Cathode and energy storage capacitor CdThe homonymous terminal of the secondary winding of the coupling inductor TR1 and the freewheeling diode D6Is connected to the anode of a freewheeling diode D6Is connected to the switching tube S1Drain electrode of (2) and bus capacitor CbusPositive electrode of (2), energy storage capacitor CdIs connected to the switching tube S1Source electrode of (1) and switching tube S2Drain electrode of (2), bus capacitor CbusNegative electrode of (2) and switching tube S2Are connected together and are connected to the negative output of the rectifier circuit.
7. According to the claimsThe quasi-single-stage high-power-factor AC-DC converter obtained in the solution 2 is characterized in that the power factor correction unit further comprises a two-winding coupling inductor TR1, the different name end of the primary winding of the coupling inductor TR1 is connected with the negative output end of the rectification circuit, the same name end of the primary winding of the coupling inductor TR1 is connected with the negative output end of the rectification circuit, and a freewheeling diode D is connected with the same name end of the primary5Is connected to the cathode of the secondary winding of the coupling inductor TR1, the dotted terminal of the secondary winding of the coupling inductor TR1 being connected to the freewheeling diode D5Anode and energy storage capacitor CdNegative electrode, alias terminal and freewheeling diode D6Is connected to the cathode of a freewheeling diode D6Is connected to the switching tube S2Source and bus capacitor CbusNegative electrode of (2), bus capacitor CbusPositive electrode of (2) and switching tube S1Are connected together to the positive output end of the rectifying circuit, and an energy storage capacitor CdIs connected to the switching tube S1Source electrode of (1) and switching tube S2The turn ratio of the primary side and the secondary side of the coupling inductor TR1 is m: 1.
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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2023207442A1 (en) * 2022-04-25 2023-11-02 上海安世博能源科技有限公司 Power circuit and power adapter

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN104158243A (en) * 2014-08-05 2014-11-19 华为技术有限公司 Uninterruptible power supply circuit and control method thereof
CN107041036A (en) * 2017-04-27 2017-08-11 福州大学 A kind of single-stage LED drive circuit of integrated bridgeless Boost and LLC circuits
CN107222100A (en) * 2017-06-12 2017-09-29 福州大学 A kind of integrated Buck Boost and LLC circuits single-stage LED drive circuit
CN108235509A (en) * 2017-12-29 2018-06-29 福州大学 A kind of single-stage LED drive circuit of integrated decompression Cuk and LLC circuits

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN104158243A (en) * 2014-08-05 2014-11-19 华为技术有限公司 Uninterruptible power supply circuit and control method thereof
CN107041036A (en) * 2017-04-27 2017-08-11 福州大学 A kind of single-stage LED drive circuit of integrated bridgeless Boost and LLC circuits
CN107222100A (en) * 2017-06-12 2017-09-29 福州大学 A kind of integrated Buck Boost and LLC circuits single-stage LED drive circuit
CN108235509A (en) * 2017-12-29 2018-06-29 福州大学 A kind of single-stage LED drive circuit of integrated decompression Cuk and LLC circuits

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
HONGBO MA 等: "A High-Efficiency Quasi-Single-Stage Bridgeless Electrolytic Capacitor-Free High-Power AC–DC Driver for Supplying Multiple LED Strings in Parallel", 《TRANSACTIONS ON POWER ELECTRONICS》 *
黄冬艳 等: "一种无光耦隔离的低成本、小体积LED驱动器", 《中国照明电器》 *

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2023207442A1 (en) * 2022-04-25 2023-11-02 上海安世博能源科技有限公司 Power circuit and power adapter

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