CN112366962B - Three-phase three-level rectifier based on three-winding isolation transformer - Google Patents

Three-phase three-level rectifier based on three-winding isolation transformer Download PDF

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CN112366962B
CN112366962B CN202011210924.6A CN202011210924A CN112366962B CN 112366962 B CN112366962 B CN 112366962B CN 202011210924 A CN202011210924 A CN 202011210924A CN 112366962 B CN112366962 B CN 112366962B
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phase
winding
isolation transformer
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inductor
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CN112366962A (en
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丁明远
贲洪奇
孙凯
赵志强
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Harbin Institute of Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/2173—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a biphase or polyphase circuit arrangement

Abstract

A three-phase three-level rectifier based on a three-winding isolation transformer solves the problems of complex structure and control of the existing three-switch Sepic type three-phase three-level rectifier, and belongs to the field of three-level rectifier topology. The three-winding isolation transformer is applied to an aviation power supply and comprises three input filter inductors a, three energy storage capacitors, three-winding isolation transformers, three groups of bidirectional switches, six power diodes and two output filter capacitors; the invention adopts simple circuit structure and control to realize better power factor correction effect function, effectively reduces the output lower limit of output voltage, and effectively reduces the voltage stress of a switching tube in the circuit by introducing the three-winding isolation transformer. The problem of reverse mutation of current does not exist when the input current is zero; meanwhile, when the input voltage passes through zero, the voltage at two ends of the energy storage capacitor is negative, and even in the stage that the input voltage does not exceed the voltage of the energy storage capacitor, the charging of the input filter inductor cannot be influenced.

Description

Three-phase three-level rectifier based on three-winding isolation transformer
Technical Field
The invention relates to a novel three-phase three-level rectifier based on a three-winding isolation transformer, and belongs to the field of three-level rectifier topologies.
Background
The multi-level rectifier has the advantages of less current harmonic content, lower voltage stress borne by a switching device and the like, and shows excellent application prospect. The VIENNA rectifier is a typical three-level topology, has a simple circuit structure, and is widely applied to the field of high-voltage and high-power factor correction.
In order to ensure the normal operation of the VIENNA rectifier, the output voltage of the VIENNA rectifier is required to be more than twice of the maximum value of the input voltage, so that the VIENNA rectifier cannot be directly applied in occasions with wide output voltage regulation range (such as 115V/400Hz of three-phase input of an aviation power supply and voltage level requirements of 270V output constant voltage), and a DC/DC conversion circuit is generally required to be cascaded behind the VIENNA rectifier to realize wide voltage output.
In view of the advantages of a Sepic PFC converter with a wide output voltage regulation range and a small input current THD, a three-switch Sepic three-phase three-level rectifier and a combined three-phase PFC converter based on a Sepic-type isolating transformer are mainly proposed for three-phase input.
Compared with a VIENNA rectifier, the three-switch Sepic type three-phase three-level rectifier effectively reduces the lower output limit of output voltage, but the practical application of the three-phase three-level rectifier is limited by the defects brought by the complex circuit structure of the three-switch Sepic type three-phase three-level rectifier. Each path adopts two energy storage capacitors, and a loop is easily formed with an output capacitor, so that a larger loop current is caused; the voltage at two ends of the energy storage capacitor is the sum of the input voltage and the output voltage of 1/2, so that the voltage stress of the switching tube is larger; the charge and discharge process of the two energy storage capacitors when the input current flows through zero needs to be considered when the control loop is designed. The above-mentioned drawbacks result in a rectifier that has a poor operational reliability and a complex control, while the rectifier is not electrically isolated.
The combined three-phase PFC converter based on the Sepic type band isolation transformer realizes the electrical isolation and the reduction of the lower limit of the output voltage, but the converter adopts more semiconductor power devices, and the loss of the converter seriously influences the efficiency of the converter under the condition of low input voltage; meanwhile, zero-crossing distortion exists in the input current of the converter, and the higher the grid frequency is, the more serious the zero-crossing distortion is; in addition, the circuit parameters of the converter are sensitive to the fluctuation of the power grid frequency, the allowable parameter change range is small, the frequency disturbance resistance is poor, and the application of the converter in occasions with wide power grid frequency change range (such as the change of the aviation power grid frequency from 360Hz to 800 Hz) is limited.
Disclosure of Invention
Aiming at the problems of complex structure and control of the conventional three-switch Sepic type three-phase three-level rectifier, the invention provides a three-phase three-level rectifier based on a three-winding isolation transformer, which has a simple structure and is easy to control.
The invention discloses a three-phase three-level rectifier based on a three-winding isolation transformer, which is applied to an aviation power supply, and comprises three input filter inductors a, three energy storage capacitors, three-winding isolation transformers, three groups of bidirectional switches, six power diodes and two output filter capacitors; each phase of input power supply is respectively connected with an input filter inductor a and a group of bidirectional switches in series in sequence, the tail ends of the three groups of bidirectional switches are connected together, the connection point is an O point, and the central line of the three-phase input power supply is connected with the O point; each energy storage capacitor is connected in series with a primary winding of a three-winding isolation transformer and is connected in parallel with a group of bidirectional switches after being connected in series; each one of which isThe secondary side of the three-winding isolation transformer comprises an upper winding and a lower winding, the homonymous ends of the upper windings of the three-winding isolation transformers are connected together, and the connection point is X1Point, the homonymous ends of the lower windings of the three-winding isolation transformers are connected together, and the connection point is X2Point, the synonym end of the upper winding of each three-winding isolation transformer is connected with the cathode of a power diode, the synonym end of the lower winding of each three-winding isolation transformer is connected with the anode of a power diode, other cathodes and anodes of six power diodes are connected together, the connection point is M point, and two output filter capacitors are respectively connected in series with X point1Point to point M and X2Between points and M points.
The invention also provides a three-phase three-level rectifier based on the three-winding isolation transformer, which is applied to an aviation power supply, wherein the three-phase three-level rectifier comprises three input filter inductors a, three energy storage capacitors, three-winding isolation transformers, three groups of bidirectional switches, six power diodes and two output filter capacitors; each phase of input power supply is respectively connected with an input filter inductor a and a group of bidirectional switches in series in sequence, and the tail ends of the three groups of bidirectional switches are connected together; each energy storage capacitor is connected in series with a primary winding of a three-winding isolation transformer and is connected in parallel with a group of bidirectional switches after being connected in series; each secondary side of the three-winding isolation transformer comprises an upper winding and a lower winding, the homonymous ends of the upper windings of the three-winding isolation transformers are connected together, and the connection point is X1Point, the homonymous ends of the lower windings of the three-winding isolation transformers are connected together, and the connection point is X2The dotted terminal of the upper winding of each three-winding isolation transformer is connected with the cathode of a power diode, the dotted terminal of the lower winding of each three-winding isolation transformer is connected with the anode of a power diode, other cathodes and anodes of six power diodes are connected together, the connection point is an M point, and two output filter capacitors are respectively connected in series between the X1 point and the M point and between the X1 point and the M point, and the X filter capacitors are respectively connected in series2Between points and M points.
The invention also provides a three-phase three-level rectifier based on the three-winding isolation transformer, which comprises three inductors b on the basis of the two three-phase three-level rectifiers, wherein the primary winding of each three-winding isolation transformer is connected with one inductor b in parallel.
The invention also provides a three-phase three-level rectifier based on the three-winding isolation transformer, and on the basis of a third three-phase three-level rectifier, an input filter inductor a and an inductor b which are positioned on the same phase are coupled together.
The three-phase three-level rectifier has the advantages that a better power factor correction effect function can be realized by adopting a simple circuit structure and control, and the lower output limit of output voltage is effectively reduced. The advantages of the circuit topology are mainly shown in that: compared with 3 switching tubes and 18 diodes of a three-switch Sepic type three-phase three-level rectifier and 3 switching tubes and 15 diodes of a combined three-phase PFC converter based on a Sepic type isolating transformer, the semiconductor power device used is reduced, the topology only adopts 6 switching tubes and 6 diodes, the number of the diodes is obviously reduced, and the loss on the power device is effectively reduced.
The problem that zero-crossing distortion exists in input current is effectively solved from the circuit structure. For the combined three-phase Sepic PFC converter, because the input filter inductive current has a hysteresis phenomenon, when the input voltage passes through zero, the inductive current does not drop to 0, and the input current has reverse mutation when the input voltage passes through zero due to the existence of the input side rectifier bridge; meanwhile, the voltage of the energy storage capacitor has a hysteresis phenomenon, and the voltage at two ends of the energy storage capacitor is not 0 when the input voltage passes through zero, so that the input filtering inductive current of the input voltage is basically unchanged within a period of time which does not exceed the voltage of the energy storage capacitor. In the rectifier topology, a rectifier bridge does not exist, so that the problem of reverse sudden change of current does not exist when the input current is zero; meanwhile, when the input voltage passes through zero, the voltage at two ends of the energy storage capacitor is negative, and even in the stage that the input voltage does not exceed the voltage of the energy storage capacitor, the charging of the input filter inductor cannot be influenced.
In addition, the voltage stress of a switching tube in the circuit is effectively reduced due to the introduction of the three-winding isolation transformer, the rectifier does not have the problem of diode reverse recovery, and the rectifier has the advantages of electrical isolation, good working reliability and suitability for occasions with wide frequency variation range of a power grid.
Drawings
FIG. 1 is a circuit diagram of a three-phase four-wire system three-phase three-level rectifier based on a three-winding isolation transformer; FIG. 2 is a circuit diagram of a three-phase three-wire system novel three-phase three-level rectifier based on a three-winding isolation transformer; FIG. 3 is a circuit diagram of a single-phase three-level rectifier according to the present invention; FIG. 4 is a waveform of the circuit operation of a single-phase (A-phase) three-level rectifier during a switching cycle; FIG. 5 is a diagram of the working mode of a single-phase (A-phase) three-level rectifier under different states, including the mode e in FIG. 5(a)A>0, the bidirectional switch is turned on, e is shown in FIG. 5(b)A>0, the bidirectional switch is turned off, and e is shown in FIG. 5(c)A<0, the bidirectional switch is turned on, e is shown in FIG. 5(d)A<0, the bidirectional switch is turned off; FIG. 6 is a diagram of a division of three-phase input voltage into different operating ranges, with the ordinate u representing voltage and the abscissa t representing operating time; FIG. 7 shows the input voltage at [0, π/6]The circuit working waveform of the three-phase three-level rectifier in one switching period in the interval; wherein, fig. 7(a) shows a three-phase input filter inductor La1、Lb、LcVoltage and current waveform diagrams, and FIG. 7(b) shows three excitation inductances Lm1、Lm2、Lm3A voltage current waveform diagram; FIG. 8 shows the input voltage at [0, π/6] for different switch states]A working mode diagram of the novel three-phase three-level rectifier in an interval, wherein fig. 8(a) is a working mode diagram of a working process (1), fig. 8(b) is a working mode diagram of a working process (2), fig. 8(c) is a working mode diagram of a working process (3), fig. 8(d) is a working mode diagram of a working process (4), and fig. 8(e) is a working mode diagram of a working process (5); FIG. 9 shows the input voltage at [0, π/6]The equivalent circuits of the novel three-phase three-level rectifier in different working processes in the interval are shown in fig. 9(a) as the equivalent circuit of the working process (1), fig. 9(b) as the equivalent circuit of the working process (2), fig. 9(c) as the equivalent circuit of the working process (3), and fig. 9(d) as the equivalent circuit of the working process (4)Fig. 9(e) is an equivalent circuit of the working process (5); FIG. 10 is a diagram showing waveforms of three-phase input voltage and current under a condition of inputting 115V/400Hz and outputting 270V constant voltage, wherein in FIG. 10, the upper diagram shows a voltage waveform diagram and the lower diagram shows a current waveform diagram; fig. 11 is a comparison graph of zero-crossing condition of input current under the conditions of three-phase input 115V/400Hz and output 270V constant voltage, the left graph shows the condition of a combined three-phase PFC converter based on a Sepic-type strip isolation transformer, and the right graph shows the condition of adopting the rectifier of the invention. FIG. 12 is a circuit diagram of a three-phase three-wire rectifier incorporating coupled inductors; FIG. 13 is a circuit diagram of a single phase three level rectifier incorporating a coupled inductor; FIG. 14 is a diagram of the working mode of an improved single-phase three-level rectifier with coupling inductors introduced in different states, wherein e is shown in FIG. 14(a)A>0, charging phase with bidirectional switch on, 14(b) eA<0, charging stage with the bidirectional switch turned on, 14(c) is eA>0, discharge phase of the bidirectional switch off, 14(d) eA<0, a discharge stage of turning off the bidirectional switch; 14(e) is eA>0, free-wheeling phase of the bidirectional switch off, 14(f) eA<0, a follow current stage of turning off the bidirectional switch; fig. 15 shows the input waveform of the three-phase three-level rectifier of embodiment 1, where L is 3.174mH and L ism95.22 muh; FIG. 16 is an input waveform L of a three-phase three-level rectifier of embodiment 21＝250μH，L295 muH, and 90 muH; fig. 17 is a circuit diagram of a three-phase three-wire rectifier incorporating a primary side parallel inductance b; fig. 18 is a circuit diagram of a three-phase four-wire rectifier incorporating a primary side parallel inductor b; fig. 19 is a circuit diagram of a three-phase four-wire rectifier incorporating coupled inductors.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention. It should be noted that the embodiments and features of the embodiments may be combined with each other without conflict. The invention is further described with reference to the following drawings and specific examples, which are not intended to be limiting.
The three-phase three-level rectifier based on the three-winding isolation transformer of the embodiment comprises three input filter inductors, wherein the three input filter inductors are respectively La1、La2、La3Three small-capacity energy-storage capacitors, each being C1、C2、C3Three-winding isolation transformers, each being T1、T2、T3Three sets of reverse series power switch tubes (first set S)a1、Sa2(ii) a Second group Sb1、Sb2(ii) a Third group Sc1、Sc2) Six power diodes and two output filter capacitors C on the DC sideo1、Co2. The inductance values of the three input filter inductors are the same, the capacitance values of the three small-capacity energy storage capacitors are the same, the capacitance values of the two output filter capacitors are the same, the three-winding isolation transformers are completely the same (the excitation inductors are the same in size and the transformation ratios are all n:1:1), and the three excitation inductors are L respectivelym1、Lm2、Lm3. Each group of the reverse series switch tubes has the same switching action and is equivalent to a bidirectional switch, so that bidirectional flow of energy can be realized, control is simplified, and the volume of the whole rectifier can be reduced.
The three-phase three-level rectifier based on the three-winding isolation transformer in the embodiment realizes a good power factor correction effect of an input side and effective reduction of an output voltage lower limit by introducing the three-winding isolation transformer and adopting a small number of semiconductor power devices. The rectifier circuit has the advantages of simple structure, no problems of zero-crossing distortion of input current and reverse recovery of a diode, easiness in control, electrical isolation, good reliability, anti-interference capability and the like.
The circuit structure of the rectifier can be divided into a three-phase three-wire system and a three-phase four-wire system according to whether a neutral wire exists in a three-phase input power supply or not.
Example 1: a three-phase four-wire three-level rectifier, as shown in FIG. 1, includes three outputsInput filter inductor La1、La2、La3Three energy storage capacitors C1、C2、C3Three-winding isolation transformer T1、T2、T3Three groups of two-way switches (first group S)a1、Sa2(ii) a Second group Sb1、Sb2(ii) a Third group Sc1、Sc2) Six power diodes and two output filter capacitors Co1、Co2；
Each phase of input power supply is respectively connected with an input filter inductor and a group of bidirectional switches in series in sequence, the tail ends of the three groups of bidirectional switches are connected together, the connection point is an O point, and the central line of the three-phase input power supply is connected with the O point;
each energy storage capacitor is connected in series with a primary winding of a three-winding isolation transformer and is connected in parallel with a group of bidirectional switches after being connected in series;
each secondary side of the three-winding isolation transformer comprises an upper winding and a lower winding, the homonymous ends of the upper windings of the three-winding isolation transformers are connected together, and the connection point is X1Point, the homonymous ends of the lower windings of the three-winding isolation transformers are connected together, and the connection point is X2Point, the synonym end of the upper winding of each three-winding isolation transformer is connected with the cathode of a power diode, the synonym end of the lower winding of each three-winding isolation transformer is connected with the anode of a power diode, the residual cathodes and the anodes of the six power diodes are connected together, the connection point is M point, and two output filter capacitors are respectively connected in series with X point1Point to point M and X2Between points and M points;
when a three-phase four-wire system is adopted, the neutral line of a three-phase input power supply is connected with the point O, the direct decoupling of the three-phase input is realized, and the three-phase input can be regarded as a single-phase three-level rectifier with three paths of outputs connected in parallel. Because of the three-phase power balance, the load resistance is 3R for each phaseLI.e. output current is io/3. Each of the three-phase three-level rectifiers of the present embodiment operates independently, and as shown in fig. 3, before analyzing the operating principle of the single-phase three-level rectifier, the following is madeDescription of the drawings:
1) the adopted components are ideal, the input filter inductor works in CCM, and the secondary side diode of the transformer works in DCM;
2) output filter capacitor Co1、Co2Sufficiently large and with equal voltage division between the two capacitors, i.e.
Co1＝Co2
Figure BDA0002758797480000061
3) The switching frequency is far greater than the grid frequency, and the switching period TcThe input voltage and the voltage of the energy storage capacitor are considered to be constant values.
Taking phase A as an example, according to the input voltage eAIn the positive and negative half cycles and the switching state of the bidirectional switch, the single-phase three-level rectifier can be divided into six different working modes, and the working principle of each mode is detailed as follows:
(1)eA>0 (i.e. positive half cycle of ac voltage), bidirectional switch (S)a1、Sa2) Conduction of
As shown in fig. 5(a), the input filter inductance La1Subject to a forward voltage equal to the input voltage eAThe inductor current rises linearly in the forward direction, La1Energy is stored. Excitation inductance Lm1The voltage at two ends is equal to the voltage u of the energy storage capacitorC1And an energy storage capacitor C1To excitation inductance Lm1Discharge, Lm1Energy is stored. Filter capacitor Co1、Co2Discharged, collectively providing energy to the load.
(2)eA>0 (i.e. positive half cycle of ac voltage), bidirectional switch (S)a1、Sa2) Switch off
As shown in fig. 5(b), the input filter inductance La1A voltage across eA-uC1-nUo/2<0, forward linear decrease of inductor current, La1Releasing energy; excitation inductance Lm1The voltage at two ends is nUo/2，Lm1The reference direction of the voltage is opposite to the current, Lm1Releasing energy;the upper winding on the secondary side of the three-winding isolation transformer works, the current of the diode connected in series with the upper winding is linearly reduced from the peak value, and when the current flows through La1Current of and flows through Lm1When the currents are equal, the diode is turned off. At this time, AC power supply eAInput filter inductor La1And an energy storage capacitor C1And an excitation inductance Lm1Forming a low frequency oscillation loop, since the switching frequency is much higher than the low frequency oscillation frequency, the phase can be considered as iAAnd iLm1A constant-current stage with equal size and keeping unchanged.
(3)eA<0 (i.e. negative half cycle of ac voltage), bidirectional switch (S)a1、Sa2) Conduction of
As shown in fig. 5(c), the input filter inductance La1Subject to a reverse voltage equal to the input voltage eAThe inductor current rises in a reverse linear manner, La1Energy is stored. Excitation inductance Lm1The voltage at two ends is equal to the voltage u of the energy storage capacitorC1And an energy storage capacitor C1To excitation inductance Lm1Discharge, Lm1Energy is stored. Filter capacitor Co1、Co2Discharged, collectively providing energy to the load.
(4)eA<0 (i.e. negative half cycle of ac voltage), bidirectional switch (S)a1、Sa2) Switch off
As shown in fig. 5(d), the input filter inductance La1A voltage across eA-uC1+nUo/2>0, reverse linear decrease of inductor current, LaReleasing energy; excitation inductance Lm1The voltage at two ends is nUo/2，Lm1The reference direction of the voltage is opposite to the current, Lm1Releasing energy; the lower winding on the secondary side of the three-winding isolation transformer works, the current of the diode connected in series with the lower winding is linearly reduced from the peak value, and when the current flows through La1Current of and flows through Lm1When the currents are equal, the diode is turned off. At this time, AC power supply eAInput filter inductor La1And an energy storage capacitor C1And an excitation inductance Lm1Forming a low frequency oscillation loop, since the switching frequency is much higher than the low frequency oscillation frequency, the phase can be considered as iAAnd iLm1A constant-current stage with equal size and keeping unchanged.
From the above analysis it can be seen that there is an input side freewheeling stage during each switching cycle, when L isa1And Lm1The voltage at both ends is 0, so that the voltage u of the energy storage capacitor can be knownC1And an input voltage eAEqual, i.e. uC1＝eA. Diode current i connected with secondary side of three-winding isolation transformer at turn-off time of bidirectional switchVD-peak＝n(iA-peak+iLm1-peak) Can be represented as
Figure BDA0002758797480000071
Wherein L represents the inductance value of the input filter inductor, LmThe inductance value of the exciting inductance is represented.
Diode current i in the switching cycleVDCan be expressed as
Figure BDA0002758797480000072
The expression of the input current is obtained from the conservation of the input and output power under ideal conditions.
Figure BDA0002758797480000073
It can be seen that at L, LmAnd when the duty ratio d is fixed, the input current can automatically track the input voltage to change in a sine rule, the same phase of the input current and the input voltage is ensured, and a control circuit is greatly simplified.
Unlike the single-phase model of the VIENNA rectifier, the single-phase model inputs a voltage across the filter inductor of
Figure BDA0002758797480000074
So that at | eA|max>UoThe stage circuit of/2 can still be normalThe lower limit of the output side voltage is effectively lowered.
Example 2: a three-phase three-wire three-level rectifier, as shown in FIG. 2, includes three input filter inductors La1、La2、La3Three energy storage capacitors C1、C2、C3Three-winding isolation transformer T1、T2、T3Three groups of two-way switches (first group S)a1、Sa2(ii) a Second group Sb1、Sb2(ii) a Third group Sc1、Sc2) Six power diodes and two output filter capacitors Co1、Co2；
Each phase of input power supply is respectively connected with an input filter inductor and a group of bidirectional switches in series in sequence, and the tail ends of the three groups of bidirectional switches are connected together;
each energy storage capacitor is connected in series with a primary winding of a three-winding isolation transformer and is connected in parallel with a group of bidirectional switches after being connected in series;
each secondary side of the three-winding isolation transformer comprises an upper winding and a lower winding, the homonymous ends of the upper windings of the three-winding isolation transformers are connected together, and the connection point is X1Point, the homonymous ends of the lower windings of the three-winding isolation transformers are connected together, and the connection point is X2Point, the synonym end of the upper winding of each three-winding isolation transformer is connected with the cathode of a power diode, the synonym end of the lower winding of each three-winding isolation transformer is connected with the anode of a power diode, the residual cathodes and the anodes of the six power diodes are connected together, the connection point is M point, and two output filter capacitors are respectively connected in series with X point1Point to point M and X2Between points and M points;
when a three-phase three-wire system is adopted, the neutral line of a three-phase input power supply is not led out, and the three phases are coupled. Neglecting the voltage drop across the input filter inductor can be obtained
Figure BDA0002758797480000081
Under balanced three-phase input conditions, eA+eB+e C0, from this point on
Figure BDA0002758797480000082
Figure BDA0002758797480000083
Since the coefficient matrix is a singular matrix, there are no sets of solutions, and one set of solutions can be expressed as
Figure BDA0002758797480000084
Substituting the above equation to obtain k1When being any real number, k 21. Value k1＝0，k 21. Thus obtaining
Figure BDA0002758797480000085
Figure BDA0002758797480000086
Under the group of values, the O point is virtually connected with the N point, and the three-phase three-wire system can be equivalent to a three-phase four-wire system. The previous analysis of the three-phase four-wire system circuit shows that a better power factor correction effect can be realized when the duty ratio d is fixed.
The duty ratio d is fixed, and the circuit working condition and the three-phase input voltage e of the novel three-phase three-level rectifierA、eB、eCThe positive and negative and the size of the three-way bidirectional switch are related to the switch state of the three-way bidirectional switch. A power grid cycle is divided into 12 intervals according to the polarity relation of three-phase input voltage, and the power grid is characterized in that the size relation of positive and negative values and absolute values of each phase voltage is unchanged. In the interval [0, π/6]For example, | eAAlways minimum, | eBAlways the maximum, | specifically explains the working condition of the circuit.
(1) As shown in fig. 8(a), when all three groups of bidirectional switches are turned on, the A, C-phase input filter inductor La1、La3Forward charging, B phase input filter inductor La2And (4) reverse charging. Energy storage capacitor C1、C2、C3Respectively exciting inductance Lm1、Lm2、Lm3And (4) discharging. FIG. 9(a) shows a further equivalent circuit at this stage, from which can be derived
Figure BDA0002758797480000087
Figure BDA0002758797480000091
(2) As shown in fig. 8(b), the three sets of bidirectional switches are all turned off, and the three-phase input filter inductor current and the three sets of exciting currents reach their peak values, that is, the three sets of bidirectional switches are turned off
Figure BDA0002758797480000092
A. C-phase input filter inductor La1、La3Forward discharge, B-phase input filter inductor La2Reverse discharge; three groups of excitation inductors Lm1、Lm2、Lm3The voltage at both ends is nUoAnd/2, the reference direction of the voltage is opposite to the current, and the three groups of excitation inductors release energy. A. The winding on the secondary side of the C-phase three-winding isolation transformer works, the current of a series diode of the isolation transformer is linearly reduced from the peak value to a filter capacitor Co1And the load provides energy; the lower winding of the secondary side of the B-phase three-winding isolation transformer works, the current of a series diode of the B-phase three-winding isolation transformer is linearly reduced from the peak value to a filter capacitor Co2And the load provides energy, a further equivalent circuit for this stage is given in fig. 9 (b).
(3) As shown in fig. 8(c), in consideration of thisThe A-phase voltage value in the input voltage interval is minimum, the stored energy is less, therefore, the diode current at the secondary side of the A-phase three-winding isolation transformer firstly drops to 0 during the turn-off period of the bidirectional switch tube, and the A-phase flows through L at the momentaCurrent of and flows through Lm1Are equal. Since the switching frequency is much higher than the low-frequency oscillation frequency, the a-phase current enters the follow current stage first by neglecting the influence of the low-frequency oscillation. While the B, C phases still transfer energy to the load side through their respective three-winding isolation transformers, a further equivalent circuit for this stage is shown in fig. 9 (c).
(4) As shown in fig. 8(d), the secondary side diode current of the C-phase three-winding isolation transformer drops to 0 during the a-phase continuous current, and the C-phase flows through LcCurrent of and flows through Lm3Are equal. Still neglecting the effect of low frequency oscillations, phase C current enters the freewheel phase second. While phase B still transfers energy to the load side through its three-winding isolation transformer, a further equivalent circuit for this stage is shown in fig. 9 (d).
(5) As shown in fig. 8(e), since the B-phase voltage value in the input voltage interval is the largest and the stored energy is more, the diode current at the secondary side of the B-phase three-winding isolation transformer finally drops to 0 during the turn-off period of the bidirectional switch tube, and at this time, the three-phase currents all enter the freewheeling stage, and fig. 9(e) shows a further equivalent circuit at this stage.
In the stage of continuous current at three-phase input side, each phase inputs filter inductor La1、La2、La3And three excitation inductances Lm1、Lm2、Lm3The voltages at two ends are both 0, so that the voltages u of the three energy storage capacitors can be knownC1、uC2、uC3And three-phase input voltage eA、eB、eCAre equal, i.e.
Figure BDA0002758797480000101
From the above analysis, it can be seen that at the turn-off time of the bidirectional switch, the secondary side diode current of each phase of the three-winding isolation transformer reaches the peak value iVDx-peakCan be represented as
Figure BDA0002758797480000102
The equivalent circuit of the working process (2) is combined to know that the stage inputs the filter inductor La1、La2、La3And three excitation inductances Lm1、Lm2、Lm3The voltage across can be expressed as
Figure BDA0002758797480000103
The diode current connected at the secondary side of the three-winding isolation transformer per phase can be expressed as
Figure BDA0002758797480000104
Considering L>>LmNeglecting the current variation on each phase of input filter inductor, the above formula can be simplified as
Figure BDA0002758797480000105
At the end of the phase, the diode current on the secondary side of the A-phase three-winding isolation transformer drops to 0, and then the freewheeling phase is entered. Thus obtaining the secondary side diode current i of the A-phase three-winding isolation transformer in the switching periodVDaAverage value of (a).
Figure BDA0002758797480000111
The equivalent circuit of the working process (3) is combined to know that the stage inputs the filter inductor La1And excitation inductance Lm1Follow current, at this time, input filter inductance La2、La3And an excitation inductance Lm2、Lm3The voltage across can be expressed as
Figure BDA0002758797480000112
Considering L>>LmIgnoring the variation of current on the B, C phase input filter inductor, the B, C phase three winding isolation transformer secondary diode current can be expressed as
Figure BDA0002758797480000113
In the formula, t2The duration of the working process (2).
At the end of the phase, the diode current on the secondary side of the C-phase three-winding isolation transformer drops to 0, and then the freewheeling phase is entered. Thus obtaining the secondary side diode current i of the C-phase three-winding isolation transformer in the switching periodVDcAverage value of (a).
Figure BDA0002758797480000114
The equivalent circuit of the working process (4) is combined to know that the stage inputs the filter inductor La1And excitation inductance Lm1Input filter inductor La3And excitation inductance Lm3Follow current, at this time, input filter inductance La2And an excitation inductance Lm2The voltage across can be expressed as
Figure BDA0002758797480000115
Figure BDA0002758797480000116
Considering L>>LmNeglecting the current change on the B-phase input filter inductor, the current of the secondary side diode of the B-phase three-winding isolation transformer can be expressed as
Figure BDA0002758797480000117
In the formula, t2For the duration of the working process (2), t3The duration of the working process (3).
At the end of the phase, the diode current on the secondary side of the B-phase three-winding isolation transformer drops to 0, and then the freewheeling phase is entered. Thus obtaining the secondary side diode current i of the B-phase three-winding isolation transformer in the switching periodVDbAverage value of (a).
Figure BDA0002758797480000121
The working conditions of other intervals are similar to the [0, pi/6 ] interval, the average value of the secondary side diode current of the three-phase three-winding isolation transformer can be also deduced, and the expression of the three-phase input current is obtained according to the conservation of the input and output power under the ideal condition.
Figure BDA0002758797480000122
It can be seen that at L, LmAnd when the duty ratio d is fixed, the three-phase input current of the three-phase three-wire system rectifier can automatically track the input voltage of each phase to change in a sine rule, and ensures that the input voltage of each phase and the input voltage of each phase have the same phase, so that a control circuit of the rectifier is greatly simplified, and the operation stability of the rectifier is improved.
In order to ensure that the secondary side diode of the transformer works in DCM, the circuit parameters of the embodiment 1 and the embodiment 2 need to be limited.
And combining the input current expression to obtain an instantaneous value of the input power.
Figure BDA0002758797480000123
In the formula of UmIs the peak value of the input voltage.
The input power instantaneous value can be integrated with time in a half power grid period
Figure BDA0002758797480000124
In consideration of input-output power conservation, it is possible to obtain
Figure BDA0002758797480000125
In the formula, PoIs the output power.
Thereby obtaining a relation between the system duty ratio d and each circuit parameter.
Figure BDA0002758797480000126
If the secondary side diode of the transformer works in the critical state between CCM and DCM, the secondary side diode of the transformer works in the critical state
Figure BDA0002758797480000131
Omega is the angular frequency of the power grid, T is the time, TcIs a switching cycle;
when the input voltage is at the peak (sin ω t 1), d takes the maximum value. Meanwhile, after the input voltage and the output voltage are determined, the maximum value of the system duty ratio d is related to the transformer transformation ratio n, and the larger n is, the larger the maximum value of d is. However, when the transformer transformation ratio n is designed, the design value of the transformation ratio n cannot be too large in consideration of the fact that the transformer secondary side current is significantly increased with the increase of the transformation ratio n, and the transformer secondary side diode has large current stress.
After the maximum duty cycle is determined, the two inductances L, L are adjustedmAnd (5) designing.
The main consideration for the design of the input filter inductor L is the magnitude of the current ripple of the input current. From the previous theoretical analysis, the current ripple of the filter inductor L is
Figure BDA0002758797480000132
Thereby obtaining a value formula of the filter inductor L.
Figure BDA0002758797480000133
Figure BDA0002758797480000134
In the formula, α is a current ripple coefficient.
After the input filter inductance L is determined, the excitation inductance L is obtained according to the duty ratio expressionmThe size of (2). Considering L>>LmExcitation inductance LmCan be approximately expressed as
Figure BDA0002758797480000135
From the above formula, the excitation inductance L is determined at a constant input voltage peak, output power and switching periodmSize and d of2The filter inductance L is in direct proportion to d/alpha, so that the inductance parameter of the circuit can be determined after the duty ratio d and the ripple factor alpha are determined. At this time, the maximum value of the switching tube current is
Figure BDA0002758797480000136
It can be seen that, when the output power and the switching period are fixed, the current stress of the switching tube is mainly related to the excitation inductance LmDirect correlation, increasing LmCan effectively reduce the current stress of the switch tube, and LmSubject to the maximum duty cycle d of the systemmaxThe limit of (2). Taking three-phase input voltage 115V/400Hz, output constant voltage 270V and output power 1500W of the aviation power supply as an example, circuit parameters are carried outDesign description of the numbers.
The transformer transformation ratio n is 2, and the switching frequency is 50 kHz. Determination of the maximum duty cycle:
Figure BDA0002758797480000141
the duty cycle d is taken to be 0.6.
And taking the input current ripple coefficient alpha as 0.1, and determining the input filter inductance L.
Figure BDA0002758797480000142
Finally, for the required excitation inductance LmA determination is made.
Figure BDA0002758797480000143
It has been found that the design values of the two inductors are generally large (especially the input filter inductors) in order to achieve low ripple of the input current and effectively reduce the current stress of the switching tube. Considering that the exciting current of the transformer is very small in practice, the exciting inductance is generally large, and considering the uncontrollable property of the exciting inductance in the manufacturing process of the transformer, in order to ensure the normal operation of the circuit, an inductance b is usually added on the primary side of the transformer, as shown in fig. 17. At this time have
Figure BDA0002758797480000144
In the formula, LbIs the inductance value of a primary side parallel inductor b of the transformer, L'mThe inductance value of the exciting inductor of the transformer used in practice.
In order to further optimize the circuit, the coupling inductor is considered to replace the input filter inductor and the transformer primary side parallel inductor b in the embodiment, so that the current ripple of the input current is effectively reduced and the current stress of the switching tube is reduced under the condition of lower self-inductance and mutual inductance values, and the circuit optimization method is implementedAnd the reduction of the inductor volume and the improvement of the power density of the rectifier are realized. The circuit structure of the improved novel three-level rectifier with the introduction of the coupling inductor can be divided into a three-phase three-wire system and a three-phase four-wire system according to whether a neutral line exists in a three-phase input power supply or not. On the basis of the embodiments 1 and 2, the three-phase inductor further comprises three inductors b which are L respectivelyb1、Lb2、Lb3The primary winding of each three-winding isolation transformer is connected with an input filter inductor b in parallel, and the input filter inductor a and the transformer parallel inductor b which are positioned in the same phase are coupled together;
example 3: this embodiment is a three-phase three-wire system three-phase three-level rectifier circuit diagram based on a three-winding isolation transformer improved on the basis of embodiment 2, as shown in fig. 12.
Taking the single-phase model as an example, as shown in fig. 13, the influence of the coupling inductance on the circuit is specifically analyzed. Because of the three-phase power balance, the load resistance is 3R for each phaseLI.e. output current is io/3。La1And Lb1The self-inductance of the coupled inductor is L1、L2Mutual inductance of M (L)1>M、L2>M). Considering that the input side freewheeling stage exists in each switching period, the voltage u of the energy storage capacitorC1And an input voltage eAEqual, i.e. uC1＝eA. The very small excitation current of the transformer is ignored during the analysis.
Two-way switch (S)a1、Sa2) When conducting, the port voltage of the coupling inductor can be expressed as
Figure BDA0002758797480000151
Thus, can obtain
Figure BDA0002758797480000152
At this time iLlIs linearly rising, L1Storing energy; i.e. iL2Is linearly rising, L2Energy is stored. Filter capacitor Co1、Co2Discharged, collectively providing energy to the load.
Two-way switch (S)a1、Sa2) When the terminal is turned off, the voltage of the coupling inductor can be expressed as
Figure BDA0002758797480000153
Thus, can obtain
Figure BDA0002758797480000154
At this time iLlLinearly decreases, L1Releasing energy; i.e. iL2Linearly decreases, L2Energy is released. The secondary winding of the transformer works, the current of the secondary side series diode is linearly reduced from the peak value when iLl＝-iL2And when the current is not enough, the diode is turned off and enters a follow current stage.
It can be seen from the port voltage formula of the coupling inductor that the introduction of the coupling inductor mainly affects the slope of the current change thereof. When the bidirectional switch is turned off, the current i of the secondary side diode of the transformerVD-peak＝n(iL1-peak+iL2-peak) Can be represented as
Figure BDA0002758797480000155
Diode current i in the switching cycleVDCan be expressed as
Figure BDA0002758797480000161
The expression of the input current is obtained from the conservation of the input and output power under ideal conditions.
Figure BDA0002758797480000162
It can be seen that, when the coupling inductance parameter and the duty ratio d are fixed, the input current can automatically track the input voltage to change in a sine rule, and ensure that the input voltage and the input voltage have the same phase, the control circuit is greatly simplified, and the introduction of the coupling inductance does not affect the PFC effect of the input side.
Theoretical analysis on a single-phase model shows that the introduction of the coupling inductance mainly affects iL1、iL2The charging and discharging slope of the inductor has no influence on the working mode of the circuit, so that the coupling inductor is introduced into a three-phase structure, the working principle of the circuit is basically unchanged, and the three-phase input current can be expressed as
Figure BDA0002758797480000163
When the parameters of the coupling inductance are designed, the main influence i of the parameters is consideredL1、iL2Has a charging and discharging slope of (1) and thus has
Figure BDA0002758797480000164
From this quantitative relationship, it can be seen that the closer M is to L2，L1The smaller the inductance value of (c).
The system duty cycle d is still limited to
Figure BDA0002758797480000165
The duty ratio d is still equal to 0.6, the input current ripple factor alpha is equal to 0.1, and the maximum value of the current of the switching tube is considered to be
Figure BDA0002758797480000166
Thereby obtaining the inductance parameter of the coupling inductor.
Figure BDA0002758797480000171
When the coupling inductor is not adopted, the inductance parameters of the two inductors are L, 3.174mH and Lm95.22 muh. Through comparison of inductance values, the inductance value (especially the input filter inductance) required by the circuit can be obviously reduced by introducing the coupling inductance under the condition of ensuring that the input current ripple and the current stress of the switching tube are the same, the size of the inductance is effectively reduced, and the power density of the circuit is improved.
Considering the influence of the excitation inductance of the transformer in practice, the design formula of the parameters can be corrected into the formula when the parameters of the coupling inductance are designed under practical application
Figure BDA0002758797480000172
At this time, the maximum value of the switching tube current is
Figure BDA0002758797480000173
Although the invention herein has been described with reference to particular embodiments, it is to be understood that these embodiments are merely illustrative of the principles and applications of the present invention. It is therefore to be understood that numerous modifications may be made to the illustrative embodiments and that other arrangements may be devised without departing from the spirit and scope of the present invention as defined by the appended claims. It should be understood that features described in different dependent claims and herein may be combined in ways different from those described in the original claims. It is also to be understood that features described in connection with individual embodiments may be used in other described embodiments.

Claims (9)

1. A three-phase three-level rectifier based on a three-winding isolation transformer is characterized by being applied to an aviation power supply and comprising three input filter inductors a, three energy storage capacitors, three-winding isolation transformers, three groups of bidirectional switches, six power diodes and two output filter capacitors;
each phase of input power supply is respectively connected with an input filter inductor a and a group of bidirectional switches in series in sequence, the tail ends of the three groups of bidirectional switches are connected together, the connection point is an O point, and the central line of the three-phase input power supply is connected with the O point;
each energy storage capacitor is connected in series with a primary winding of a three-winding isolation transformer and is connected in parallel with a group of bidirectional switches after being connected in series;
each secondary side of the three-winding isolation transformer comprises an upper winding and a lower winding, the homonymous ends of the upper windings of the three-winding isolation transformers are connected together, and the connection point is X1Point, the homonymous ends of the lower windings of the three-winding isolation transformers are connected together, and the connection point is X2Point, the synonym end of the upper winding of each three-winding isolation transformer is connected with the cathode of a power diode, the synonym end of the lower winding of each three-winding isolation transformer is connected with the anode of a power diode, other cathodes and anodes of six power diodes are connected together, the connection point is M point, and two output filter capacitors are respectively connected in series with X point1Point to point M and X2Between points and M points.
2. A three-phase three-level rectifier based on a three-winding isolation transformer is characterized by being applied to an aviation power supply and comprising three input filter inductors a, three energy storage capacitors, three-winding isolation transformers, three groups of bidirectional switches, six power diodes and two output filter capacitors;
each phase of input power supply is respectively connected with an input filter inductor a and a group of bidirectional switches in series in sequence, and the tail ends of the three groups of bidirectional switches are connected together;
each energy storage capacitor is connected in series with a primary winding of a three-winding isolation transformer and is connected in parallel with a group of bidirectional switches after being connected in series;
each secondary side of the three-winding isolation transformer comprises an upper winding and a lower winding, the homonymous ends of the upper windings of the three-winding isolation transformers are connected together, and the connection point is X1Point, three and three windingsThe homonymous ends of the lower windings of the group isolation transformer are connected together, and the connection point is X2Point, the synonym end of the upper winding of each three-winding isolation transformer is connected with the cathode of a power diode, the synonym end of the lower winding of each three-winding isolation transformer is connected with the anode of a power diode, other cathodes and anodes of six power diodes are connected together, the connection point is M point, and two output filter capacitors are respectively connected in series with X point1Point to point M and X2Between points and M points.
3. A three-phase three-level rectifier based on a three-winding isolation transformer according to claim 1 or 2,
Figure FDA0003229183930000011
Figure FDA0003229183930000021
Figure FDA0003229183930000022
where d is the duty cycle, L is the inductance of the input filter inductor a, and L ismInductance value of exciting inductor, UmFor the peak value of the input voltage, UoFor output voltage, n is the transformation ratio of the three-winding isolation transformer, omega is the angular frequency of the power grid, T is time, TcFor a switching period, PoTo output power, α is the input current ripple factor.
4. The three-phase three-level rectifier based on the three-winding isolation transformer as claimed in claim 1 or 2, wherein the three-phase three-level rectifier further comprises three inductors b, and the primary winding of each three-winding isolation transformer is connected in parallel with one inductor b.
5. The three-phase three-level rectifier based on the three-winding isolation transformer as claimed in claim 4, wherein the input filter inductor a and the input filter inductor b located in the same phase are coupled together.
6. A three-phase three-level rectifier based on a three-winding isolation transformer according to claim 5,
Figure FDA0003229183930000023
L1、L2respectively representing the self inductance of an input filter inductor a and an inductor b connected in parallel on the primary side of the three-winding isolation transformer, and W representing the mutual inductance of the input filter inductor a and the inductor b connected in parallel on the primary side of the three-winding isolation transformer; l is the inductance of the input filter inductor a when uncoupled, LmThe inductance value of the excitation inductor is required when the excitation inductor is not coupled;
maximum value d of duty ratio dmaxThe limiting conditions are as follows:
Figure FDA0003229183930000024
Umfor the peak value of the input voltage, UoIs output voltage, and n is the transformation ratio of the three-winding isolation transformer;
maximum value of switching tube current in bidirectional switch
Figure FDA0003229183930000025
TcFor a switching period, PoIs the output power.
7. A three-phase three-level rectifier based on a three-winding isolation transformer according to claim 5,
Figure FDA0003229183930000031
L1、L2respectively representing the self inductance of an input filter inductor a and an inductor b connected in parallel on the primary side of the three-winding isolation transformer, and W representing the mutual inductance of the input filter inductor a and the inductor b connected in parallel on the primary side of the three-winding isolation transformer; l is the inductance of the input filter inductor a when uncoupled, LmL 'as an inductance value of an exciting inductor required when not coupled'mRepresenting the inductance, L, of the exciting inductance of the transformer used in practicebThe inductance value of the inductor b when the inductor b is not coupled;
maximum value d of duty ratio dmaxThe limiting conditions are as follows:
Figure FDA0003229183930000032
Umfor the peak value of the input voltage, UoIs output voltage, and n is the transformation ratio of the three-winding isolation transformer;
maximum value of switching tube current in bidirectional switch
Figure FDA0003229183930000033
TcFor a switching period, PoIs the output power.
8. The three-phase three-level rectifier based on the three-winding isolation transformer of claim 7, wherein the input filter inductor a operates in an inductor current continuous operation mode, capacitance values of two output filter capacitors are equal and are large enough, voltage division of the two output filter capacitors is equal, a switching frequency is much larger than a grid frequency, and an input voltage of the input power supply and a voltage of the energy storage capacitor are constant values in a switching period.
9. The three-phase three-level rectifier based on the three-winding isolation transformer as claimed in claim 7, wherein the bidirectional switch is implemented by two switching tubes connected in series in an opposite direction.
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