CN112217294A - Non-communication constant current control method applied to bidirectional wireless power transmission circuit - Google Patents

Non-communication constant current control method applied to bidirectional wireless power transmission circuit Download PDF

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CN112217294A
CN112217294A CN202010839420.4A CN202010839420A CN112217294A CN 112217294 A CN112217294 A CN 112217294A CN 202010839420 A CN202010839420 A CN 202010839420A CN 112217294 A CN112217294 A CN 112217294A
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resonant cavity
secondary side
bridge arm
frequency
current
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CN112217294B (en
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张东博
陈敏
李博栋
陈宁
汪小青
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Zhejiang University ZJU
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/80—Circuit arrangements or systems for wireless supply or distribution of electric power involving the exchange of data, concerning supply or distribution of electric power, between transmitting devices and receiving devices

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Abstract

The invention relates to the field of wireless power transmission system application, and aims to provide a communication-free constant current control method applied to a bidirectional wireless power transmission circuit. The invention combines the characteristics of two control schemes based on relative phase shift angle detection and reactive power detection, after the working frequency of the system is stable, the relative phase shift angle of the original secondary bridge arm can be maintained at a fixed value, at the moment, the secondary side carries out synchronous rectification according to the detected polarity of the output current of the resonant cavity, namely, the phase information of the secondary bridge arm relative to the primary bridge arm is obtained, and then the internal phase shift angle of the secondary bridge arm is adjusted to adjust the output power. The method can avoid the condition that the relative phase shift angle of the primary side and the secondary side is different from the theoretical value caused by the parameter error of the system, and has better robustness; active and reactive detection is not needed, and no additional hardware is needed; simple structure and low loss. The invention solves the problem that the transmission active power is 0 due to the deviation of the working frequency of the original secondary side, has no reactive closed loop of PI regulation, has no reactive flow in the whole process, and has quick system response.

Description

Non-communication constant current control method applied to bidirectional wireless power transmission circuit
Technical Field
The invention relates to a communication-free constant current control method applied to a bidirectional wireless power transmission circuit, relates to constant current control of a bidirectional wireless charging system, belongs to the field of application of wireless power transmission systems, relates to bidirectional flow of electric energy, and simultaneously relates to multiple application occasions, in particular to dispatching management of the electric energy, and belongs to the field of power industry.
Background
In the use of electric energy, the traditional power supply realizes the electric energy transmission through a cable, but the wired connection can bring the problems of cable aging, interface abrasion and the like, the reliability and the safety of the power supply are reduced, and meanwhile, the power supply is extremely inconvenient when the cable is used in the environments of some special working conditions such as seabed, mine, space and the like. The wearing and tearing and the corruption of abominable operating mode, interface can let security greatly reduced, and two-way wireless charging has characteristics of no cable, contactless, also has the advantage that the energy can two-way flow, improves security, convenience and the flexibility of charging greatly, also can realize a lot of special applications, if: the portable devices are charged mutually to deal with emergency situations, the mine robots are charged mutually to prolong the endurance and the like.
In order to achieve uniformity and symmetrical characteristics in control, the circuit structures of the primary side and the secondary side of the bidirectional wireless power transmission system are generally the same, the primary side and the secondary side are provided with controllable H bridges, the control units are mutually independent, and the control strategies used in the conventional bidirectional wireless charging mainly comprise an additional DC-DC circuit, phase shift angle control and frequency conversion control.
Compared with an additional DC-DC circuit and frequency conversion control, the phase shift angle control has the advantages of simple hardware structure, low cost and low loss, but in order to ensure that the reactive power in the system is 0, the phase difference of the original secondary side bridge arm needs to be kept at +/-90 degrees, and wireless communication of the original secondary side is needed for constant current control and the requirement on the relative phase shift angle of the original secondary side. In addition, the inconsistent primary and secondary frequencies can make the transmission power of the system be 0, the wireless communication delay is high, the interference of high-frequency electromagnetic fields is easy, and the safety and the stability of the system can be reduced.
In the existing strategy for solving the communication problem, the scheme based on the phase shift angle detection has poor robustness, and the scheme based on the active detection and the reactive detection has a complex hardware structure, so that a communication-free control scheme with simple structure, good robustness and quick response is required.
Disclosure of Invention
The technical problem to be solved by the invention is to overcome the defects in the prior art and provide a communication-free constant current control method applied to a bidirectional wireless power transmission circuit.
In order to solve the technical problem, the invention provides a communication-free constant current control method applied to a bidirectional wireless power transmission circuit, which is characterized by comprising the following steps of:
(1) in a resonant cavity wireless charging circuit, a primary side is at a preset initial frequency f0Carrying out full-bridge inversion; the MOS switch tube on the secondary side is fully turned off and works in an uncontrolled rectification state;
(2) the primary side controller samples input voltage and current of the primary side resonant cavity and then obtains a square wave signal representing polarity through processing of the comparator; measuring the time interval of the two rising edges and calculating the phase difference
Figure BDA0002640885210000021
According to a specified phase difference phisThe difference value between the two signals is used for regulating the frequency of the inversion of the primary side bridge arm through a PI (proportional integral) so as to track the frequency of the resonance point; at the same time will
Figure BDA0002640885210000023
And phisThe difference between the two is compared with the allowable control error value phi _ max if
Figure BDA0002640885210000022
Stopping frequency modulation, otherwise repeating the step (2) to continue frequency modulation;
(3) the secondary side controller detects whether the frequency of the resonant cavity input current is stable, and if so, the step (4) is carried out; otherwise, repeating the step (3) to continue the detection;
(4) the secondary side controller samples input current of the secondary side resonant cavity and then obtains a square wave signal representing polarity through processing of the comparator; detecting secondary resonant cavity input current (i.e. secondary resonant inductor L)2Medium current) as the switching frequency of the secondary side bridge arm; secondary sideThe controller detects the rising edge of the current polarity signal, namely the zero crossing point of the resonant cavity input current, and the secondary side controller outputs a driving signal at the rising edge to carry out synchronous rectification on the secondary side bridge arm;
(5) secondary controller detection system output current IoCalculating to obtain the output power PoObtaining PoThe secondary side controller adjusts the phase shift angle theta in the secondary side bridge arm through feedback according to the difference value of the specified output power P _ refs；
(6) And (3) detecting the rising edge of the current polarity signal by the secondary side controller, namely detecting the zero crossing point of the resonant cavity input current, integrally shifting the phase of the secondary side bridge arm at the rising edge to ensure that the phase of the fundamental wave of the resonant cavity input voltage is the same as the phase of the detected current, and then returning to the step (5).
In the invention, a resonant cavity with constant current source property is used in a resonant cavity wireless charging circuit, namely, the output current of a secondary resonant cavity is related to the input voltage of a primary resonant cavity and is unrelated to the input voltage of a secondary resonant cavity; the resonant cavity is any one of an SS resonance compensation network, a double-LCC resonance compensation network or a double-LCL resonance compensation network.
In the present invention, in the step (3), the method for detecting whether the frequency of the resonant cavity input current is stable includes: sampling the input current of the secondary resonant cavity to obtain a square wave signal representing the polarity, detecting the rising edge of the obtained polarity signal by a secondary controller, and measuring the time between two rising edges as t, wherein the current frequency of the resonant cavity is 1/t; continuously detecting the current frequency of the resonant cavity for a plurality of times (the continuous detection times can be adjusted according to the actual situation), and solving the difference value f _ c between the maximum value and the minimum value; specifying a maximum measurement frequency fluctuation range f _ max allowed when the frequency is stable, and if f _ c is less than or equal to f _ max, judging that the system frequency is stable; if f _ c > f _ max, the system has not reached steady state.
In the invention, the resonant cavity wireless charging circuit is a double-LCC resonant cavity wireless charging circuit, and a secondary side full bridge of the resonant cavity wireless charging circuit comprises a third bridge arm and a fourth bridge arm which are connected in parallel; the third bridge arm comprises a fifth switching tube Q5 and a seventh switching tube Q7 which are connected in series, and the fourth bridge arm comprises a sixth switching tube Q6 and an eighth switching tube Q8 which are connected in series; a third node C is arranged between the fifth switching tube Q5 and the seventh switching tube Q7, the third node C is electrically connected to one end of the secondary side of the LCC resonant cavity, a fourth node D is arranged between the sixth switching tube Q6 and the eighth switching tube Q8, and the fourth node D is electrically connected to the other end of the secondary side of the LCC resonant cavity;
in the step (5), when the system output power P is detected0<When the output power P _ ref is given, the secondary side bridge arm adjusts the internal phase angle theta when the active power is adjusteds＝θs-1; when P is present0>P _ ref, θs＝θs+ 1; secondary side bridge arm internal shift angle thetasThe adjusting method comprises the following steps: on the basis of the integral phase of the secondary side bridge arm determined when the zero crossing point of the input current of the secondary side resonant cavity is detected, the phases of the fifth switching tube Q5 and the seventh switching tube Q7 are advanced by thetas/2, the phase lag θ between the sixth switch tube Q6 and the eighth switch tube Q8s/2。
In the invention, in the step (6), the integral phase shift angle of the secondary bridge arm is adjusted without using a reactive power detection mode PI, the secondary bridge arm detects the rising edge of the resonant cavity input current polarity signal in each control period, and the integral phase shift angle of the secondary bridge arm is synchronized at a zero-crossing point, namely, the phase shift enables the fundamental wave phase of the input voltage of the secondary resonant cavity to be the same as the current phase.
Compared with the prior art, the invention has the beneficial effects that:
(1) the invention combines the characteristics of two control schemes based on relative phase shift angle detection and reactive power detection, after the working frequency of the system is stable, the relative phase shift angle of the original secondary bridge arm can be maintained at a fixed value, at the moment, the secondary side carries out synchronous rectification according to the detected polarity of the output current of the resonant cavity, namely, the phase information of the secondary bridge arm relative to the primary bridge arm is obtained, and then the internal phase shift angle of the secondary bridge arm is adjusted to adjust the output power. Therefore, the method can avoid the condition that the relative phase shift angle of the primary side and the secondary side is different from the theoretical value caused by the error of system parameters, and has better robustness; active and reactive detection is not needed, and no additional hardware is needed; simple structure and low loss.
(2) The invention synchronizes the phase of the secondary bridge arm by continuously detecting the current polarity of the secondary resonant cavity, solves the problem that the transmission active power is 0 due to the deviation of the original secondary working frequency, is essentially a reactive closed loop without PI regulation, has no reactive flow in the whole process, and has quick system response.
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The following describes embodiments of the present invention in further detail with reference to the accompanying drawings.
FIG. 1 is a schematic diagram of the present invention illustrating a bi-directional wireless charging control energy transfer from a primary side to a secondary side;
FIG. 2 is a schematic diagram illustrating the adjustment of the phase shift angle of the secondary bridge arm according to the present invention;
fig. 3 is a primary side control block diagram of the bidirectional wireless charging communication-free constant current control scheme mentioned in the present invention;
fig. 4 is a control block diagram of a secondary side of the bidirectional wireless charging communication-free constant current control scheme mentioned in the invention.
In fig. 1: inductor L3And L4The primary and secondary filter inductors and the capacitor C are respectively1And C2The filter inductors of the original secondary side are respectively, Q1-Q4 are MOS switching tubes of a primary side bridge arm, Q5-Q8 are secondary side bridge arm switching tubes, and a resonant inductor L1Resonant inductor LPResonant capacitor Cp1Resonant capacitor Cp2Form a primary LCC resonant cavity and a resonant inductor L2Resonant inductor Ls and resonant capacitor Cs1Resonant capacitor Cs2Forming a secondary LCC cavity, phi being the phase difference between the cavity input voltage and current detected on the primary sidesIs a specified value of the phase difference between the voltage and the current of the primary resonant cavity in the process of tracking the frequency of the resonance point, fpIs the working frequency of the primary bridge arm, f and theta are the system working frequency obtained by the secondary side detecting the rising edge of the resonant cavity current polarity signal and the phase of the whole secondary bridge arm, thetas is the phase angle of the secondary bridge arm when the secondary bridge arm regulates the active power, PoIs the output power detected by the system and P _ ref is the given output power.
In FIG. 2, Ug5-Ug8 are driving signals of MOS transistors Q5-Q8, respectively, UAuxiliary setIs the input voltage signal of the secondary side resonator.
In the figure3 middle phisIs a specified value for the phase difference between the input voltage and current to the primary cavity, and phi max is the maximum difference between the allowed phase difference measurement and the specified value.
In fig. 4 f _ c is the difference between the maximum and minimum values of the measured 20 frequencies, and f _ max is the maximum frequency difference of the 20 measurements when the system is allowed to stabilize. The continuous detection times can be adjusted according to actual conditions.
Detailed Description
The invention will be further described with reference to specific examples, but the scope of the invention is not limited thereto.
Taking a wireless charging circuit with double LCC resonant cavities as an example, the hardware circuit for transmitting electric energy from a primary side to a secondary side of the wireless charging circuit without communication constant current control method applied to the bidirectional wireless electric energy transmission circuit provided by the invention is shown in FIG. 1. The bidirectional wireless charging circuit comprises a bidirectional direct-current voltage source VDC1And VDC2Primary side filter inductance L3Primary side filter capacitor C1Secondary side filter capacitor C2Secondary side filter inductor L4The system comprises a primary side controller, a secondary side controller, a primary side full bridge, a secondary side full bridge and a double LCC resonant cavity. Wherein the content of the first and second substances,
the primary side full bridge comprises a first bridge arm and a second bridge arm which are connected in parallel, wherein the first bridge arm comprises a first switching tube Q1 and a third switching tube Q3 which are connected in series, and the second bridge arm comprises a second switching tube Q2 and a fourth switching tube Q4 which are connected in series. A first node a is arranged between the first switch tube Q1 and the third switch tube Q3, the first node a is electrically connected to one end of the primary side of the LCC resonant cavity, a second node B is arranged between the second switch tube Q2 and the fourth switch tube Q4, and the second node B is electrically connected to the other end of the primary side of the LCC resonant cavity.
The secondary side full bridge comprises a third bridge arm and a fourth bridge arm which are connected in parallel, wherein the third bridge arm comprises a fifth switching tube Q5 and a seventh switching tube Q7 which are connected in series, and the fourth bridge arm comprises a sixth switching tube Q6 and an eighth switching tube Q8 which are connected in series. A third node C is arranged between the fifth switching tube Q5 and the seventh switching tube Q7, the third node C is electrically connected to one end of the secondary side of the LCC resonant cavity, a fourth node D is arranged between the sixth switching tube Q6 and the eighth switching tube Q8, and the fourth node D is electrically connected to the other end of the secondary side of the LCC resonant cavity.
The double LCC resonant cavity comprises a primary side resonant inductor L1Primary side resonance inductance LpPrimary side resonance capacitor Cp1Primary side resonance capacitor Cp2Secondary side resonance inductor L2Secondary side resonance inductor LsSecondary side resonance capacitor Cs2And secondary side resonance capacitor Cs2Primary side resonance inductance L1Primary side resonance inductance LpPrimary side resonance capacitor Cp1And primary side resonance capacitor Cp2A secondary resonant inductor L arranged on the primary side of the double LCC resonant cavities2Secondary side resonance inductor LsSecondary side resonance capacitor Cs2And secondary side resonance capacitor Cs2Is arranged on the secondary side of the dual LCC resonator.
The bidirectional wireless charging communication-free constant current control method comprises the following steps:
the working direction of the circuit can be determined by an external given signal, and the direction switching can also be automatically carried out in a timing mode. When the circuit works, the duty ratios of driving signals of four switching tubes (a first switching tube Q1, a second switching tube Q2, a third switching tube Q3 and a fourth switching tube Q4) of the primary side bridge are all 0.5, wherein the driving waveforms of the first switching tube Q1 and the fourth switching tube Q4 are completely the same. The second switch tube Q2 and the third switch tube Q3 are the same, and the first switch tube Q1 and the third switch tube Q3 are complementary, and particularly in practical application, a dead time (a specific value is generally adjusted according to experimental test results) is added in the middle of switching of the first switch tube Q1 and the third switch tube Q3 according to the switching characteristics of the switch tubes, so that the duty ratio of a driving signal in practical application is slightly less than 0.5. During the resonant point frequency tracking process, the controller changes the circuit operating frequency by changing the switching frequency of the switching tubes (the first switching tube Q1, the second switching tube Q2, the third switching tube Q3 and the fourth switching tube Q4).
The invention can realize the constant current control without communication, taking the electric energy transferred from the primary side to the secondary side as an example, the flow charts of the primary side and the secondary side in the control process without communication are respectively shown in fig. 3 and fig. 4, and the realization steps are as follows:
step 1: the system starts to work, the primary side is at a preset initial frequency f0Full-bridge inversion is carried out, the secondary MOS is completely switched off, and the secondary MOS works in an uncontrolled rectification state;
step 2: the primary side controller samples input voltage and current of the resonant cavity, square wave signals representing polarity are obtained through processing of the comparator, rising edge time intervals of the two are measured, and phase difference between the two is calculated
Figure BDA0002640885210000051
According to a specified phase difference phisThe difference value between the two frequency values is used for regulating the frequency of the inversion of the primary side bridge arm through PI (proportion integration) so as to track the frequency of a resonance point and simultaneously track the frequency of the resonance point
Figure BDA0002640885210000052
And phisThe difference between the two is compared with the allowable control error value phi _ max if
Figure BDA0002640885210000053
Stopping frequency modulation, otherwise repeating the step 2 to continue frequency modulation;
and step 3: and the secondary side controller detects the rising edge of the polarity signal of the input current of the resonant cavity, and the time between two rising edges is t, so that the current frequency of the resonant cavity is 1/t. Continuously detecting the current frequency of the resonant cavity twenty times (the continuous detection times can be adjusted according to actual conditions), calculating the difference value f _ c between the maximum value and the minimum value in the twenty times, specifying the allowable maximum measurement frequency fluctuation range f _ max when the frequency is stable, and if f _ c is less than or equal to f _ max, judging that the system frequency is stable, and performing step 4; if f _ c > f _ max, repeating the step 3 to continue the detection;
and 4, step 4: the secondary side controller samples the input current of the secondary side resonant cavity, square wave signals representing the polarity are obtained through the processing of the comparator, and the input current of the resonant cavity, namely the secondary side resonant inductance L, is detected2The frequency f of the medium current is used as the switching frequency of the secondary side bridge arm, the secondary side controller detects the rising edge of a current polarity signal, namely the zero crossing point of the input current of the resonant cavity, and outputs a driving signal to carry out the same operation of the secondary side bridge arm at the rising edgeAnd (6) rectifying.
And 5: secondary controller detection system output current IoCalculating to obtain the output power PoAdjusting the internal phase shift angle theta s of the secondary side bridge arm: when Po is detected<When P _ ref, θ s is θ s-1, when Po>When the value is P _ ref, theta s is theta s +1, and the mode can ensure the stability of the system and the regulation speed; the process of adjusting the internal phase shift angle theta s by the secondary bridge arm is as follows: on the basis of the integral phase of the secondary side bridge arm determined when the zero crossing point of the input current of the secondary side resonant cavity is detected, the phases of the MOS tubes Q5 and Q7 are advanced by thetasPhase lag of 2, Q6 and Q8s/2。
Step 6: and (5) detecting the rising edge of the current polarity signal by the secondary side controller, namely detecting the zero crossing point of the resonant cavity input current, integrally shifting the phase of the secondary side bridge arm at the rising edge to ensure that the fundamental phase of the resonant cavity input voltage is the same as the detected current phase, and returning to the step 5.
The invention is applicable to resonant cavities exhibiting constant current source properties, i.e., resonant cavities in which the secondary resonant cavity output current is related to the primary resonant cavity input voltage and is not related to the secondary resonant cavity input voltage, including but not limited to SS resonant compensation networks, dual LCC resonant compensation networks, and dual LCL resonant compensation networks, should be considered as the scope of the invention.
Finally, it is to be noted that the above-mentioned list is only a few specific embodiments of the present invention. It is obvious that the invention is not limited to the above embodiments, but that many variations are possible. Moreover, all modifications attainable by one versed in the art from the present disclosure within the scope and spirit of the present invention are to be considered as within the scope and spirit of the present invention.

Claims (5)

1. A non-communication constant current control method applied to a bidirectional wireless power transmission circuit is characterized by comprising the following steps:
(1) in a resonant cavity wireless charging circuit, a primary side is at a preset initial frequency f0Carrying out full-bridge inversion; the MOS switch tube on the secondary side is fully turned off and works in an uncontrolled rectification state;
(2) input electricity of primary side controller to primary side resonant cavitySampling the voltage and the current, and then processing the voltage and the current by a comparator to obtain a square wave signal representing the polarity; measuring the time interval of the two rising edges and calculating the phase difference
Figure FDA0002640885200000011
According to a specified phase difference phisThe difference value between the two signals is used for regulating the frequency of the inversion of the primary side bridge arm through a PI (proportional integral) so as to track the frequency of the resonance point; at the same time will
Figure FDA0002640885200000012
φsThe difference between the two is compared with the allowable control error value phi _ max if
Figure FDA0002640885200000013
Stopping frequency modulation, otherwise repeating the step (2) to continue frequency modulation;
(3) the secondary side controller detects whether the frequency of the resonant cavity input current is stable, and if so, the step (4) is carried out; otherwise, repeating the step (3) to continue the detection;
(4) the secondary side controller samples input current of the secondary side resonant cavity and then obtains a square wave signal representing polarity through processing of the comparator; detecting the frequency f of the input current of the secondary resonant cavity, and taking the frequency f as the switching frequency of a secondary bridge arm; the secondary side controller detects the rising edge of a current polarity signal, namely the zero crossing point of the input current of the resonant cavity, and outputs a driving signal at the rising edge to carry out synchronous rectification on a secondary side bridge arm;
(5) secondary controller detection system output current IoCalculating to obtain the output power PoObtaining PoThe secondary side controller adjusts the phase shift angle theta in the secondary side bridge arm through feedback according to the difference value of the specified output power P _ refs；
(6) And (3) detecting the rising edge of the current polarity signal by the secondary side controller, namely detecting the zero crossing point of the resonant cavity input current, integrally shifting the phase of the secondary side bridge arm at the rising edge to ensure that the phase of the fundamental wave of the resonant cavity input voltage is the same as the phase of the detected current, and then returning to the step (5).
2. The method of claim 1, wherein a resonant cavity exhibiting constant current source properties is used in the resonant cavity wireless charging circuit, i.e., the secondary resonant cavity output current is related to the primary resonant cavity input voltage and is not related to the secondary resonant cavity input voltage; the resonant cavity is any one of an SS resonance compensation network, a double-LCC resonance compensation network or a double-LCL resonance compensation network.
3. The method of claim 1, wherein in step (3), the step of detecting whether the frequency of the resonator input current is stable comprises: sampling the input current of the secondary resonant cavity to obtain a square wave signal representing the polarity, detecting the rising edge of the obtained polarity signal by a secondary controller, and measuring the time between two rising edges as t, wherein the current frequency of the resonant cavity is 1/t; continuously detecting the current frequency of the resonant cavity for a plurality of times, and solving the difference f _ c between the maximum value and the minimum value; specifying a maximum measurement frequency fluctuation range f _ max allowed when the frequency is stable, and if f _ c is less than or equal to f _ max, judging that the system frequency is stable; if f _ c > f _ max, the system has not reached steady state.
4. The method of claim 1, wherein the resonant cavity wireless charging circuit is a dual LCC resonant cavity wireless charging circuit, and the secondary side full bridge comprises a third leg and a fourth leg connected in parallel; the third bridge arm comprises a fifth switching tube Q5 and a seventh switching tube Q7 which are connected in series, and the fourth bridge arm comprises a sixth switching tube Q6 and an eighth switching tube Q8 which are connected in series; a third node C is arranged between the fifth switching tube Q5 and the seventh switching tube Q7, the third node C is electrically connected to one end of the secondary side of the LCC resonant cavity, a fourth node D is arranged between the sixth switching tube Q6 and the eighth switching tube Q8, and the fourth node D is electrically connected to the other end of the secondary side of the LCC resonant cavity;
in the step (5), when the system output power P is detected0<When the output power P _ ref is given, the secondary side bridge arm adjusts the internal phase angle theta when the active power is adjusteds＝θs-1; when P is present0>P _ ref, θs＝θs+ 1; secondary side bridge arm internal shift angle thetasThe adjusting method comprises the following steps: on the basis of the integral phase of the secondary side bridge arm determined when the zero crossing point of the input current of the secondary side resonant cavity is detected, the phases of the fifth switching tube Q5 and the seventh switching tube Q7 are advanced by thetas/2, the phase lag θ between the sixth switch tube Q6 and the eighth switch tube Q8s/2。
5. The method according to claim 1, wherein in the step (6), the reactive power detection mode PI is not used for adjusting the overall phase shift angle of the secondary side bridge arm, the secondary side bridge arm detects the rising edge of the resonant cavity input current polarity signal in each control cycle, and the overall phase shift angle of the secondary side bridge arm is synchronized at the zero-crossing point, namely, the phase shift is carried out so that the fundamental wave phase and the current phase of the secondary resonant cavity input voltage are the same.
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Cited By (4)

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CN113271016A (en) * 2021-05-28 2021-08-17 中国电力科学研究院有限公司 Multi-level bidirectional wireless power transmission system and method
CN113525149A (en) * 2021-08-12 2021-10-22 长春捷翼汽车零部件有限公司 Electric energy supply control method and device, electronic equipment and storage medium
CN113972843A (en) * 2021-10-25 2022-01-25 珠海格力电器股份有限公司 Frequency tracking control method and device and power supply
CN115489349A (en) * 2022-09-05 2022-12-20 青岛理工大学 Constant-current and constant-voltage device applied to wireless charging system of electric automobile

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