CN107968571B - A kind of double active three phase-shifting control methods of bridging parallel operation - Google Patents
A kind of double active three phase-shifting control methods of bridging parallel operation Download PDFInfo
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- CN107968571B CN107968571B CN201711208282.4A CN201711208282A CN107968571B CN 107968571 B CN107968571 B CN 107968571B CN 201711208282 A CN201711208282 A CN 201711208282A CN 107968571 B CN107968571 B CN 107968571B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
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Abstract
The present invention relates to the control methods of double active bridging parallel operations, it is desirable to provide a kind of double active three phase-shifting control methods of bridging parallel operation.It is the output voltage controller being arranged in double active bridge DC converters of two-way topological structure for adjusting output voltage, the input signal of the output voltage controller is the given value of secondary side DC voltage and the difference of actual measured value, its output signal is control signal alpha, for adjusting the duty ratio D1 and D2 and its phase difference D3 of primary side bridge arm mid-point voltage and secondary side bridge arm mid-point voltage.The present invention solves the problems, such as double active bridge current stress optimal solutions and control complexity: acquiring corresponding D1, D2 and D3 when the inductive current stress minimum value under each power points, and solve the relationship between three, it proposes easy control method, only can be achieved with converter with a PI controller and run by the smallest track of current stress.
Description
Technical field
The present invention relates to a kind of control methods of the double active bridging parallel operations of single-phase or multiphase, belong to the double of field of power electronics
To direct-current isolating switch power supply direction.
Background technique
Converter with isolation, energy in bidirectional flow has a wide range of applications demand, such as microgrid, solid-state transformer, electricity
Electrical automobile charging pile etc..The either reversible transducer of exchange or direct current, core are all that two-way DC- is isolated in medium-high frequency
DC converter.In practical applications, to reduce energy loss, cost and volume, efficiency and power density are that evaluation isolation is two-way
The important indicator of DC-DC converter.
In numerous isolation bidirectional DC-DC converters topology, double active bridges because of its symmetrical configuration, control flexibly, Yi Shixian
No-voltage is opened and is widely studied and applied.The topological structure of common single-phase double active bridges is as shown in Figure 1, the topological structure
For symmetrical structure, transformer primary side and secondary side form full-bridge circuit, V by switching tubeabAnd VcdIt is primary side and two respectively
Secondary side bridge arm mid-point voltage, iLIt is inductive current.Two full-bridge circuits pass through a medium/high frequency transformer connection.
Common single-phase double active bridges can produce phase difference between each bridge arm altogether there are four bridge arm, thus there are three controls
Variable, including VabAnd VcdDuty ratio D1And D2And the phase difference between Vab and Vcd.Traditional phase shift modulation method is only adjusted
φ is saved, and keeps D1And D2It is 50%, this method control is simple and switching tube can realize that no-voltage opens (ZVS-on) spy automatically
Property, but being limited in scope of opening of no-voltage and there are biggish current stresses, will increase conduction loss.Scholars carry out
To this numerous studies, research emphasis is to try to adjust D simultaneously1、D2And φ reduces conduction loss with smaller current stress.
2013 in IEEE Transaction on Industrial Electronics[power electronics periodical] on deliver
“Current-stress-optimized switching strategy of isolated bidirectional DC–DC
A converter with dual-phase-shift control " text, proposes while adjusting D1、D2Reduce electric current with φ
Stress, but since D1 and D2 keeps equal, which has substantially only carried out the adjusting of two dimensions, acquires
Current stress minimum value is only the optimal of part；2012 in IEEE Transaction on Power Electronics
" the Closed form solution for minimum conduction loss that [power electronics periodical] is delivered
A modulation of DAB converters " text, by changing D1, D2Decoupling with tri- dimensions of φ is adjusted to be led to reduce
Logical loss, but this method expression formula is complicated, and without carrying out closed loop design, complicated control method under medium power level
Make them unsuitable for engineering practice.2016 in IEEE Transaction on Industrial Electronics[electric power electricity
Sub- periodical] on " the Unified Triple-Phase-Shift Control to Minimize Current Stress that delivers
And Achieve Full Soft-Switching of Isolated Bidirectional DC-DC Converter ", mentions
Go out and has been acquired under each power points using the method for Karush-Kuhn-Tucker condition by freely adjusting three dimensions
The minimum value of current stress, but this method adjusts D1、D2With the size for needing to know output power when Df, then need to increase electricity
Flow sensor carries out output electric current real-time sampling, and the electric current of high frequency is difficult to adopt standard, increases the cost and control of controller
Difficulty.
In summary, existing double active bridge control methods cannot be considered in terms of current stress optimal solution and control complexity.
Summary of the invention
The technical problem to be solved by the present invention is to overcome deficiency in the prior art, provide a kind of double active bridging parallel operations
Three phase-shifting control methods.This method adjusts D by three phase-shifting control methods1、D2And D3, reach double active bridge inductive current stress
To minimum value, and the internal relation of three dimensions is found, simplifies control method, it is simple and easy, it is suitable for engineering practice.
In order to solve the technical problem, solution of the invention is:
A kind of double active three phase-shifting control methods of bridging parallel operation are provided, are double active bridge direct currents changes in two-way topological structure
Output voltage controller for adjusting output voltage is set in parallel operation, and the input signal of the output voltage controller is secondary side
The given value of DC voltage and the difference of actual measured value, output signal is control signal alpha, for adjusting in primary side bridge arm
The duty ratio D of point voltage and secondary side bridge arm mid-point voltage1And D2And its phase difference D3；
The duty ratio D of the primary side and secondary side bridge arm mid-point voltage1And D2And phase difference D between the two3, lead to
It crosses following formula and calculates acquisition:
In above-mentioned formula, α is the control signal of output voltage controller output, and value range is [0,1]；V1And V2Point
It is not the DC voltage of primary side and secondary side, n is that primary side is unlimited to the value range of the no-load voltage ratio n:1, n of secondary side, and d is to become
The voltage gain ratio nV of parallel operation2/V1。
In the present invention, the primary side of double active bridge DC converters can be exchanged with secondary side；Double active bridge direct currents
Converter is any one following: single-phase double active bridge DC converters, the double active bridge DC converters of multiphase, two level are double
The double active bridge DC converters of active bridge DC converter, more level, or the modular multilevel circuit based on double active bridges.
In the present invention, double active bridge DC converters are single-phase double active bridging parallel operations, primary side and secondary side
Eight switching tubes are shared, are the first switch tube S1, second switch S2, the switch of third switching tube S3 and the 4th of primary side respectively
The 5th switching tube S5, the 6th switching tube S6, the 7th switching tube S7 and the 8th switching tube S8 of pipe S4 and secondary side；It is concatenated
Switching tube first switch tube S1 and second switch S2 and concatenated third switching tube S3 and the 4th switching tube S4 simultaneously connects, concatenated
5th switching tube S5 and the 6th switching tube S6 and concatenated 7th switching tube S7 and the 8th switching tube S8 simultaneously connects；
The driving signal of all switching tubes is all 50% square-wave signal, is according to phase difference D3, primary side and secondary side
The duty ratio D of bridge arm mid-point voltage1、D2It generates；Wherein, first switch tube S1 is complementary with the signal of second switch S2, third
Switching tube S3 is complementary with the signal of the 4th switching tube S4, the 5th switching tube S5 is complementary with the signal of the 6th switching tube S6, the 7th opens
It is complementary with the signal of the 8th switching tube S8 to close pipe S7；The time of the advanced S3 of switching tube S1 is by duty ratio D1Control, the 5th switching tube
The time of the advanced 7th switching tube S7 of S5 is by duty ratio D2Control, between switching tube first switch tube S1 and the 5th switching tube S5
Phase difference D3Control.
In the present invention, the output voltage controller is controlled with proportional integration PI.
In the present invention, the output voltage controller includes sequentially connected voltage difference comparator, PI controller and limit
Width device；Wherein, the input signal of voltage difference comparator be secondary side DC voltage given value and actual measured value difference,
PI controller controls to obtain control signal alpha, and limiter is limited in signal alpha is controlled in [0,1], and makes output power and control signal
α is in monotonic relationshi, and by calculating so that duty ratio D1And D2It is limited in [0,1] range, D3 is limited in [0,0.5] range.
Compared with prior art, the invention has the following beneficial technical effects:
Double active three phase-shifting control methods of bridge of the invention solve double active bridge current stress optimal solutions and control is complicated
The problem of spending: corresponding D when the inductive current stress minimum value under each power points is acquired1、D2And D3, and solve between three
Relationship, propose easy control method, only can be achieved with converter by the smallest track of current stress with a PI controller
Operation.
Detailed description of the invention
Fig. 1 is the topological structure of common double active bridge bidirectional DC-DC converters；
Fig. 2 is former secondary side bridge arm mid-point voltage waveform and phase relation schematic diagram；
Fig. 3 is control block diagram of the invention；
Fig. 4 is to work as V1≥nV2When the former secondary side bridge arm mid-point voltage waveform diagram of different loads situations；
Fig. 5 is to work as V1< nV2When the former secondary side bridge arm mid-point voltage waveform diagram of different loads situations.
Specific embodiment
The present invention is described in detail below in conjunction with drawings and examples, while also describing technical solution of the present invention solution
Certainly the technical issues of and beneficial effect, it should be pointed out that described embodiment is intended merely to facilitate the understanding of the present invention, and
Any restriction effect is not played to it.
Single-phase double active bridge bidirectional DC-DC converter circuit topological structures are as shown in Figure 1.Primary side is by four switching tubes
S1-S4 composition, two bridge arms constitute a full-bridge circuit, and the midpoint of two bridge arms is respectively a, b two o'clock.A, b two o'clock connection becomes
The first side winding of depressor.Secondary side is made of four switching tube S5-S8, and two bridge arms constitute a full-bridge circuit, two bridges
The midpoint of arm is respectively c, d two o'clock.C, the secondary side winding of d two o'clock connection transformer.LkFor transformer leakage inductance or outer power-up
Sense.VabFor the voltage difference between a point and b point；VcdFor the voltage difference between c point and d point；iLFor inductive current；i1And i2Respectively
To output and input electric current；V1For the DC voltage of primary side；V2For the DC voltage of secondary side.
Single-phase double active bridge bidirectional DC-DC converter key operation waveforms are as shown in Fig. 2, D1And D2Respectively indicate primary side
With the duty ratio of secondary side bridge arm mid-point voltage, D3Indicate phase difference between the two.
Control block diagram used by the present embodiment is as shown in figure 3, include sequentially connected voltage difference comparator, PI control
Device, limiter, duty ratio and phase difference calculating module and driving signal generation module.Wherein, the input of voltage difference comparator
Signal is the given value V of secondary side DC voltage2refWith actual measured value V2Difference；The signal is controlled by PI
Signal alpha；The purpose of limiter is that α is limited between 0 to 1, it is easy to accomplish rear class control passs output power and α in dullness
Increasing relationship, works as V2Less than V2refWhen, difference is positive, and control signal alpha becomes larger, and increases output power, makes V2Increase；Work as V2Greatly
In V2refWhen, difference is negative, and control signal alpha gradually becomes smaller, and reduces output power, makes V2Reduce；Pass through duty ratio and phasometer
Module is calculated, former pair side duty ratio D is obtained according to control signal alpha1, D2And its phase difference D3, calculation formula is as follows:
Wherein V1And V2It is primary side and secondary side DC voltage respectively, n is no-load voltage ratio n of the transformer primary side to secondary side:
1, d is the voltage gain ratio nV of converter2/V1, because output power and α are in monotonic increase relationship, Fig. 4 and Fig. 5 are shown respectively
V1≥nV2And V1< nV2Two kinds in the case of with changed power the secondary side bridge arm mid-point voltage waveform diagram of original, with output power
Increase, α is gradually incremented by, D1, D2, D3Reach the output power of needs according to the variation of above-mentioned relation formula.
Finally according to D1、D2And D3Value, pass through driving signal generation module generate eight driving signals: all drivings
Signal is all 50% square-wave signal；S1 is complementary with S2, S3 is complementary with S4, S5 is complementary with S6, S7 is complementary with S8；The advanced S3's of S1
Time is by D1Control, the time of the advanced S7 of S5 is by D2Control, the phase difference between S1 and S5 is by D3Control.
Claims (5)
1. a kind of double active three phase-shifting control methods of bridging parallel operation, which is characterized in that be double active bridges in two-way topological structure
Output voltage controller for adjusting output voltage is set in DC converter, and the input signal of the output voltage controller is
The given value and actual measured value of secondary side DC voltage, output signal is control signal alpha, for adjusting in primary side bridge arm
The duty ratio D of point voltage and secondary side bridge arm mid-point voltage1And D2And its phase difference D3；
The duty ratio D of the primary side and secondary side bridge arm mid-point voltage1And D2And phase difference D between the two3, under
It states formula and calculates acquisition:
In above-mentioned formula, α is the control signal of output voltage controller output, and value range is [0,1]；V1And V2It is respectively
The DC voltage of primary side and secondary side, n are primary side to no-load voltage ratio n: 1 of secondary side, and the value range of n is unlimited, and d is converter
Voltage gain ratio nV2/V1。
2. the method according to claim 1, wherein the primary side of double active bridge DC converter with it is secondary
Side can exchange；Double active bridge DC converters are any one following: single-phase double active bridge DC converters, multiphase pair have
The double active bridge DC converters of source bridge DC converter, two level, the double active bridge DC converters of more level, or had based on double
The modular multilevel circuit of source bridge.
3. the method according to claim 1, wherein double active bridge DC converters are single-phase double active bridges
Converter, primary side and secondary side share eight switching tubes, are first switch tube S1, the second switch of primary side respectively
5th switching tube S5 of S2, third switching tube S3 and the 4th switching tube S4 and secondary side, the 6th switching tube S6, the 7th switch
Pipe S7 and the 8th switching tube S8；Concatenated switching tube first switch tube S1 and second switch S2 and concatenated third switching tube S3
With the 4th switching tube S4 and connect, concatenated 5th switching tube S5 and the 6th switching tube S6 and concatenated 7th switching tube S7 and the 8th
Switching tube S8 simultaneously connects；
The driving signal of all switching tubes is all 50% square-wave signal, is according to phase difference D3, in primary side and secondary side bridge arm
The duty ratio D of point voltage1、D2It generates；Wherein, first switch tube S1 is complementary with the signal of second switch S2, third switching tube
S3 is complementary with the signal of the 4th switching tube S4, the 5th switching tube S5 is complementary with the signal of the 6th switching tube S6, the 7th switching tube S7
It is complementary with the signal of the 8th switching tube S8；The time of the advanced S3 of switching tube S1 is by duty ratio D1Control, the 5th switching tube S5 are advanced
The time of 7th switching tube S7 is by duty ratio D2Control, the phase difference between switching tube first switch tube S1 and the 5th switching tube S5
D3Control.
4. the method according to claim 1, wherein the output voltage controller is controlled with proportional integration PI.
5. the method according to claim 1, wherein the output voltage controller includes sequentially connected voltage
Difference comparsion device, PI controller and limiter；Wherein, the input signal of voltage difference comparator is giving for secondary side DC voltage
Definite value and actual measured value, PI controller control to obtain control signal alpha, and limiter is limited in signal alpha is controlled in [0,1], makes
Output power and control signal alpha are in monotonic relationshi, and by calculating so that duty ratio D1And D2It is limited in [0,1] range, D3 limit
System is in [0,0.5] range.
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| US9356523B2 (en) * | 2012-12-28 | 2016-05-31 | Panasonic Intellectual Property Management Co., Ltd. | DC-to-DC converter |
| CN104779802B (en) * | 2015-03-26 | 2017-03-01 | 西南交通大学 | A kind of minimum optimal control method of the monolateral three level DC DC converter current virtual values of bi-directional half bridge |
| CN104753356B (en) * | 2015-03-26 | 2017-03-01 | 西南交通大学 | A kind of bi-directional half bridge three level DC DC converter current virtual value minimizes control method |
| JP6235540B2 (en) * | 2015-08-28 | 2017-11-22 | 株式会社豊田中央研究所 | Power conversion circuit |
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