CN112086721A - Broadband two-dimensional and differential phase comparison network based on multilayer microstrip slot coupling structure - Google Patents
Broadband two-dimensional and differential phase comparison network based on multilayer microstrip slot coupling structure Download PDFInfo
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Abstract
The invention discloses a broadband two-dimensional difference phase comparison network based on a multilayer microstrip slot coupling structure, which solves the problem of narrow bandwidth of the conventional two-dimensional difference phase comparison network and can be used for feeding a broadband two-dimensional monopulse array antenna in a monopulse radar. The dielectric plate comprises a first dielectric plate (1) and a second dielectric plate (2) which are stacked up and down. An upper microstrip line is printed on the upper surface of the first dielectric plate (1), and four circular gaps and four linear gaps are formed in a metal floor (14) printed on the lower surface of the first dielectric plate. The lower surface of the second dielectric plate (2) is printed with a lower microstrip line. Four microstrip nodes of the upper layer microstrip line, four circular gaps at corresponding positions on the metal floor and four microstrip nodes at corresponding positions on the lower layer microstrip line form four patch gap couplers; four linear slots etched on the metal floor and the microstrip open-circuit ends at the corresponding positions form four slot coupling phase shifters.
Description
Technical Field
The invention belongs to the technical field of microwaves, relates to a broadband two-dimensional sum-difference phase comparison network, and particularly relates to a broadband two-dimensional sum-difference phase comparison network based on a multilayer microstrip slot coupling structure, which can be used for feeding a broadband two-dimensional monopulse array antenna in a monopulse radar.
Background
The sum-difference phase comparison network is an important microwave passive device, and can be combined with the array antenna feed network to perform phase sum-difference comparison operation on the received four-path antenna independent signals to obtain an angle error signal. The sum-difference phase network is widely applied to the feed network of the monopulse radar array antenna to realize tactical targets such as target tracking.
The traditional two-dimensional and differential phase comparison network is usually based on a metal waveguide structure, on one hand, the traditional two-dimensional and differential phase comparison network has narrower working and phase bandwidths, which limits the application of the traditional two-dimensional and differential phase comparison network in broadband and differential beam forming, on the other hand, the traditional two-dimensional and differential phase comparison network has the defects of large volume, heavy weight, complex structure, high cost and difficulty in integration with a planar circuit, and brings inconvenience for realizing the miniaturization, light weight and integrated design of a radar system.
For example, chinese patent with publication number CN 105762473B entitled "millimeter wave two-dimensional sum-difference network" discloses an eight-port two-dimensional sum-difference phase comparison network, which includes a microstrip line conductor strip, a microstrip line dielectric slab, and a metal shield plate. The front and the back of the network metal shielding plate are respectively provided with a sum port, a pitch difference port, a azimuth difference port and a double difference port. In addition, the network adopts a traditional broadband microstrip 3dB bridge cascade mode, overcomes the defects that the traditional two-dimensional and differential phase comparison network is large in size, heavy in weight, complex in structure, high in cost and not easy to integrate with a planar circuit, and can improve the bandwidth of the network. However, the two-dimensional sum-difference phase comparison network can only realize the two-dimensional sum-difference function within 16% of the relative bandwidth, and cannot meet the requirement of a plurality of monopulse radar systems on broadband two-dimensional sum-difference beam signals.
Disclosure of Invention
The invention aims to overcome the defects in the prior art, and provides a broadband two-dimensional and differential phase comparison network based on a multilayer microstrip slot coupling structure, which is used for solving the technical problem of narrow bandwidth in the prior art.
In order to achieve the above object, the present invention adopts a technical solution including a first dielectric plate 1 and a second dielectric plate 2 which are rectangular and stacked up and down, wherein:
the upper-layer microstrip lines distributed along one diagonal line are printed on the upper surface of the first dielectric plate 1, and each upper-layer microstrip line comprises a first composite microstrip line 11, a second composite microstrip line 12 and a first straight microstrip line 13; the first composite microstrip line 11 and the second composite microstrip line 12 are both composed of three smooth L-shaped microstrip lines connected by microstrip nodes, wherein the input end and the output end of the first composite microstrip line 11 are respectively positioned at the edges of the long side and the short side of the first dielectric slab 1; the input end of the second composite microstrip line 12 is positioned at the edge of the long edge opposite to the input end of the first composite microstrip line 11, and the open end is positioned close to the edge of the short edge opposite to the output end of the first composite microstrip line 11; the open end of the first straight microstrip line 13 is coupled with the open end of the second composite microstrip line 12, and the output end is positioned at the edge of the short edge of the output end of the first composite microstrip line 11; a metal floor 14 is printed on the lower surface of the first dielectric plate 1, circular gaps are etched on the metal floor 14 at the projection positions of the microstrip nodes on the first composite microstrip line 11 and the second composite microstrip line 12, and four linear gaps are also etched on the metal floor 14.
The lower surface of the second dielectric plate 2 is printed with lower microstrip lines which are distributed along a diagonal line intersecting with the projection of the diagonal line where the upper microstrip line is located, and the lower microstrip lines comprise a third composite microstrip line 21, a fourth composite microstrip line 22, a fifth composite microstrip line 23, a sixth composite microstrip line 24 and a second straight microstrip line 25; the third composite microstrip line 21 and the sixth composite microstrip line 24 both adopt a smooth L-shaped microstrip line structure with an arm provided with a microstrip node, the microstrip node on the third composite microstrip line 21 is positioned at the projection position of the microstrip node of the second composite microstrip line 12 close to the input end, the microstrip node on the sixth composite microstrip line 24 is positioned at the projection position of the microstrip node of the first composite microstrip line 11 close to the input end, and the input ends of the two composite microstrip lines are respectively positioned at the edge positions of the long edges of the dielectric slabs; the output end of the second linear microstrip line 25 is positioned on the short side which is the same as the output end of the first composite microstrip line 11; the fourth composite microstrip line 22 and the fifth composite microstrip line 23 are both composed of two smooth L-shaped microstrip lines connected by a microstrip node, the microstrip node on the fourth composite microstrip line 22 is located at the projection position of the microstrip node of the first composite microstrip line 11 close to the output end, the microstrip node on the fifth composite microstrip line 23 is located at the projection position of the microstrip node of the second composite microstrip line 12 close to the open end, wherein one open end of the fourth composite microstrip line 22 is coupled with the open end of the second linear microstrip line 25, the other open end is coupled with the open end of the third composite microstrip line 21, the output end of the fifth composite microstrip line 23 is located at the short edge same as the output end of the first linear microstrip line 13, and the open end of the sixth composite microstrip line 24 form a coupling microstrip line.
Four microstrip nodes on the upper layer microstrip line, four circular gaps at corresponding positions on the metal floor 14 and four microstrip nodes at corresponding positions on the lower layer microstrip line form four patch gap couplers; one of the four linear slots etched on the metal floor 14 corresponds to the coupling position of the open end of the first linear microstrip line 13 and the open end of the second composite microstrip line 12, and the other three slots correspond to the coupling position of the open end of the third composite microstrip line 21 and the open end of the fourth composite microstrip line 22, the coupling position of the open end of the fourth composite microstrip line 22 and the open end of the second linear microstrip line 25, and the coupling position of the open end of the fifth composite microstrip line 23 and the open end of the sixth composite microstrip line 24, respectively, so as to form four slot-coupled phase shifters.
According to the broadband two-dimensional and differential phase comparison network based on the multilayer microstrip slot coupling structure, the two arms of the L-shaped microstrip line are perpendicular, and the joint is in a smooth arc shape.
According to the broadband two-dimensional and differential phase comparison network based on the multilayer microstrip slot coupling structure, the microstrip nodes are rectangular microstrip lines with round, oval or smooth arcs at four corners.
In the broadband two-dimensional and differential phase comparison network based on the multilayer microstrip slot coupling structure, the center of the microstrip node on the upper layer microstrip line, the center of the circular slot at the corresponding position on the metal floor 14, and the center of the microstrip node at the corresponding position on the lower layer microstrip line are all located on a normal line passing through the center of the microstrip node.
In the broadband two-dimensional and differential phase comparison network based on the multilayer microstrip slot coupling structure, the open end of the second composite microstrip line 12, the open end of the first linear microstrip line 13, the open end of the third composite microstrip line 21, the open end of the fourth composite microstrip line 22, the open end of the fifth composite microstrip line 23, the open end of the sixth composite microstrip line 24, the open end of the second linear microstrip line 25, and two ends of the four linear slots all adopt fan-shaped structures.
Compared with the prior art, the invention has the following advantages:
1) four micro-strip nodes on the middle upper layer micro-strip line, four circular gaps at corresponding positions on the metal floor and four micro-strip nodes at corresponding positions on the lower layer micro-strip line form four patch gap couplers with functions of broadband coupling power division and broadband phase shift; four linear slots etched on the metal floor and the microstrip open circuit ends corresponding to the coupling positions form four slot coupling phase shifters with broadband phase shifting function; the gap capacitance in the multilayer gap coupling structure can counteract the inductance generated in an equivalent circuit, and the characteristic of multi-resonance mode of the multilayer gap coupling structure can generate a plurality of phase-shifting resonance points, so that a wider bandwidth can be obtained, and stable phase difference and amplitude exist in a broadband, thereby realizing the characteristic of broadband operation. The four patch slot coupling phase shifters formed by the multilayer slot coupling structures have a broadband power division phase shifting function, and the four slot coupling phase shifters have a broadband direction shifting function. Therefore, stable two-dimensional and differential phase can be obtained in a wide bandwidth by optimally adjusting the parameters of the multilayer slot coupling structure. Compared with the prior art, the method effectively widens the working bandwidth of the comparison network, and simulation results show that the method can realize stable two-dimensional sum-difference phase within 40% of relative bandwidth.
2) The invention adopts a multi-layer microstrip slot coupling structure, only adopts a low-cost dielectric plate and a printed metal layer structure, does not need additional components, adopts a structure that an upper layer microstrip line and a lower layer microstrip line which are composed of smooth L-shaped microstrip lines are distributed along a crossed diagonal line, has the advantages of compact structure, easy planar integration and contribution to large-scale production, is particularly suitable for being integrated in a radar system, and is very convenient to install and debug.
Drawings
FIG. 1 is a schematic view of the overall structure of the present invention;
fig. 2 is a schematic structural diagram of an upper microstrip line according to the present invention;
FIG. 3 is a schematic structural view of the metal floor of the present invention;
fig. 4 is a schematic structural diagram of a lower microstrip line according to the present invention;
fig. 5 is a simulation graph of S-parameters of an input port of a first composite microstrip line according to the present invention;
fig. 6 is a simulation graph of S-parameters of an input port of a second composite microstrip line according to the present invention;
fig. 7 is a simulation graph of S-parameters of an input port of a third composite microstrip line according to the present invention;
fig. 8 is a simulation graph of the S-parameter of the input port of the sixth composite microstrip line of the present invention.
Detailed Description
The invention is described in further detail below with reference to the figures and specific examples.
Referring to fig. 1, the present invention includes: a first dielectric sheet 1 and a second dielectric sheet 2 which are rectangular in shape and stacked one on top of the other. The upper surface of the first dielectric plate 1 is printed with upper microstrip lines arranged along a diagonal line, the lower surface is printed with a metal floor 14, and the lower surface of the second dielectric plate 2 is printed with lower microstrip lines arranged along a diagonal line intersecting with the projection of the diagonal line where the upper microstrip lines are located. And the multilayer microstrip lines along the crossed diagonal line are arranged, so that the sum and difference have a compact structure compared with a network, and plane integration and large-scale production are facilitated. The first dielectric plate 1 and the second dielectric plate 2 are both made of F4B dielectric plates with the length of 70mm, the width of 47mm, the thickness of 0.5mm and the relative dielectric constant of 2.65.
The structure of the upper microstrip line is shown in fig. 2. The upper microstrip line comprises a first composite microstrip line 11, a second composite microstrip line 12 and a first straight microstrip line 13.
The first composite microstrip line 11 and the second composite microstrip line 12 are composed of three smooth L-shaped microstrip lines connected by microstrip nodes, two arms of the L-shaped microstrip lines are perpendicular, and the joint is in a smooth arc shape. The two perpendicular arms of the L-shaped microstrip line and the smooth connecting structure enable the sum and difference to have a more compact structure than a network, and are beneficial to the complementation of the performance among the structures in the network so as to obtain better broadband performance. The microstrip node serving as the connection structure may be a circular microstrip line, an oval microstrip line, or a rectangular microstrip line with four smooth arcs, and since the oval microstrip node has more optimized variables relative to the circular microstrip node and has a smoother profile relative to the rectangular microstrip node with a smooth profile, the embodiment takes the oval microstrip node as an example to obtain a wider bandwidth.
The input end 113 and the output end 114 of the first composite microstrip line 11 are respectively located at the edges of the long side and the short side of the first dielectric slab 1; the input end 124 of the second composite microstrip line 12 is located at the edge of the long side opposite to the input end 112 of the first composite microstrip line 11, and the open end 123 is located close to the edge of the short side opposite to the output end 114 of the first composite microstrip line 11; the open end 132 of the first straight microstrip line 13 is coupled with the open end 123 of the second composite microstrip line 12, and the output end 132 is located at the edge of the short side of the output end 114 of the first composite microstrip line 11.
The centers of the two arms of the two smooth L-shaped microstrip lines connected by the oval microstrip node 111 on the first composite microstrip line 11 are collinear, and the long axis of the oval node 111 is collinear with the centers of the two arms of the two smooth L-shaped microstrip lines connected thereto. The centers of the two arms of the two smooth L-shaped microstrip lines connected by the elliptic microstrip node 112 on the first composite microstrip line 11 are collinear, and the long axis of the elliptic node 112 is collinear with the centers of the two arms of the two smooth L-shaped microstrip lines connected with the elliptic node 112. The microstrip line where the open end 123 of the second composite microstrip line 12 is located is parallel to the open end 132 of the first straight microstrip line 13, and the open end 123 and the open end 132 are cross-coupled to each other. Under the condition that the length and the structure of the microstrip line are the same, compared with other coupling structures, the arrangement mode of the collinear centers of the upper layer microstrip line, the arrangement mode of the parallel open ends and the cross coupling mode have stronger coupling effect, and are beneficial to realizing the broadband performance of the invention.
The structure of the metal floor 14 is shown in fig. 3. The metal floor 14 is formed by etching four circular gaps and four linear gaps with fan-shaped two ends at the projection positions of the elliptic microstrip nodes on the first composite microstrip line 11 and the second composite microstrip line 12. The diameters of four circular gaps on the metal floor are all 5.95mm, the widths of four linear gaps are all 0.2mm, the lengths of the four linear gaps are all 5.4mm, and the radiuses and angles of the fan-shaped structures at the two ends are 1.1mm and 60 degrees respectively.
The structure of the lower microstrip line is shown in fig. 4. The lower microstrip line comprises a third composite microstrip line 21, a fourth composite microstrip line 22, a fifth composite microstrip line 23, a sixth composite microstrip line 24 and a second straight microstrip line 25. The microstrip node as the connection structure can adopt a circular, elliptical or rectangular microstrip line with four smooth arcs, and the elliptical microstrip node has more optimization variables relative to the circular microstrip node and has a smoother profile relative to the rectangular microstrip node with the smoother profile, so that the lower-layer microstrip line in the embodiment also adopts the elliptical microstrip node to obtain a wider bandwidth.
The third composite microstrip line 21 and the sixth composite microstrip line 24 both adopt a smooth L-shaped microstrip line structure with an arm having a microstrip node, the two arms of the L-shaped microstrip line are perpendicular, and the joint is in a smooth arc shape. The two perpendicular arms of the L-shaped microstrip line and the smooth connecting structure enable the sum and difference to have a more compact structure than a network, and are beneficial to the complementation of the performance among the structures in the network so as to obtain better broadband performance. The elliptical microstrip node 211 on the third composite microstrip line 21 is located at the projection position of the elliptical microstrip node 121 on the second composite microstrip line 12. The projection position of the elliptical microstrip node 241 on the sixth composite microstrip line 24 on the elliptical microstrip node 112 of the first composite microstrip line 11. The input end 213 of the third composite microstrip line 21 and the input end 243 of the sixth composite microstrip line 24 are respectively located at the edge positions of the two long sides of the second dielectric slab 2.
The fourth composite microstrip line 22 and the fifth composite microstrip line 23 are both composed of two smooth L-shaped microstrip lines connected by a microstrip node, two arms of the L-shaped microstrip lines are perpendicular, and the joint is in a smooth arc shape. The two perpendicular arms of the L-shaped microstrip line and the smooth connecting structure enable the sum and difference to have a more compact structure than a network, and are beneficial to the complementation of the performance among the structures in the network so as to obtain better broadband performance. The elliptical microstrip node 221 on the fourth composite microstrip line 22 is located at the projection position of the elliptical microstrip node 111 of the first composite microstrip line 11, and the elliptical microstrip node 231 on the fifth composite microstrip line 23 is located at the projection position of the elliptical microstrip node 122 of the second composite microstrip line 12. The open end 223 of the fourth composite microstrip 22 is coupled to the open end 212 of the third composite microstrip 21, and the open end 222 is coupled to the open end 251 of the second linear microstrip 25. The output end 233 of the fifth composite microstrip line 23 is located on the short side at the same position as the output end 132 of the first straight microstrip line 13, and the open end 232 is coupled with the open end 242 of the sixth composite microstrip line 24.
The centers of the two arms of the two smooth L-shaped microstrip lines connected by the elliptic microstrip node 211 on the third composite microstrip line 21 are collinear. The centers of the two arms of the two smooth L-shaped microstrip lines connected by the elliptic microstrip node 221 on the fourth composite microstrip line 22 are collinear. The centers of the two arms of the two smooth L-shaped microstrip lines connected by the elliptic microstrip node 231 on the fifth composite microstrip line 23 are collinear. The centers of the two arms of the two smooth L-shaped microstrip lines connected by the elliptic microstrip node 241 on the sixth composite microstrip line 24 are collinear. The microstrip line on which the open end 212 of the third composite microstrip line 21 is located and the microstrip line on which the open end 223 of the fourth composite microstrip line 22 is located are parallel, and the open end 212 and the open end 223 are cross-coupled to each other. The microstrip line where the open end 222 of the fourth composite microstrip line 22 is located is parallel to the open end 251 of the second linear microstrip line 25, and the open end 222 and the open end 251 are cross-coupled to each other. The microstrip line on which the open end 232 of the fifth composite microstrip line 23 is located is parallel to the microstrip line on which the open end 242 of the sixth composite microstrip line 24 is located, and the open end 232 and the open end 242 are cross-coupled to each other. Similarly, the arrangement mode of the center collineation, the arrangement mode of the open end parallel and the cross coupling of the lower microstrip line have stronger coupling effect compared with other coupling structures, and are beneficial to realizing the broadband performance of the invention.
The open end 123 of the second composite microstrip line 12, the open end 131 of the first linear microstrip line 13, the open end 212 of the third composite microstrip line 21, the open end 222 and the open end 223 of the fourth composite microstrip line 22, the open end 232 of the fifth composite microstrip line 23, the open end 242 of the sixth composite microstrip line 24, and the open end 251 of the second linear microstrip line 25 all adopt a fan-shaped structure with a radius of 2mm and a radian of 120 °. The two ends of four linear gaps on the metal floor 2 are both fan-shaped structures with the radius of 1.1mm and the radian of 60 degrees. Major axes of elliptic microstrip nodes on the first composite microstrip line 11, the second composite microstrip line 12, the third composite microstrip line 21, the fourth composite microstrip line 22 and the fifth composite microstrip line 23 are all 6.7mm, and minor axes are all 3.8 mm. The upper microstrip line and the lower microstrip line are both 50 ohm microstrip lines, and the line width is 1.33 mm. Two arms of the L-shaped microstrip line which forms the upper layer microstrip line and the lower layer microstrip line are connected by an arc microstrip with the inner diameter of 3.5 mm.
The center of the elliptical microstrip node 111 on the first composite microstrip line 11, the center of the circular slot 141 on the metal floor, and the center of the elliptical microstrip node 221 on the fourth composite microstrip line 22 are all located on a normal line passing through the center of the elliptical microstrip node 111, and the three structures form a first patch slot coupler; the center of the elliptical microstrip node 112 on the first composite microstrip line 11, the center of the circular slot 142 on the metal floor, and the center of the elliptical microstrip node 241 on the sixth composite microstrip line 24 are all located on a normal line passing through the center of the elliptical microstrip node 112, and the three structures form a second patch slot coupler; the center of the elliptical microstrip node 121 on the second composite microstrip line 12, the center of the circular slot 143 on the metal floor, and the center of the elliptical microstrip node 211 on the third composite microstrip line 21 are all located on a normal line passing through the center of the elliptical microstrip node 121, and the three structures form a third patch slot coupler; the center of the elliptical microstrip node 122 on the second composite microstrip line 12, the center of the circular slot 144 on the metal floor, and the center of the elliptical microstrip node 231 on the fifth composite microstrip line 23 are all located on a normal line passing through the center of the elliptical microstrip node 122, and the above three structures constitute a fourth patch slot coupler.
The arrangement direction of the linear slot 145 on the metal floor 14 is perpendicular to the arrangement direction of the microstrip line where the open end 123 and the open end 132 at corresponding positions are located, and the position is between the two corresponding open ends to adjust the phase, so that the three form a first slot coupling phase shifter; the arrangement direction of the linear slot 146 on the metal floor 14 is perpendicular to the arrangement direction of the microstrip line where the open-circuit end 232 and the open-circuit end 242 at corresponding positions are located, and the position is between the two corresponding open-circuit ends to adjust the phase, so that the three form a second slot coupling phase shifter; the arrangement direction of the linear slot 147 on the metal floor 14 is perpendicular to the arrangement direction of the microstrip line where the open end 212 and the open end 223 at corresponding positions are located, and the position is between the two corresponding open ends to adjust the phase, so that a third slot coupling phase shifter is formed by the three parts; the arrangement direction of the linear slot 148 on the metal floor 14 is perpendicular to the arrangement direction of the microstrip line where the open end 222 and the open end 251 at corresponding positions are located, and the position is between the two open ends to adjust the phase, so that the fourth slot-coupled phase shifter is formed.
The four patch slot coupling phase shifters formed by the multilayer slot coupling structure have a broadband power division phase shifting function, and the four slot coupling phase shifters have a broadband moving function. Therefore, stable two-dimensional and differential phase can be obtained in a wide bandwidth by optimally adjusting the parameters of the multilayer slot coupling structure.
The working principle of the invention is as follows:
a signal input by the input end 113 of the first composite microstrip line is output by one path through the output end 114 of the first composite microstrip line; one path couples the signal to the fourth composite microstrip line 22 through the first patch slot coupler, and then couples the signal to the output end 252 of the second linear microstrip line 25 through the fourth slot coupling phase shifter for output; one path couples the signal to the sixth composite microstrip line 24 through the second patch slot coupler, then couples the signal to the fifth composite microstrip line 23 through the second slot coupling phase shifter, and outputs the signal through the output end 233 of the fifth composite microstrip line 23; and one path couples a signal to the sixth composite microstrip line 24 through the second patch slot coupler, then couples the signal to the fifth composite microstrip line 23 through the second slot coupling phase shifter, couples the signal to the second composite microstrip line 12 through the fourth patch slot coupler, and outputs the signal from the output end 132 of the first straight microstrip line 13 through the first slot coupling phase shifter. After the signal input from the first composite microstrip line 11 passes through the multi-layer slot coupling structure, the signals at the output end 114 of the first composite microstrip line and the output end 132 of the first straight microstrip line are in phase, the signal at the output end 233 of the fifth composite microstrip line and the signal at the output end 252 of the line microstrip line are in phase, and the phases of the signals at the output end 114 of the first composite microstrip line and the output end 132 of the first straight microstrip line lag behind 180 degrees from the phases of the signal at the output end 233 of the fifth composite microstrip line and the signal at the output end 252 of the line microstrip line. The first composite microstrip input 113 is now a vertical difference beam input port.
After passing through the first slot coupling phase shifter, one path of the signal input by the input end 124 of the second composite microstrip line 12 is output by the output end 132 of the first linear microstrip line; one path couples the signal to the third composite microstrip line 21 through the third patch slot coupler, then couples the signal to the fourth composite microstrip line 22 through the third slot coupling phase shifter, and couples the signal to the output end 252 of the second linear microstrip line 25 through the fourth slot coupling phase shifter for output; one path couples the signal to the third composite microstrip line 21 through the third patch slot coupler, then couples the signal to the fourth composite microstrip line 22 through the third slot coupling phase shifter, and couples the signal to the output end 114 of the first composite microstrip line through the first patch slot coupler for output; one path along the second composite microstrip line 12 is coupled to the fifth composite microstrip line 23 through the fourth patch slot coupler, and is output through the output 233 of the fifth composite microstrip line 23. After the signal input from the input end 124 of the second composite microstrip line passes through the multi-layer slot coupling structure, the signals of the output ends 233 of the first and fifth composite microstrip lines 132 and 233 are in phase, the signals of the output ends 114 of the first and second composite microstrip lines are in phase, and the phases of the signals of the output ends 132 and 233 of the first and fifth composite microstrip lines lag behind the phases of the signals of the output ends 114 and 252 of the first and second composite microstrip lines by 180 °. The second complex microstrip input 124 is now a level difference beam input port.
A signal input from the input end 213 of the third composite microstrip line 21 is coupled to the second composite microstrip line 12 through the third patch slot coupler, coupled to the first straight microstrip line 13 along the second composite microstrip line through the first slot coupling phase shifter, and output from the output end 132 of the first straight microstrip line; one path couples the signal to the second composite microstrip line 12 through the third patch slot coupler, and couples the signal to the fifth composite microstrip line 23 through the fourth patch slot coupler along the second composite microstrip line, and outputs the signal from the output end 233 of the fifth composite microstrip line; one path of the third composite microstrip line is coupled to the fourth composite microstrip line 22 through the third slot-coupled phase shifter, is coupled to the second linear microstrip line 25 through the fourth slot-coupled phase shifter, and is output by the output end 252 of the second linear microstrip line; one path of the third composite microstrip line is coupled to the fourth composite microstrip line 22 by the third slot-coupled phase shifter, is coupled to the first composite microstrip line 11 by the first patch slot coupler, and is output by the output end 114 of the first composite microstrip line; after the signal input from the third composite microstrip line 21 passes through the multi-layer slot coupling structure, the signals at the output end 132 of the first straight microstrip line, the output end 233 of the fifth composite microstrip line, the output end 114 of the first composite microstrip line, and the output end 252 of the second straight microstrip line are in phase. The third complex microstrip input 213 is now the sum beam input.
A signal input from the input end 243 of the sixth composite microstrip line 24 is coupled to the fifth composite microstrip line 23 through the second slot coupling phase shifter in one path and is output from the output end 233 of the fifth composite microstrip line; one path couples the signal to the fifth composite microstrip line 23 through the second slot coupling shifter, couples the signal to the second composite microstrip line 12 through the fourth patch slot coupler, couples the signal to the first straight microstrip line 13 through the first slot coupling shifter, and outputs the signal through the output end 132 of the first straight microstrip line; one path couples a signal to a fifth composite microstrip line 23 through a second slot coupling shifter, couples the signal to a second composite microstrip line 12 through a fourth patch slot coupler, couples the signal to a third composite microstrip line 21 through a third patch slot coupler along the second composite microstrip line, couples the signal to a fourth composite microstrip line 22 through a third slot coupling phase shifter, couples the signal to a second linear microstrip line 25 through a fourth slot coupling phase shifter, and outputs the signal through a second linear microstrip line output end 252; in one path, a signal is coupled to the fifth composite microstrip line 23 through the second slot coupling shifter, the signal is coupled to the second composite microstrip line 12 through the fourth patch slot coupler, the signal is coupled to the third composite microstrip line 21 through the third patch slot coupler along the second composite microstrip line, the signal is coupled to the fourth composite microstrip line 22 through the third slot coupling phase shifter, the signal is coupled to the first composite microstrip line 11 through the first patch slot coupler, and the signal is output from the output end 114 of the first composite microstrip line. After the signal input from the input end 243 of the sixth composite microstrip line passes through the multi-layer slot coupling structure, the signals of the output end 132 of the first straight microstrip line and the output end 252 of the second straight microstrip line are in phase, the signals of the output end 114 of the first composite microstrip line and the output end 233 of the fifth composite microstrip line are in phase, and the phases of the signals of the output end 114 of the first composite microstrip line and the output end 233 of the fifth composite microstrip line lag behind the phases of the signals of the output end 132 of the first straight microstrip line and the output end 252 of the second straight microstrip line by 180 degrees. In this case, the input end 243 of the sixth composite microstrip line is a diagonal plane difference beam input port.
The technical effects of the invention are further explained by combining simulation experiments as follows:
1. simulation conditions and contents:
the invention utilizes commercial simulation software ANSYS HFSS v15.0 to respectively perform simulation calculation on the S parameters of the four input ports of the embodiment in the range of 7-13 GHz.
Simulation 1: the result of simulation calculation of the S parameter at the input end of the first composite microstrip line is shown in fig. 5.
Simulation 2: the result of simulation calculation of the S parameter at the input end of the second composite microstrip line is shown in fig. 6.
Simulation 3: the result of simulation calculation of the S parameter at the input end of the third composite microstrip line is shown in fig. 7.
And (4) simulation: the result of simulation calculation of the S parameter at the input end of the sixth composite microstrip line is shown in fig. 8.
2. And (3) simulation result analysis:
fig. 5 is a simulation calculation result of the S parameter of the input port of the first composite microstrip line. As shown in fig. 5(a), when the present invention employs a vertical difference beam feed, the present network has a good impedance match (less than-10 dB) within 7-13 GHz; the first composite microstrip line input port and the other three input ports have better port isolation (higher than 10 dB). As shown in FIG. 5(b), the present network has a stable transmission amplitude in 8-12 GHz. As shown in fig. 5(c), the present network has a stable transmission phase within 7-13GHz and the required phase difference is substantially stable at 180 °. In conclusion, the invention can realize vertical difference beam feeding in the frequency band of 8-12GHz (40% of the relative bandwidth), and has good broadband feeding amplitude and feeding phase stability.
Fig. 6 is a result of simulation calculation of the S parameter of the input port of the second composite microstrip line. As shown in fig. 6(a), when the present invention adopts the horizontal difference beam feed, the present network has good impedance matching (less than-10 dB) in 7-13 GHz; and the second composite microstrip line input port and the other three input ports have better port isolation (higher than 10 dB). As shown in FIG. 6(b), the present network has a stable transmission amplitude in 8-12 GHz. As shown in fig. 6(c), the present network has a stable transmission phase within 7-13GHz and the required phase difference is substantially stable at 180 °. In conclusion, the invention can realize horizontal difference beam feeding in the frequency band of 8-12GHz (40% of the relative bandwidth), and has good broadband feeding amplitude and feeding phase stability.
Fig. 7 is a simulation calculation result of the S parameter of the input port of the third composite microstrip line. As shown in fig. 7(a), when the present invention employs sum beam feeding, the present network has a good impedance match (less than-10 dB) within 7-13 GHz; and the third composite microstrip line input port and the other three input ports have better port isolation (higher than 10 dB). As shown in FIG. 7(b), the present network has a stable transmission amplitude in 8-12 GHz. As shown in fig. 7(c), the present network has a stable transmission phase within 7-13GHz and the phase difference is substantially stable at 0 °. In conclusion, the invention can realize beam feeding in the frequency band of 8-12GHz (40% of the relative bandwidth), and has good broadband feeding amplitude and feeding phase stability.
Fig. 8 is a result of simulation calculation of the S parameter of the input port of the sixth composite microstrip line. As shown in fig. 8(a), when the present invention employs sum beam feeding, the present network has a good impedance match (less than-10 dB) within 7-13 GHz; and the sixth composite microstrip line input port and the other three input ports have better port isolation (higher than 10 dB). As shown in FIG. 8(b), the present network has a stable transmission amplitude in 8-12 GHz. As shown in fig. 8(c), the present network has a stable transmission phase within 7-13GHz and the required phase difference is substantially stable at 180 °. In conclusion, the invention can realize diagonal plane difference beam feeding in the frequency band of 8-12GHz (40% of the relative bandwidth), and has good broadband feeding amplitude and feeding phase stability.
In conclusion, the invention can realize stable two-dimensional sum-difference phase output performance within the bandwidth of 8-12GHz (40%).
The above description is only a preferred example of the present invention and does not constitute any limitation to the present invention, and it is obvious to those skilled in the art that various modifications and changes in form and detail, such as changes to various parameters of the feeding network structure, are possible based on the principle and structure of the present invention after understanding the content of the present invention and the design principle. Such modifications and variations that are based on the inventive idea are still within the protective scope of the claims of the invention.
Claims (5)
1. A broadband two-dimensional and differential phase comparison network based on a multilayer microstrip slot coupling structure is characterized by comprising a first dielectric plate (1) and a second dielectric plate (2) which are rectangular and are stacked up and down, wherein:
the upper-layer microstrip line distributed along one diagonal line is printed on the upper surface of the first dielectric plate (1), and the upper-layer microstrip line comprises a first composite microstrip line (11), a second composite microstrip line (12) and a first straight microstrip line (13); the first composite microstrip line (11) and the second composite microstrip line (12) are both composed of three smooth L-shaped microstrip lines connected through microstrip nodes, wherein the input end and the output end of the first composite microstrip line (11) are respectively positioned at the edges of the long side and the short side of the first dielectric slab (1); the input end of the second composite microstrip line (12) is positioned at the edge of the long edge opposite to the input end of the first composite microstrip line (11), and the open end is positioned close to the edge of the short edge opposite to the output end of the first composite microstrip line (11); the open end of the first straight microstrip line (13) is coupled with the open end of the second composite microstrip line (12), and the output end of the first straight microstrip line is positioned at the edge of the short edge of the output end of the first composite microstrip line (11); a metal floor (14) is printed on the lower surface of the first dielectric plate (1), circular gaps are etched in the projection positions of the metal floor (14) on the microstrip nodes on the first composite microstrip line (11) and the second composite microstrip line (12), and four linear gaps are also etched in the metal floor (14);
the lower surface of the second dielectric plate (2) is printed with lower microstrip lines which are distributed along a diagonal line intersecting with the projection of the diagonal line where the upper microstrip line is located, and the lower microstrip lines comprise a third composite microstrip line (21), a fourth composite microstrip line (22), a fifth composite microstrip line (23), a sixth composite microstrip line (24) and a second straight microstrip line (25); the third composite microstrip line (21) and the sixth composite microstrip line (24) both adopt a smooth L-shaped microstrip line structure with an arm provided with a microstrip node, the microstrip node on the third composite microstrip line (21) is positioned at the projection position of the microstrip node of the second composite microstrip line (12) close to the input end, the microstrip node on the sixth composite microstrip line (24) is positioned at the projection position of the microstrip node of the first composite microstrip line (11) close to the input end, and the input ends of the two composite microstrip lines are respectively positioned at the edge positions of the long edge of the dielectric slab; the output end of the second linear microstrip line (25) is positioned on the short side with the same position as the output end of the first composite microstrip line (11); the fourth composite microstrip line (22) and the fifth composite microstrip line (23) are both composed of two smooth L-shaped microstrip lines connected through microstrip nodes, the microstrip node on the fourth composite microstrip line (22) is positioned at the projection position of the first composite microstrip line (11) close to the microstrip node at the output end, the microstrip node on the fifth composite microstrip line (23) is positioned at the projection position of the second composite microstrip line (12) close to the microstrip node at the open end, wherein one open end of the fourth composite microstrip line (22) is coupled with the open end of the second linear microstrip line (25), the other open end is coupled with the open end of the third composite microstrip line (21), the output end of the fifth composite microstrip line (23) is positioned on the short side which is the same as the output end of the first straight microstrip line (13), and the open end is coupled with the open end of the sixth composite microstrip line (24);
four microstrip nodes on the upper layer microstrip line, four circular gaps at corresponding positions on the metal floor (14) and four microstrip nodes at corresponding positions on the lower layer microstrip line form four patch gap couplers; one of the four linear slots etched on the metal floor (14) corresponds to the coupling position of the open end of the first linear microstrip line (13) and the open end of the second composite microstrip line (12), and the other three slots correspond to the coupling position of the open end of the third composite microstrip line (21) and the open end of the fourth composite microstrip line (22), the coupling position of the open end of the fourth composite microstrip line (22) and the open end of the second linear microstrip line (25), and the coupling position of the open end of the fifth composite microstrip line (23) and the open end of the sixth composite microstrip line (24), so that four slot coupling phase shifters are formed.
2. The broadband two-dimensional and differential phase comparison network based on the multi-layer microstrip slot coupling structure according to claim 1, wherein two arms of the L-shaped microstrip line are perpendicular, and a joint is a smooth circular arc.
3. The broadband two-dimensional and differential phase comparison network based on the multi-layer microstrip slot coupling structure according to claim 1, wherein the microstrip node is a rectangular microstrip line with a circular, oval or smooth arc at four corners.
4. The wideband two-dimensional and differential phase comparison network based on the multi-layer microstrip slot coupling structure as claimed in claim 1, wherein the center of the microstrip node on the upper layer microstrip line, the center of the circular slot at the corresponding position on the metal floor (14), and the center of the microstrip node at the corresponding position on the lower layer microstrip line are all located on a normal line passing through the center of the microstrip node.
5. The broadband two-dimensional and differential phase comparison network based on the multi-layer microstrip slot coupling structure according to claim 1, wherein the open end of the second composite microstrip line (12), the open end of the first straight microstrip line (13), the open end of the third composite microstrip line (21), the open end of the fourth composite microstrip line (22), the open end of the fifth composite microstrip line (23), the open end of the sixth composite microstrip line (24), the open end of the second straight microstrip line (25), and both ends of the straight slot adopt fan-shaped structures.
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