CN111786556B - Dual-mode compensation system for peak current control mode boost converter - Google Patents

Dual-mode compensation system for peak current control mode boost converter Download PDF

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CN111786556B
CN111786556B CN202010779381.3A CN202010779381A CN111786556B CN 111786556 B CN111786556 B CN 111786556B CN 202010779381 A CN202010779381 A CN 202010779381A CN 111786556 B CN111786556 B CN 111786556B
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current
mode
switch tube
flip
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CN111786556A (en
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孟煦
尹勇生
孟睿锐
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Hefei University of Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/157—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators with digital control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0012—Control circuits using digital or numerical techniques
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0025—Arrangements for modifying reference values, feedback values or error values in the control loop of a converter

Abstract

The invention relates to the technical field of power management, in particular to a dual-mode compensation system for a peak current control mode boost converter, which comprises a current integration module, a threshold comparison module, a logic control module and a capacitance multiplication module, wherein the current integration module is used for outputting a periodic voltage waveform with load current information; the threshold comparison module is used for outputting a trigger pulse or a low level; the logic control module outputs an enable signal to determine the equivalent capacitance of the capacitance multiplication module, change the parameters of the compensation network and realize the switching of dual-mode compensation. According to the invention, the compensation network parameters are adjusted by detecting the load current, so that the transient enhancement function of the boost converter in the face of switching from light load to heavy load is realized, and the loop stability of the boost converter in the face of switching from heavy load to light load is improved.

Description

Dual-mode compensation system for peak current control mode boost converter
Technical Field
The invention relates to the technical field of power management, in particular to a dual-mode compensation system for a peak current control mode boost converter.
Background
With the rapid development of modern electronic technology, the requirements of electronic products on power management circuits are higher and higher, mainly expressed in the aspects of output voltage stability, transient response performance, size of the power management circuits and the like. The switching power supply is widely applied to electronic products due to the characteristics of small volume, high efficiency, wide power supply voltage range and the like. When the electronic product is actually applied, the situation of sudden change of load current often occurs. The switching power supply is often used as the first stage of a power management circuit of an electronic product, and needs good stability and load transient response performance to ensure the normal operation of the electronic product.
The switching power supply system is a nonlinear time-varying system, and an alternating current small signal model needs to be established when system performance research is carried out. The performance index of the switching power supply depends on the loop characteristics under the alternating current small signal model. In order to meet the application requirements of the switching power supply, a proper compensation network needs to be designed to obtain the expected loop characteristics. The loop characteristics are greatly limited due to the presence of the right half-plane zero in the boost converter. The traditional compensation network design is generally based on a zero-pole placement method or a K-factor method, and can obtain better loop characteristics under specific load conditions. However, in practical applications, the boost converter has a large load variation range, and the conventional compensation network design needs to take account of the whole load range. When the boost converter is switched from light load to heavy load, the recovery time of the voltage at the output end is longer, and the transient response performance of the load is insufficient; when the boost converter is switched to light load in the face of heavy load, the voltage of the output end vibrates, and the stability of a loop is insufficient.
Disclosure of Invention
It is an object of the present invention to overcome the problems of the prior art and to provide a dual mode compensation system for a peak current controlled mode boost converter which addresses at least to some extent the problems of the prior art.
In order to achieve the technical purpose and achieve the technical effect, the invention is realized by the following technical scheme:
a dual-mode compensation system for a peak current control mode boost converter comprises a current integration module, a threshold comparison module, a logic control module and a capacitance multiplication module, wherein,
the current integration module is used for sampling current of the power switch tube when the power switch tube is switched on, simultaneously charging the capacitor, discharging the capacitor when the power switch tube is switched off, and outputting periodic voltage waveform with load current information;
the threshold comparison module is used for comparing the voltage waveform output by the current integration module with a threshold and outputting a trigger pulse or a low level according to the peak value of the voltage waveform output by the current integration module;
the logic control module demodulates the output signal of the threshold comparison module, outputs an enabling signal to determine the equivalent capacitance of the capacitance multiplication module, changes the parameters of the compensation network and realizes the switching of dual-mode compensation.
Preferably, the current integration module is composed of a current mirror circuit, an integration capacitor and a switch tube for controlling the charging and discharging state of the integration capacitor, the control signal connected with the grid electrode of the switch tube is the inverse logic of the driving signal of the power tube, and is obtained by the control signal of the power switch tube through a first-stage inverter,
when the power switch tube is conducted, the switch tube is turned off, the sampling current of the power switch tube is copied by the current mirror circuit according to a certain proportionality coefficient and then charges the integrating capacitor, and the voltage of the output end of the current integrating module continuously rises;
when the power switch tube is turned off, the switch tube is turned on, the integrating capacitor discharges, the voltage at the output end of the current integrating module decreases, the process is repeated in each switching period, and the output end of the current integrating module outputs a periodic voltage waveform VI。
Preferably, the threshold comparison module is composed of a current mirror circuit, a comparator and an inverter, a non-inverting input terminal of the threshold comparison module is connected to an output terminal of the current integration module, an inverting input terminal of the threshold comparison module is connected to a preset threshold voltage, and when the boost converter works in a heavy load mode and a light load mode, an output terminal Vcomp of the threshold comparison module outputs a trigger pulse and a low level respectively.
Preferably, the logic control module consists of a D flip-flop, an inverter and a two-input and gate, the logic control module has two input ends and an output end, one input end is connected with the output end of the threshold comparison module, the other input end is connected with the control signal of the power switching tube, the input ends of the inverters U1 and U2 are grounded, the output ends are respectively connected with the D ends of the flip-flops D1 and D2, the input end of the inverter U3 is connected with the clk end of the flip-flop D2, and the output end is connected with the clk end of the flip-flop D3; the clk end of the flip-flop D1 is connected with the output end of the threshold comparison module, the Q end of the flip-flop D1 is connected with one input end of the two-input AND gate U4, the Reset end of the flip-flop D1 is connected with the output end of the two-input AND gate U4, the clk end of the flip-flop D2 is connected with a power switch tube control signal, the Q end of the flip-flop D2 is connected with the other input end of the two-input AND gate U4, the Reset end of the flip-flop D2 is connected with the output end of the two-input AND gate U2, the clk end of the flip-flop D3 is connected with the output end of the inverter U3, the D end of the flip-flop D3 is connected with the Q end of the flip-flop D2, the QN end of the flip-flop D3 is the output end EN of the logic control module, when the output end of the threshold comparison module outputs a constant low level, the output end EN.
Preferably, the capacitance multiplication module is composed of a current mirror circuit, a unity gain buffer, a capacitor and a switching tube, and two capacitors are applied to two capacitors in the traditional compensation networkThe capacitance multiplication module realizes control over equivalent capacitance values of two compensation capacitors, namely, the boost converter works under the condition of heavy load, the two capacitance multiplication modules provide one group of equivalent capacitance values to form a compensation network under the heavy load mode, when the boost converter works under the condition of light load, the two capacitance multiplication modules provide the other group of equivalent capacitance values to form a compensation network under the light load mode, when the output end EN of the logic control module is set to be 1, the switch tube is switched off, and the equivalent capacitance of the capacitance multiplication circuit is CXWhen the output end EN of the logic control module is set to be 0, the switch tube is conducted, and the equivalent capacitance of the capacitance multiplication circuit is (K +1) CXDifferent EN signals realize different compensation network parameters, the compensation network is in a heavy load compensation mode when EN is 1, and the compensation network is in a light load compensation mode when EN is 0.
The operating principle of the dual-mode compensation system for the peak current control mode boost converter comprises the following steps:
the current integration module integrates the sampling current when the switching tube is conducted, so that a periodic voltage waveform with load current information is obtained, the periodicity is realized through a switching signal with fixed frequency, and the inverse logic Ctrl _ SW _ N of a control signal of the power switching tube is adopted; the load current information is represented by the peak value of the periodic voltage waveform, and the average value I of the current of the power switch tube in the conduction stage of each switching period can be obtained by the characteristics of the boost converterLThe peak value V of the periodic voltage waveform can be obtained from the characteristics of the integrating circuitI_PEAK：
Figure BDA0002619638240000041
ILIn the expression of (1)OIs the load current, D is the duty ratio of the power tube driving signal, VI_PEAKIn the formula (II) in which R isIIs the ratio of the integral current to the inductive current when the switching tube is on, CIT is the period of the power tube driving signal, from VI_PEAKV can be seen from the expressionIThe peak value of the signal is proportional to the load current;
the threshold comparison module will compare VIWith a predetermined threshold value VthComparing, outputting trigger pulse or low level at output end, and when the boost converter is in heavy load mode, i.e. the load current value is greater than the threshold value, VI_PEAKGreater than VthThe threshold comparison module outputs a trigger pulse, and when the boost converter works in a light load mode, namely the load current value is smaller than the threshold value, VI_PEAKLess than VthThe threshold comparison module outputs a low level;
the logic control module demodulates the output signal of the threshold comparison module: when the boost converter works in a heavy load mode, namely the threshold comparison module outputs a trigger pulse, the output end of the logic control module is set to be 1, and when the boost converter works in a light load mode, namely the threshold comparison module outputs a low level, the output end of the logic control module is set to be 0;
the switch tube of the capacitance multiplication module is controlled by the output end of the logic control module, when the boost converter works in a heavy-load mode, namely the output end of the logic control module is arranged at 1, the switch tube of the capacitance multiplication module is switched off, namely the equivalent capacitance of the module is unchanged and is still CX(ii) a When the boost converter works in a light load mode, namely the output end of the logic control module is arranged at 0, the switch tube of the capacitance multiplication module is conducted, and the equivalent capacitance of the module is increased to (K +1) CX，From KCL law:
Figure BDA0002619638240000051
so when EN is 0, the equivalent capacitance of the capacitance multiplication module is (K +1) CXHere, CXThe boost converter comprises compensation capacitors C1 and C2, namely an EN signal can increase or decrease the compensation capacitors C1 and C2 at the same time, the adjustment of a compensation capacitance value is realized through a load current detection technology, a transient enhanced compensation network parameter under a heavy load mode and a compensation network parameter with improved stability under a light load mode are obtained, when the boost converter works in the heavy load mode, the EN signal is set to be 1, and an equivalent capacitor of a capacitance multiplication module is CXHigh frequency of the compensation zero point, so as to be raisedWhen the voltage converter is switched from light load to heavy load, the time constant of the load transient recovery process is smaller, the load transient recovery process is faster, transient enhancement is realized, when the boost converter works in a light load compensation mode, an EN signal is set to be 0, and the equivalent capacitance of the capacitance multiplication module is (K +1) CXAnd the compensation capacitance value is larger, and the compensation zero frequency is lower, so that when the boost converter is switched from heavy load to light load, the loop phase margin is larger, and the stability is stronger.
The invention has the beneficial effects that: aiming at the problems that the transient response is poor when the traditional compensation technology is switched from light load to heavy load and the stability is poor when the heavy load is switched to the light load loop, the invention provides a dual-mode compensation technology for controlling a boost converter in a peak current mode, which comprises the following steps: when the load current is detected to be larger than the threshold value, the compensation network is switched to a heavy load compensation mode to enhance the transient response of the boost converter; when the load current is detected to be smaller than the threshold value, the compensation network is switched to a light-load compensation mode to improve the stability of the boost converter. The load current detection is realized through integration, the influence of instant conduction ringing of the switch tube is weakened, and the precision and reliability of the load current detection are improved. The design idea of adjusting the compensation network parameter of the boost converter by detecting the load current is provided. The background of the application of the invention is a boost converter, but the dual-mode compensation technology provided by the invention can be adopted for an inductive switching power supply (such as a buck converter, a buck-boost converter, a flyback converter and the like).
Drawings
In order to more clearly illustrate the technical solutions of the embodiments of the present invention, the drawings used in the description of the embodiments will be briefly introduced below, and it is obvious that the drawings in the following description are only some embodiments of the present invention, and it is obvious for those skilled in the art that other drawings can be obtained according to the drawings without creative efforts.
FIG. 1 is a schematic diagram of the circuit structure of the present invention;
FIG. 2 is a schematic diagram of a circuit structure of the current integration module according to the present invention;
FIG. 3 is a schematic circuit diagram of a threshold comparison module according to the present invention;
FIG. 4 is a schematic circuit diagram of the logic control module according to the present invention;
FIG. 5 is a schematic diagram of a circuit structure of the capacitance multiplication module according to the present invention;
FIG. 6 is a diagram of a power switch tube current waveform during a switching cycle in accordance with the present invention;
FIG. 7 is a graph of the voltage waveform at the output of the current integration module during one switching cycle in accordance with the present invention;
FIG. 8 is a schematic diagram of the overload mode threshold comparison module of the present invention;
FIG. 9 is a schematic diagram of the operation of the light load mode threshold comparison module according to the present invention;
FIG. 10 is a schematic diagram of the heavy load mode logic control module of the present invention;
FIG. 11 is a schematic diagram of the operation of the light load mode logic control module of the present invention;
FIG. 12 is a small signal model diagram of a light load mode capacitance multiplication module according to the present invention;
FIG. 13 is a Bode plot of the compensation network in two compensation modes of the present invention;
FIG. 14 is a schematic view of the load transient enhancement of the present invention.
Detailed Description
In order to make the technical means, the creation characteristics, the achievement purposes and the effects of the invention easy to understand, the technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, but not all the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
And (3) dual-mode compensation: namely, the dual-mode compensation network, the switching of the compensation network is made according to the magnitude of the load current value. When the load current is larger than the threshold value, the compensation network is switched to a heavy load compensation mode; when the load current is less than the threshold, the compensation network switches to a light load compensation mode.
Load transient response: the method is characterized in that when the load current at the output end changes in a step mode, the transient waveform of the voltage at the output end, the performance indexes of the transient response of the load mainly have the sizes of overshoot and undershoot and the transient recovery time of the load.
Referring to fig. 1-14, fig. 1-14 show a dual-mode compensation system for a peak current control mode boost converter, including a current integration module, a threshold comparison module, a logic control module, and a capacitance multiplication module, where the current integration module includes a current mirror circuit, an integration capacitor, and a switching tube for controlling the charging/discharging state of the integration capacitor, as shown in fig. 2. The control signal connected with the grid electrode of the switch tube is the inverse logic of the driving signal of the power tube, and the control signal of the power tube is obtained by passing through a first-stage phase inverter. When the power switch tube is conducted, the switch tube is turned off, the sampling current of the power switch tube is copied by the current mirror circuit according to a certain proportionality coefficient and then charges the integrating capacitor, and the voltage of the output end of the current integrating module continuously rises; when the power switch tube is turned off, the switch tube is turned on, the integrating capacitor discharges, and the voltage of the output end of the current integrating module drops. The above process is repeated in each switching period, and the output end of the current integration module outputs a periodic voltage waveform VI。
The threshold comparison module is composed of a current mirror circuit, a comparator and an inverter, and is specifically shown in fig. 3. The non-inverting input end of the threshold comparison module is connected with the output end of the current integration module, and the inverting input end of the threshold comparison module is connected with a preset threshold voltage. When the boost converter works in a heavy load mode and a light load mode, the output end Vcomp of the threshold comparison module respectively outputs trigger pulses and low levels.
The logic control module is composed of a D flip-flop, a phase inverter and a two-input and gate, and has two input terminals and an output terminal, one input terminal is connected to the output terminal of the threshold comparison module, and the other input terminal is connected to the power switch tube control signal, as shown in fig. 4. The specific technical scheme is as follows: the input ends of the inverters U1 and U2 are grounded, and the output ends are respectively connected with the D ends of the flip-flops D1 and D2; the input end of the inverter U3 is connected with the clk end of the flip-flop D2, and the output end of the inverter U3 is connected with the clk end of the flip-flop D3; the clk end of the trigger D1 is connected with the output end of the threshold comparison module, the Q end of the trigger D1 is connected with one input end of the two-input AND gate U4, and the Reset end of the trigger D1 is connected with the output end of the two-input AND gate U4; the clk end of the trigger D2 is connected with a power switch tube control signal, the Q end of the trigger D2 is connected with the other input end of the two-input AND gate U4, and the Reset end of the trigger D2 is connected with the output end of the two-input AND gate U2; the clk end of the flip-flop D3 is connected with the output end of the inverter U3, the D end of the flip-flop D3 is connected with the Q end of the flip-flop D2, and the QN end of the flip-flop D3 is the output end EN of the logic control module. When the output end of the threshold comparison module outputs a constant low level, the output end EN of the logic control module is set to be 0; when the output end of the threshold comparison module outputs the periodic pulse, the output end EN of the logic control module is set to be 1.
The capacitance multiplication module is composed of a current mirror circuit, a unity gain buffer, a capacitor and a switch tube, and is specifically shown in fig. 5. The invention applies two capacitance multiplication modules aiming at two capacitors in the traditional compensation network, and realizes the control of equivalent capacitance values of the two compensation capacitors. Namely, under the condition that the boost converter works under heavy load, the two capacitance multiplication modules provide a group of equivalent capacitance values to form a compensation network under a heavy load mode; when the boost converter works under the condition of light load, the two capacitance multiplication modules provide another group of equivalent capacitance values to form a compensation network under the light load mode. When the output end EN of the logic control module is set to be 1, the switch tube is turned off, and the equivalent capacitance of the capacitance multiplying circuit is CX(ii) a When the output end EN of the logic control module is set to be 0, the switch tube is conducted, and the equivalent capacitance of the capacitance multiplication circuit is (K +1) CX. Different EN signals realize different compensation network parameters, the compensation network is in a heavy load compensation mode when EN is 1, and the compensation network is in a light load compensation mode when EN is 0.
The working principle of the invention is as follows:
the current integration module integrates the sampling current when the switch tube is conducted, so that a periodic voltage waveform with load current information is obtained. The periodicity is realized by a switching signal with fixed frequency, and the inverse logic Ctrl _ SW _ N of a control signal of a power switching tube is adopted; load(s)The current information is represented by the peak value of the periodic voltage waveform, the average value IL of the current in the conduction stage of the power switch tube in each switching period can be obtained by the characteristics of the boost converter, and the peak value V of the periodic voltage waveform can be obtained by the characteristics of the integrating circuitI_PEAK：
Figure BDA0002619638240000101
ILIn the expression of (1)OD is the duty ratio of the power tube driving signal; vI_PEAKIn the expression (RI) is the ratio of the integral current to the inductive current when the switch tube is conducted, CI is the integral capacitance, and T is the period of the power tube driving signal. From above VI_PEAKThe expression shows that the peak value of the VI signal is proportional to the load current. The current waveform of the power switch tube in one switching period is shown in fig. 6, and the voltage waveform of the output end of the current integration module in one switching period is shown in fig. 7.
The threshold comparison module will compare VICompared with a preset threshold value Vth, the output end outputs a trigger pulse or a low level. When the boost converter is operated in a heavy load mode, i.e. the load current value is greater than a threshold value, VI_PEAKIf the threshold value is larger than the Vth, the threshold value comparison module outputs a trigger pulse, and the working principle is as shown in FIG. 8; when the boost converter operates in a light load mode, i.e. the load current value is less than a threshold value, VI_PEAKLess than Vth, the threshold comparison module outputs a low level, and the operation principle is as shown in fig. 9.
The logic control module demodulates the output signal of the threshold comparison module: when the boost converter works in the heavy-load mode, that is, the threshold comparison module outputs the trigger pulse, the output end of the logic control module is set to 1, and the working principle is as shown in fig. 10; when the boost converter operates in the light load mode, that is, the threshold comparison module outputs a low level, the output terminal of the logic control module is set to 0, and the operation principle is as shown in fig. 11.
The switch tube of the capacitance multiplication module is controlled by the output end of the logic control module, and when the boost converter works in a heavy-load mode, namely the output end of the logic control module is arranged at 1, electricity is suppliedThe switch tube of the capacitance multiplication module is turned off, namely the equivalent capacitance of the module is not changed and is still CX(ii) a When the boost converter works in a light load mode, namely the output end of the logic control module is arranged at 0, the switch tube of the capacitance multiplication module is conducted, and the equivalent capacitance of the module is increased to (K +1) CXThe principle of capacitance multiplication is shown in fig. 12. From KCL law:
Figure BDA0002619638240000111
so when EN is 0, the equivalent capacitance of the capacitance multiplication module is (K +1) CX. Note that C hereXIncluding the compensation capacitors C1 and C2 in fig. 1, the EN signal may increase or decrease the compensation capacitors C1 and C2 at the same time. The compensation capacitance value is adjusted by the load current detection technology, so that a transient enhanced compensation network parameter in a heavy load mode and a compensation network parameter with improved stability in a light load mode are obtained, and the baud graphs of the two compensation modes are shown in fig. 13. When the boost converter works in a heavy-load mode, an EN signal is set to be 1, and the equivalent capacitance of the capacitance multiplication module is CXThe frequency of the compensation zero point is high, so that when the boost converter is switched from light load to heavy load, the time constant of the load transient recovery process is smaller, the load transient recovery process is faster, and transient enhancement is realized, as shown in fig. 14; when the boost converter works in a light load compensation mode, the EN signal is set to be 0, and the equivalent capacitance of the capacitance multiplication module is (K +1) CXAnd the compensation capacitance value is larger, and the compensation zero frequency is lower, so that when the boost converter is switched from heavy load to light load, the loop phase margin is larger, and the stability is stronger.
It is noted that, herein, relational terms such as first and second, and the like may be used solely to distinguish one entity or action from another entity or action without necessarily requiring or implying any actual such relationship or order between such entities or actions. Also, the terms "comprises," "comprising," or any other variation thereof, are intended to cover a non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements does not include only those elements but may include other elements not expressly listed or inherent to such process, method, article, or apparatus. Without further limitation, an element defined by the phrase "comprising an … …" does not exclude the presence of other identical elements in a process, method, article, or apparatus that comprises the element.
The preferred embodiments of the invention disclosed above are intended to be illustrative only. The preferred embodiments are not intended to be exhaustive or to limit the invention to the precise embodiments disclosed. Obviously, many modifications and variations are possible in light of the above teaching. The embodiments were chosen and described in order to best explain the principles of the invention and the practical application, to thereby enable others skilled in the art to best utilize the invention. The invention is limited only by the claims and their full scope and equivalents.

Claims (5)

1. A dual-mode compensation system for a peak current control mode boost converter is characterized by comprising a current integration module, a threshold comparison module, a logic control module and a capacitance multiplication module, wherein,
the current integration module is used for sampling current of the power switch tube when the power switch tube is switched on, simultaneously charging the capacitor, discharging the capacitor when the power switch tube is switched off, and outputting periodic voltage waveform with load current information;
the threshold comparison module is used for comparing the voltage waveform output by the current integration module with a threshold and outputting a trigger pulse or a low level according to the peak value of the voltage waveform output by the current integration module;
the logic control module demodulates the output signal of the threshold comparison module, outputs an enable signal to determine the equivalent capacitance of the capacitance multiplication module, changes the parameters of the compensation network, and realizes the switching of dual-mode compensation, namely, the two capacitance multiplication modules provide one group of equivalent capacitance values to form the compensation network in a heavy load mode when the boost converter works in a heavy load condition, and the two capacitance multiplication modules provide the other group of equivalent capacitance values to form the compensation network in a light load mode when the boost converter works in a light load condition.
2. The dual-mode compensation system of claim 1, wherein the current integration module comprises a current mirror circuit, an integration capacitor, and a switch tube for controlling the charging/discharging status of the integration capacitor, the control signal connected to the gate of the switch tube is the inverse logic of the driving signal of the power switch tube, and is obtained by passing the control signal of the power switch tube through a first-stage inverter,
when the power switch tube is conducted, the switch tube is turned off, the sampling current of the power switch tube is copied by the current mirror circuit according to a certain proportionality coefficient and then charges the integrating capacitor, and the voltage of the output end of the current integrating module continuously rises;
when the power switch tube is turned off, the switch tube is turned on, the integrating capacitor discharges, the voltage at the output end of the current integrating module decreases, the process is repeated in each switching period, and the output end of the current integrating module outputs a periodic voltage waveform VI。
3. The dual-mode compensation system of claim 1, wherein the threshold comparison module comprises a current mirror circuit, a comparator and an inverter, the non-inverting input of the threshold comparison module is connected to the output of the current integration module, the inverting input of the threshold comparison module is connected to a predetermined threshold voltage, and the output of the threshold comparison module, Vcomp, outputs a trigger pulse and a low level when the boost converter operates in the heavy load mode and the light load mode.
4. The dual-mode compensation system for the peak current control mode boost converter according to claim 1, wherein said logic control module comprises a D flip-flop, an inverter and a two-input and gate, the logic control module has two input terminals and an output terminal, one input terminal is connected to the output terminal of the threshold comparison module, the other input terminal is connected to the power switch tube control signal, the input terminals of the inverters U1 and U2 are grounded, the output terminals are respectively connected to the D terminals of the flip-flops D1 and D2, the input terminal of the inverter U3 is connected to the clk terminal of the flip-flop D2, and the output terminal is connected to the clk terminal of the flip-flop D3; the clk end of the flip-flop D1 is connected with the output end of the threshold comparison module, the Q end of the flip-flop D1 is connected with one input end of the two-input AND gate U4, the Reset end of the flip-flop D1 is connected with the output end of the two-input AND gate U4, the clk end of the flip-flop D2 is connected with a power switch tube control signal, the Q end of the flip-flop D2 is connected with the other input end of the two-input AND gate U4, the Reset end of the flip-flop D2 is connected with the output end of the two-input AND gate U2, the clk end of the flip-flop D3 is connected with the output end of the inverter U3, the D end of the flip-flop D3 is connected with the Q end of the flip-flop D2, the QN end of the flip-flop D3 is the output end EN of the logic control module, when the output end of the threshold comparison module outputs a constant low level, the output end EN.
5. The dual-mode compensation system of claim 1, wherein the capacitance multiplication module comprises a current mirror circuit, a unity gain buffer, a capacitor and a switch, and for two capacitors in a conventional compensation network, two capacitance multiplication modules are applied to control equivalent capacitance values of two compensation capacitors, when an output end EN of the logic control module is set to 1, the switch is turned off, and the equivalent capacitance of the capacitance multiplication circuit is CXWhen the output end EN of the logic control module is set to be 0, the switch tube is conducted, and the equivalent capacitance of the capacitance multiplication circuit is (K +1) CXDifferent EN signals realize different compensation network parameters, the compensation network is in a heavy load compensation mode when EN is 1, and the compensation network is in a light load compensation mode when EN is 0.
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