CN111711375A - Neutral point active clamping three-level inverter, control method and control device - Google Patents
Neutral point active clamping three-level inverter, control method and control device Download PDFInfo
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- CN111711375A CN111711375A CN202010594975.7A CN202010594975A CN111711375A CN 111711375 A CN111711375 A CN 111711375A CN 202010594975 A CN202010594975 A CN 202010594975A CN 111711375 A CN111711375 A CN 111711375A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/483—Converters with outputs that each can have more than two voltages levels
- H02M7/487—Neutral point clamped inverters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention is suitable for the technical field of inverters, and provides a midpoint active clamping three-level inverter, a control method and a control device, wherein the midpoint active clamping three-level inverter comprises the following components: the bridge arm output end is connected with the bridge arm unit; the bridge arm unit comprises a first switch tube, a second switch tube, a third switch tube, a fourth switch tube, a first switch tube, a second switch tube, a third switch tube and a fourth switch tube, wherein the first diode, the second diode, the third diode and the fourth diode are connected in anti-parallel; the clamping unit comprises a fifth switching tube, a sixth switching tube, a fifth diode and a sixth diode which are connected with the fifth switching tube and the sixth switching tube in an anti-parallel mode; the fifth diode and the sixth diode are silicon carbide diodes. The invention can reduce the uneven heating of each switching tube and improve the electric energy conversion efficiency and stability.
Description
Technical Field
The invention belongs to the technical field of inverters, and particularly relates to a midpoint active clamping three-level inverter, a control method and a control device.
Background
The inverter is an electric energy conversion device for converting direct current into alternating current, and in practical application, two-level and three-level topologies are more adopted, wherein the three-level topologies are divided into a T-type three-level topology, an I-type three-level topology, a midpoint active clamping three-level topology and the like. The existing expansion and control processing scheme of the inverter is as follows: t-type three-level is suitable for 1000V system due to the limitation of switch tube specification, and I-type three-level can select switch tubes with different specifications to respectively correspond to 1000V system and 1500V system. But the performance of an inner tube and a clamping diode in the I-type three-level middle tube is greatly limited, a clamping switch tube is added to the midpoint active clamping three-level middle tube, and the control is flexible. However, the clamp diode has large direct loss, and the heating of each switching tube is easy to be uneven. And each switch tube has low utilization ratio, so that each switch tube is influenced by the stress between the switch tubes, and the electric energy conversion efficiency of the circuit is low and the stability is poor.
Disclosure of Invention
The embodiment of the invention provides a midpoint active clamping three-level inverter, aiming at solving the problems of uneven heating of each switching tube, low electric energy conversion efficiency and poor stability in a circuit.
In a first aspect, an embodiment of the present invention provides a midpoint active clamped three-level inverter, including: the bridge arm comprises a bridge arm unit, a clamping unit connected with the bridge arm unit and a bridge arm output end connected with the bridge arm unit;
the bridge arm unit comprises a first switch tube, a second switch tube, a third switch tube and a fourth switch tube which are sequentially connected in series, and a first diode, a second diode, a third diode and a fourth diode which are in inverse parallel connection with the first switch tube, the second switch tube, the third switch tube and the fourth switch tube in a one-to-one correspondence manner;
the clamping unit comprises a fifth switching tube, a sixth switching tube, a fifth diode and a sixth diode, wherein the fifth switching tube and the sixth switching tube are sequentially connected in series, the fifth diode and the sixth diode are connected in anti-parallel with the fifth switching tube and the sixth switching tube in a one-to-one correspondence mode, one end, far away from the sixth switching tube, of the fifth switching tube is arranged on a connecting line between the first switching tube and the second switching tube, and one end, far away from the fifth switching tube, of the sixth switching tube is arranged on a connecting line between the third switching tube and the fourth switching tube;
the bridge arm output end is arranged on a connecting line between the second switching tube and the third switching tube;
the fifth switch tube or the fifth diode and the second switch tube or the second diode form a first freewheeling circuit, the sixth switch tube or the sixth diode and the third switch tube or the third diode form a second freewheeling circuit, and the first freewheeling circuit and the second freewheeling circuit form a dual freewheeling circuit for changing a freewheeling path;
the fifth diode and the sixth diode are silicon carbide diodes.
In a second aspect, an embodiment of the present invention further provides a control method of a midpoint active clamping three-level inverter, where the control method is used for the midpoint active clamping three-level inverter provided in the above embodiment, and the method includes:
acquiring a first driving signal, a second driving signal, a third driving signal, a fourth driving signal, a fifth driving signal and a sixth driving signal corresponding to the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube and the sixth switching tube;
and controlling the on-off states of the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube and the sixth switching tube based on a preset power switching mode according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal and the sixth driving signal to form a double-follow current loop so as to realize a current conversion path and electric energy conversion.
In a third aspect, an embodiment of the present invention further provides a control apparatus for a midpoint active clamping three-level inverter, where the control apparatus is used for the midpoint active clamping three-level inverter provided in the foregoing embodiment, and the apparatus includes:
the acquisition unit is used for acquiring a first driving signal, a second driving signal, a third driving signal, a fourth driving signal, a fifth driving signal and a sixth driving signal corresponding to the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube and the sixth switching tube;
and the control unit is used for controlling the on-off states of the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube and the sixth switching tube based on a preset power switching mode according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal and the sixth driving signal to form a double-follow current loop so as to realize a commutation path and electric energy conversion.
The silicon carbide diode has the advantages that the fifth diode and the sixth diode are silicon carbide diodes, so that the switching-on loss of the first switching tube and the fourth switching tube is reduced, the conduction of the fifth switching tube and the sixth switching tube is controlled, the direct-connection loss of the fifth diode and the sixth diode can be reduced, and the switching tubes can uniformly heat. And only the fifth diode and the sixth diode are silicon carbide diodes, so that the requirements of the silicon carbide diodes are reduced, and the material cost can be reduced. And a follow current path is changed by adopting a double follow current loop, so that the thermal stress among the switch tubes is dispersed. The sixth switching tube or the fifth switching tube corresponding to the half cycle is closed before the first switching tube and/or the fourth switching tube is switched on, so that the defect that the first switching tube and the fourth switching tube additionally generate switching loss due to the fact that the second diode and the third diode which are reversely connected in parallel are silicon diodes is avoided. The voltage stress of the corresponding switch tube is reduced, the forward through loss of the fifth diode and the sixth diode is reduced, the electric energy conversion efficiency of the circuit is improved, and the stability of the inverter in reliable operation is improved.
Drawings
Fig. 1 is a circuit diagram of a midpoint active clamp three-level inverter according to an embodiment of the present invention;
fig. 2 is a flowchart of a control method of a midpoint active clamped three-level inverter according to an embodiment of the present invention;
FIG. 3 is a schematic diagram of a positive and negative half cycle wave generation according to an embodiment of the present invention;
FIG. 4 is a schematic diagram of a modality provided by modality one in the embodiment of the present invention;
FIG. 5 is a schematic diagram of one mode provided by mode two in an embodiment of the present invention;
FIG. 6 is a schematic diagram of a mode provided by mode three in an embodiment of the present invention;
FIG. 7 is a schematic diagram of a mode provided by mode four in an embodiment of the invention;
FIG. 8 is a flowchart of a method provided by step 102 in an embodiment of the present invention;
FIG. 9 is a schematic illustration of a modality provided by modality five in an embodiment of the invention;
FIG. 10 is a schematic illustration of a mode provided by mode six in an embodiment of the invention;
FIG. 11 is a schematic diagram of a mode provided by mode seven in an embodiment of the invention;
FIG. 12 is a flow chart of another method provided by step 102 in an embodiment of the present invention;
fig. 13 is a schematic structural diagram of a control device of a midpoint active clamped three-level inverter according to an embodiment of the present invention;
FIG. 14 is a schematic diagram of a structure provided by the control unit in the embodiment of the present invention;
fig. 15 is another schematic structural diagram provided by the control unit in the embodiment of the present invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention.
According to the invention, the advantages that the fifth diode and the sixth diode are silicon carbide diodes are adopted, the turn-on loss of the first switching tube and the fourth switching tube is reduced, the turn-on loss of the fifth diode and the sixth diode can be reduced by controlling the turn-on of the fifth switching tube and the sixth switching tube, and the switching tubes can uniformly heat. And only the fifth diode and the sixth diode are silicon carbide diodes, so that the requirements of the silicon carbide diodes are reduced, and the material cost can be reduced. And a follow current path is changed by adopting a double follow current loop, so that the thermal stress among the switch tubes is dispersed. The sixth switching tube or the fifth switching tube corresponding to the half cycle is closed before the first switching tube and/or the fourth switching tube is switched on, so that the defect that the first switching tube and the fourth switching tube additionally generate switching loss due to the fact that the second diode and the third diode which are reversely connected in parallel are silicon diodes is avoided. The voltage stress of the corresponding switch tube is reduced, the forward through loss of the fifth diode and the sixth diode is reduced, the electric energy conversion efficiency of the circuit is improved, and the stability of the inverter in reliable operation is improved.
Example one
As shown in fig. 1, fig. 1 is a circuit diagram of a midpoint active clamping three-level inverter according to an embodiment of the present invention, where the midpoint active clamping three-level inverter includes: the bridge arm comprises a bridge arm unit 2, a clamping unit 3 connected with the bridge arm unit 2 and a bridge arm output end 1 connected with the bridge arm unit 2.
The bridge arm unit 2 comprises a first switch tube T1, a second switch tube T2, a third switch tube T3 and a fourth switch tube T4 which are sequentially connected in series, and a first diode D1, a second diode D2, a third diode D3 and a fourth diode D4 which are connected in anti-parallel with the first switch tube T1, the second switch tube T2, the third switch tube T3 and the fourth switch tube T4 in a one-to-one correspondence manner.
The clamping unit 3 includes a fifth switch tube T5, a sixth switch tube T6, a fifth diode D5 and a sixth diode D6 connected in series in sequence, and connected in inverse parallel with the fifth switch tube T5 and the sixth switch tube T6 in one-to-one correspondence, one end of the fifth switch tube T5 far from the sixth switch tube T6 is disposed on a connection line between the first switch tube T1 and the second switch tube T2, and one end of the sixth switch tube T6 far from the fifth switch tube T5 is disposed on a connection line between the third switch tube T3 and the fourth switch tube T4.
And a bridge arm output end 1 arranged on a connecting line between the second switching tube T2 and the third switching tube T3.
The fifth switch tube T5 or the fifth diode D5 and the second switch tube T2 or the second diode D2 form a first freewheeling circuit, the sixth switch tube T6 or the sixth diode D6 and the third switch tube T3 or the third diode D3 form a second freewheeling circuit, and the first freewheeling circuit and the second freewheeling circuit form a dual freewheeling circuit for changing a freewheeling path.
The first switch tube T1, the second switch tube T2, the third switch tube T3, the fourth switch tube T4, the fifth switch tube T5 and the sixth switch tube T6 correspond to each other in a one-to-one manner and include a first MOS tube, a second MOS tube, a third MOS tube, a fourth MOS tube, a fifth MOS tube and a sixth MOS tube, or include a first triode, a second triode, a third triode, a fourth triode, a fifth triode and a sixth triode. The first switching tube T1, the second switching tube T2, the third switching tube T3, the fourth switching tube T4, the fifth switching tube T5 and the sixth switching tube T6 may be of the type of Si-IGBT (silicon insulated gate bipolar transistor). The bridge arm output end 1 is also connected with an inductor L.
The first switch tube T1 and the fourth switch tube may be referred to as an outer tube, and the second switch tube T2 and the third switch tube T3 may be referred to as an outer tube. The fifth switch transistor T5 and the sixth switch transistor T6 may be referred to as clamping transistors.
The first diode D1, the second diode D2, the third diode D3 and the fourth diode D4 include a first silicon diode, a second silicon diode, a third silicon diode and a fourth silicon diode in a one-to-one correspondence. The silicon DIODE can be represented by a Si-DIODE as well as a Si DIODE.
The fifth diode D5 and the sixth diode D6 are silicon carbide diodes. The silicon carbide diode may be a schottky diode, the two most important performance criteria of which are its low reverse recovery charge (Qrr) and recovery softening coefficient. The low reverse recovery charge Qrr greatly shortens the time required for the turn-off process, i.e. the reverse recovery time trr, when the diode voltage becomes reverse biased. The silicon carbide diode trr is less than 0.01 microseconds. It is convenient for use in the high frequency range. A high softening coefficient will reduce the emi noise generated by the diode turn-off and reduce the commutation operation interference. Silicon carbide DIODEs may be represented by SiC-DIODE, as well as SiC DIODEs.
The first freewheel loop may be referred to as a 0+ loop and the second freewheel loop may be referred to as a 0-loop. When only the first freewheeling circuit or the second freewheeling circuit works alone, the first freewheeling circuit or the second freewheeling circuit may be referred to as a single freewheeling circuit, and when the first freewheeling circuit and the second freewheeling circuit work simultaneously, the first freewheeling circuit and the second freewheeling circuit form a dual freewheeling circuit, which may be referred to as a dual freewheeling circuit 0+, 0-. When the dual-freewheel circuit performs freewheeling, the dual-freewheel circuit may be referred to as dual-freewheel 0+ and 0-freewheel.
In one embodiment of the present invention, the midpoint active clamping three-level inverter further includes a voltage dividing unit 4 connected to the bridge arm unit 2 and the clamping unit 3, respectively; the voltage dividing unit 4 comprises a first voltage dividing capacitor C1 and a second voltage dividing capacitor C2 which are sequentially connected in series, the first voltage dividing capacitor C1 is far away from one end of the second voltage dividing capacitor C2 and connected with one end of the first switch tube T1 and far away from one end of the second switch tube T2, the second voltage dividing capacitor C2 is far away from one end of the first voltage dividing capacitor C1 and connected with one end of the fourth switch tube T4 and far away from one end of the third switch tube T3. The first voltage-dividing capacitor C1, the fifth switch transistor T5 or the fifth diode D5, the second switch transistor T2 or the second diode D2 form a first freewheeling circuit, and the second voltage-dividing capacitor C2, the sixth switch transistor T6 or the sixth diode D6, the third switch transistor T3 or the third diode D3 form a second freewheeling circuit.
The first voltage-dividing capacitor C1 and the second voltage-dividing capacitor C2 perform voltage-dividing function to divide the voltage of the circuit. The first voltage-dividing capacitor C1 and the second voltage-dividing capacitor C2 can also play a role in filtering.
Specifically, an input end of the first switch tube T1 is connected to one end of the first voltage-dividing capacitor C1, which is far from the second voltage-dividing capacitor C2, an output end of the first switch tube T1 is connected to an input end of the second switch tube T2 and an input end of the fifth switch tube T5, an output end of the second switch tube T2 is connected to an input end of the third switch tube T3 and the bridge arm output end 1, an output end of the third switch tube T3 is connected to an input end of the fourth switch tube T4 and an output end of the sixth switch tube T6, and an output end of the fourth switch tube T4 is connected to one end of the second voltage-dividing capacitor C2, which is far from the first voltage-dividing capacitor C1.
A cathode of the first diode D1 is connected to an input end of the first switching tube T1, an anode of the first diode D1 is connected to an output end of the first switching tube T1, a cathode of the second diode D2 is connected to an input end of the second switching tube T2, an anode of the second diode D2 is connected to an output end of the second switching tube T2, a cathode of the third diode D3 is connected to an input end of the third switching tube T3, an anode of the third diode D3 is connected to an output end of the third switching tube T3, a cathode of the fourth diode D4 is connected to an input end of the fourth switching tube T4, an anode of the fourth diode D4 is connected to an output end of the fourth switching tube T4, a cathode of the fifth diode D5 is connected to an input end of the fifth switching tube T5, an anode of the fifth diode D5 is connected to an output end of the fifth switching tube T5, and a cathode of the sixth diode D6 is connected to an input end of the sixth switching tube T57324, the anode of the sixth diode D6 is connected to the output terminal of the sixth switching tube.
It can be understood that when the first switch transistor T1, the second switch transistor T2, the third switch transistor T3, the fourth switch transistor T4, the fifth switch transistor T5 and the sixth switch transistor T6 correspond to the first MOS transistor, the second MOS transistor, the third MOS transistor, the fourth MOS transistor, the fifth MOS transistor and the sixth MOS transistor one by one, corresponding input ends of the first switch transistor T1, the second switch transistor T2, the third switch transistor T3, the fourth switch transistor T4, the fifth switch transistor T5 and the sixth switch transistor T6 are all corresponding D poles (drains) of the first MOS transistor, the second MOS transistor, the third MOS transistor, the fourth MOS transistor, the fifth MOS transistor and the sixth MOS transistor.
The output ends corresponding to the first switching tube T1, the second switching tube T2, the third switching tube T3, the fourth switching tube T4, the fifth switching tube T5 and the sixth switching tube T6 are all the S poles (source electrodes) corresponding to the first MOS tube, the second MOS tube, the third MOS tube, the fourth MOS tube, the fifth MOS tube and the sixth MOS tube.
When the first switching tube T1, the second switching tube T2, the third switching tube T3, the fourth switching tube T4, the fifth switching tube T5 and the sixth switching tube T6 are corresponding to a first triode, a second triode, a third triode, a fourth triode, a fifth triode and a sixth triode one by one, corresponding input ends of the first switching tube T1, the second switching tube T2, the third switching tube T3, the fourth switching tube T4, the fifth switching tube T5 and the sixth switching tube T6 are all corresponding C poles (collector electrodes) of the first triode, the second triode, the third triode, the fourth triode, the fifth triode and the sixth triode.
The output ends corresponding to the first switch tube T1, the second switch tube T2, the third switch tube T3, the fourth switch tube T4, the fifth switch tube T5 and the sixth switch tube T6 are all E poles (emitting poles) corresponding to the first triode, the second triode, the third triode, the fourth triode, the fifth triode and the sixth triode.
The embodiment of the invention also provides a preset power switching mode and a driving signal of each switching tube, and flexibly controls the on-off of each switching tube and each diode according to the driving signal of each switching tube and the preset power switching mode to form the switching between the single follow current loop and the double follow current loop, so as to flexibly switch the current path and realize the electric energy conversion. The specific control method is as the specific steps and effects of the control method of the midpoint active clamp three-level inverter in the second embodiment.
In the embodiment of the present invention, the advantage that the fifth diode D5 and the sixth diode D6 are silicon carbide diodes is adopted, so that the turn-on loss of the first switch tube T1 and the fourth switch tube T4 is reduced, and the turn-on loss of the fifth diode D5 and the sixth diode D6 can be reduced by controlling the conduction of the fifth switch tube T5 and the sixth switch tube T6, so that the heat generation of the switch tubes is uniform. And only the fifth diode D5 and the sixth diode D6 are silicon carbide diodes, so that the requirements of the silicon carbide diodes are reduced, and the material cost can be reduced. And a follow current path is changed by adopting a double follow current loop, so that the thermal stress among the switch tubes is dispersed. Before the first switch tube T1 and/or the fourth switch tube T4 are turned on, the sixth switch tube T6 or the fifth switch tube T5 in the corresponding half cycle is turned off, so as to avoid the disadvantage that the first switch tube T1 and the fourth switch tube T4 additionally generate turn-on loss due to the fact that the second diode D2 and the third diode D3 which are inversely connected in parallel with the second switch tube T2 and the third switch tube T3 are silicon diodes. The voltage stress of the corresponding switch tube is reduced, the forward through loss of the fifth diode D5 and the sixth diode D6 is reduced, the electric energy conversion efficiency of the circuit is improved, and the stability of the inverter in reliable operation is improved.
Example two
As shown in fig. 2, fig. 2 is a flowchart of a control method of a midpoint active clamping three-level inverter provided in an embodiment of the present invention, which is used for the midpoint active clamping three-level inverter provided in the above embodiment, and the control method of the midpoint active clamping three-level inverter includes the following steps:
The first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal are used for driving the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube and the sixth switching tube. The first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal may be pulse signals, including a high level and a low level, and the pulse signals are turned on when the pulse signals are the high level and turned off when the pulse signals are the low level. The first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal may further include timing information. The first drive signal, the second drive signal, the third drive signal, the fourth drive signal, the fifth drive signal, and the sixth drive signal may be preset or temporarily generated.
Specifically, referring to fig. 3, fig. 3 is a schematic diagram of a wave generation situation during positive and negative half cycles according to an embodiment of the present invention. In fig. 3, Vge _ T1 to Vge _ T6 are respectively a first driving signal, a second driving signal, a third driving signal, a fourth driving signal, a fifth driving signal and a sixth driving signal corresponding to a first switching tube, a second switching tube, a third switching tube, a fourth switching tube, a fifth switching tube and a sixth switching tube. The overall logic of the fifth switching tube and the sixth switching tube to the third switching tube and the second switching tube is to switch on first and then switch off, the complementary wave generation between the first switching tube and the third switching tube, and the complementary wave generation between the second switching tube and the fourth switching tube. Fig. 3 includes the wave conditions of the positive half cycle 5 and the wave conditions of the negative half cycle 6.
In fig. 3, the dead zone between the on state of the first switching tube (fourth switching tube) and the off state of the third switching tube (second switching tube) is t 1.
The dead zone between the on state of the third switching tube (second switching tube) and the off state of the first switching tube (fourth switching tube) is t 2.
The fifth switching tube (the sixth switching tube) is integrally turned on and off along with the third switching tube (the second switching tube), the fifth switching tube (the sixth switching tube) is turned off before the fourth switching tube (the first switching tube) is turned on, and the fifth switching tube (the sixth switching tube) is turned on after the fourth switching tube (the first switching tube) is turned on t 7.
The delay from the switching on of the second switching tube (sixth switching tube) to the switching on of the third switching tube (second switching tube) is t 6.
The time delay from the turning-off of the fifth switching tube (the sixth switching tube) to the turning-off of the third switching tube (the second switching tube) is t 3.
And step 102, controlling the on-off states of the first switch tube, the second switch tube, the third switch tube, the fourth switch tube, the fifth switch tube and the sixth switch tube based on a preset power switching mode according to the first drive signal, the second drive signal, the third drive signal, the fourth drive signal and the sixth drive signal to form a double-follow current loop so as to realize a current conversion path and electric energy conversion.
Specifically, the preset power switching mode includes a forward power switching mode and a reverse power switching mode.
In an embodiment of the present invention, the forward power switching mode includes:
the first mode is as follows: and controlling the first switch tube and the second switch tube to be switched on.
Specifically, as shown in fig. 4, at this time, the forward output power of the circuit does not have reverse recovery basically because the fifth diode is a silicon carbide diode, so that the turn-on loss of the first switching tube can be greatly reduced, and the turn-on speed of the first switching tube can be increased under the same working condition. And enabling the current to flow to the output end of the bridge arm through the first switching tube and the second switching tube, and enabling the output end of the bridge arm to output a first preset level. The first preset level may be a P level, or may be referred to as a high level.
Mode two: on the basis of the mode one, the first switch tube, the second switch tube and the sixth switch tube are controlled to be switched on.
Specifically, as shown in fig. 5, at this time, the bridge arm outputs the first preset level, the current path is not changed, only the sixth switching tube is turned on, and the circuit still outputs power in the forward direction, so as to prepare for the follow current of the dual-follow current circuit. And enabling the current to flow to the output end of the bridge arm through the first switching tube and the second switching tube, wherein the output end of the bridge arm outputs a first preset level.
Mode three: on the basis of the mode two, the first switching tube is controlled to be turned off, and the fifth diode, the second switching tube, the sixth switching tube and the third diode are controlled to be turned on.
Specifically, as shown in fig. 6, the existence of the second freewheel circuit reduces the freewheel current of the SiC diode in the first freewheel circuit, so that the capacity of the fifth diode 5 can be reduced, the cost can be saved, and the existence of the dual freewheel circuit can disperse the thermal stress between the switching tubes. And enabling the current to flow to the output end of the bridge arm from a first follow current loop formed by the first voltage-dividing capacitor, the fifth diode and the second switch tube, and enabling the current to flow to the output end of the bridge arm from a second follow current loop formed by the second voltage-dividing capacitor, the sixth switch tube and the third diode, so that the follow current of the double follow current loop is realized, and the output end of the bridge arm outputs a second preset level.
And, modality four: and on the basis of the mode III, the sixth switching tube is controlled to be switched off, and the fifth diode and the second switching tube are controlled to be switched on.
Specifically, as shown in fig. 7, at this time, the single freewheeling circuit 0+ freewheels, and when the second preset level freewheeling is about to end, the sixth switching tube is turned off to prepare for turning on the first switching tube, so that the sixth switching tube is ensured to be turned off before the first switching tube is turned on, and the problem that the first switching tube is additionally subjected to turn-on loss due to the existence of the third diode (the third diode is a silicon diode) when the first switching tube is turned on can be avoided. And enabling current to flow to the output end of the bridge arm through a first follow current loop formed by the first voltage-dividing capacitor, the fifth diode and the second switch tube, and enabling the output end of the bridge arm to output a second preset level.
More specifically, as shown in fig. 8, step 102 includes the steps of:
And/or step 202, sequentially switching the output level of the output end of the bridge arm from the second preset level to the first preset level through the mode three, the mode four and the mode one according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal.
As can be seen from steps 201 and 202, the power switching path fully utilizes the advantage of the midpoint active clamp three-level dual freewheeling circuit in dispersing thermal stress between the switching tubes, and avoids the influence of the additional turn-on loss of the first switching tube caused by the Si diode serving as the third diode. Therefore, the level output by the output end of the bridge arm is switched, and the current transformation is further realized.
In an embodiment of the present invention, the reverse power switching mode includes:
a fifth mode: and controlling the third switching tube and the fifth switching tube to be switched off, and controlling the first diode and the second diode to be switched on.
Specifically, as shown in fig. 9, at this time, a current is caused to flow from the arm output terminal to the second diode and the first diode, and the arm output terminal outputs a P level.
A sixth mode: and on the basis of the mode five, controlling the fifth switching tube and the second diode to be switched on.
Specifically, as shown in fig. 10, the output is now passed through the single-wheeling circuit 0 +. The fifth switching tube is superior to the third switching tube in opening, and the fifth switching tube is switched by a small loop, so that the influence of larger parasitic parameters of a large loop on the loop switching can be reduced, and the voltage stress of the switching tube is reduced. And enabling the current to flow to the second diode, the fifth switching tube and the first voltage division capacitor from the output end of the bridge arm to form a first follow current loop, and enabling the output end of the bridge arm to output the P level.
And, modality seven: and on the basis of the mode six, controlling the fifth switching tube, the second diode, the sixth diode and the third switching tube to be switched on.
Specifically, as shown in FIG. 11, a dual-freewheel loop 0+, 0-output is formed at this time. Due to the double-loop chopping, the thermal stress between the switching tubes can be dispersed. Enabling current to flow from the output end of the bridge arm to the second diode, the fifth switching tube and the first voltage division capacitor to form a first follow current loop, and enabling the output end of the bridge arm to output a first preset level; and enabling the current to flow to a second follow current loop formed by the third switching tube, the sixth diode and the second voltage division capacitor from the output end of the bridge arm, wherein the output end of the bridge arm inputs a second preset level.
More specifically, as shown in fig. 12, step 102 includes:
And/or step 302, sequentially switching the output level of the output end of the bridge arm from the second preset level to the first preset level through the mode seven, the mode six and the mode five according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal.
As shown in steps 301 and 302, the power switching path employs double-loop chopping to reduce the voltage stress of the switching tubes and to disperse the thermal stress between the switching tubes.
It should be noted that the negative half-cycle commutation path is similar to the forward power switching and reverse power switching methods, and will not be described here.
In the embodiment of the present invention, a first driving signal, a second driving signal, a third driving signal, a fourth driving signal, a fifth driving signal, and a sixth driving signal corresponding to the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube, and the sixth switching tube are obtained; and controlling the on-off states of the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube and the sixth switching tube based on a preset power switching mode according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal and the sixth driving signal to form a double-follow current loop so as to realize a current conversion path and electric energy conversion. Therefore, the on-off conditions of each switch tube and each diode can be controlled through the driving signal of each switch tube and the preset power switching state, follow current is switched through the single follow current loop and the double follow current loop, the thermal stress between the switch tubes is reduced, the reverse recovery loss of the diodes is reduced, the electric energy conversion efficiency of the circuit is improved, and the stability of the reliable operation of the inverter is improved.
EXAMPLE III
As shown in fig. 13, fig. 13 is a schematic structural diagram of a control apparatus of a midpoint active clamping three-level inverter according to an embodiment of the present invention, where the control apparatus 400 of the midpoint active clamping three-level inverter includes:
the obtaining unit 401 is configured to obtain a first driving signal, a second driving signal, a third driving signal, a fourth driving signal, a fifth driving signal, and a sixth driving signal corresponding to the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube, and the sixth switching tube.
The first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal are used for driving the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube and the sixth switching tube. The first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal may be pulse signals, including a high level and a low level, and the pulse signals are turned on when the pulse signals are the high level and turned off when the pulse signals are the low level. The first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal may further include timing information. The first drive signal, the second drive signal, the third drive signal, the fourth drive signal, the fifth drive signal, and the sixth drive signal may be preset or temporarily generated.
Specifically, referring to fig. 3, it is a schematic diagram of a wave generation situation during positive and negative half cycles according to an embodiment of the present invention. In fig. 3, Vge _ T1 to Vge _ T6 are respectively a first driving signal, a second driving signal, a third driving signal, a fourth driving signal, a fifth driving signal and a sixth driving signal corresponding to a first switching tube, a second switching tube, a third switching tube, a fourth switching tube, a fifth switching tube and a sixth switching tube. The overall logic of the fifth switching tube and the sixth switching tube to the third switching tube and the second switching tube is to switch on first and then switch off, the complementary wave generation between the first switching tube and the third switching tube, and the complementary wave generation between the second switching tube and the fourth switching tube. Fig. 3 includes the wave conditions of the positive half cycle 5 and the wave conditions of the negative half cycle 6.
In fig. 3, the dead zone between the on state of the first switching tube (fourth switching tube) and the off state of the third switching tube (second switching tube) is t 1.
The dead zone between the on state of the third switching tube (second switching tube) and the off state of the first switching tube (fourth switching tube) is t 2.
The fifth switching tube (the sixth switching tube) is integrally turned on and off along with the third switching tube (the second switching tube), the fifth switching tube (the sixth switching tube) is turned off before the fourth switching tube (the first switching tube) is turned on, and the fifth switching tube (the sixth switching tube) is turned on after the fourth switching tube (the first switching tube) is turned on t 7.
The delay from the switching on of the second switching tube (sixth switching tube) to the switching on of the third switching tube (second switching tube) is t 6.
The time delay from the turning-off of the fifth switching tube (the sixth switching tube) to the turning-off of the third switching tube (the second switching tube) is t 3.
And a control unit 402, configured to control on-off states of the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube, and the sixth switching tube based on a preset power switching mode according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, and the sixth driving signal, so as to form a dual-freewheel loop, so as to implement a commutation path and electric energy conversion.
Specifically, the preset power switching mode includes a forward power switching mode and a reverse power switching mode.
In an embodiment of the present invention, the forward power switching mode includes:
the first mode is as follows: and controlling the first switch tube and the second switch tube to be switched on.
Specifically, as shown in fig. 4, at this time, the forward output power of the circuit does not have reverse recovery basically because the fifth diode is a silicon carbide diode, so that the turn-on loss of the first switching tube can be greatly reduced, and the turn-on speed of the first switching tube can be increased under the same working condition. And enabling the current to flow to the output end of the bridge arm through the first switching tube and the second switching tube, and enabling the output end of the bridge arm to output a first preset level. The first preset level may be a P level, or may be referred to as a high level.
Mode two: on the basis of the mode one, the first switch tube, the second switch tube and the sixth switch tube are controlled to be switched on.
Specifically, as shown in fig. 5, at this time, the bridge arm outputs the first preset level, the current path is not changed, only the sixth switching tube is turned on, and the circuit still outputs power in the forward direction, so as to prepare for the follow current of the dual-follow current circuit. And enabling the current to flow to the output end of the bridge arm through the first switching tube and the second switching tube, wherein the output end of the bridge arm outputs a first preset level.
Mode three: on the basis of the mode two, the first switching tube is controlled to be turned off, and the fifth diode, the second switching tube, the sixth switching tube and the third diode are controlled to be turned on.
Specifically, as shown in fig. 6, the existence of the second freewheel circuit reduces the freewheel current of the SiC diode in the first freewheel circuit, so that the capacity of the fifth diode 5 can be reduced, the cost can be saved, and the existence of the dual freewheel circuit can disperse the thermal stress between the switching tubes. And enabling the current to flow to the output end of the bridge arm from a first follow current loop formed by the first voltage-dividing capacitor, the fifth diode and the second switch tube, and enabling the current to flow to the output end of the bridge arm from a second follow current loop formed by the second voltage-dividing capacitor, the sixth switch tube and the third diode, so that the follow current of the double follow current loop is realized, and the output end of the bridge arm outputs a second preset level.
And, modality four: and on the basis of the mode III, the sixth switching tube is controlled to be switched off, and the fifth diode and the second switching tube are controlled to be switched on.
Specifically, as shown in fig. 7, at this time, the single freewheeling circuit 0+ freewheels, and when the second preset level freewheeling is about to end, the sixth switching tube is turned off to prepare for turning on the first switching tube, so that the sixth switching tube is ensured to be turned off before the first switching tube is turned on, and the problem that the first switching tube is additionally subjected to turn-on loss due to the existence of the third diode (the third diode is a silicon diode) when the first switching tube is turned on can be avoided. And enabling current to flow to the output end of the bridge arm through a first follow current loop formed by the first voltage-dividing capacitor, the fifth diode and the second switch tube, and enabling the output end of the bridge arm to output a second preset level.
More specifically, as shown in fig. 14, the control unit 402 includes:
the first switching module 4021 is configured to switch the output level of the output end of the bridge arm from a first preset level to a second preset level sequentially based on the mode one, the mode two, and the mode three according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal, and the sixth driving signal.
And/or the second switching module 4022 is configured to sequentially switch the output level of the output end of the bridge arm from the second preset level to the first preset level through the mode three, the mode four, and the mode one according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal, and the sixth driving signal.
As can be seen from the first switching module 4021 and the second switching module 4022, the power switching path fully utilizes the advantage of the midpoint active clamp three-level dual freewheeling circuit to distribute thermal stress between the switching tubes, and avoids the influence of additional turn-on loss on the first switching tube caused by the third diode being a Si diode. Therefore, the level output by the output end of the bridge arm is switched, and the current is converted.
In an embodiment of the present invention, the reverse power switching mode includes:
a fifth mode: and controlling the third switching tube and the fifth switching tube to be switched off, and controlling the first diode and the second diode to be switched on.
Specifically, as shown in fig. 9, at this time, a current is caused to flow from the arm output terminal to the second diode and the first diode, and the arm output terminal outputs a P level.
A sixth mode: and on the basis of the mode five, controlling the fifth switching tube and the second diode to be switched on.
Specifically, as shown in fig. 10, the output is now passed through the single-wheeling circuit 0 +. The fifth switching tube is superior to the third switching tube in opening, and the fifth switching tube is switched by a small loop, so that the influence of larger parasitic parameters of a large loop on the loop switching can be reduced, and the voltage stress of the switching tube is reduced. And enabling the current to flow to the second diode, the fifth switching tube and the first voltage division capacitor from the output end of the bridge arm to form a first follow current loop, and enabling the output end of the bridge arm to output the P level.
And, modality seven: and on the basis of the mode six, controlling the fifth switching tube, the second diode, the sixth diode and the third switching tube to be switched on.
Specifically, as shown in FIG. 11, a dual-freewheel loop 0+, 0-output is formed at this time. Due to the double-loop chopping, the thermal stress between the switching tubes can be dispersed. Enabling current to flow from the output end of the bridge arm to the second diode, the fifth switching tube and the first voltage division capacitor to form a first follow current loop, and enabling the output end of the bridge arm to output a first preset level; and enabling the current to flow to a second follow current loop formed by the third switching tube, the sixth diode and the second voltage division capacitor from the output end of the bridge arm, wherein the output end of the bridge arm inputs a second preset level.
More specifically, as shown in fig. 15, the control unit 402 includes:
a third switching module 4023, configured to switch the output level of the output end of the bridge arm from the first preset level to a second preset level sequentially based on a mode five, a mode six, and a mode seven according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal, and the sixth driving signal;
and/or the fourth switching module 4024 is configured to switch the output level of the output end of the bridge arm from the second preset level to the first preset level sequentially according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal, and the sixth driving signal.
As can be seen from the third switching module 4023 and the fourth switching module 4024, the power switching path employs dual-loop chopping to reduce the voltage stress of the switching tubes and to disperse the thermal stress between the switching tubes.
It should be noted that the negative half-cycle commutation path is similar to the forward power switching and reverse power switching methods, and will not be described here.
In this embodiment of the present invention, the obtaining unit 401 obtains a first driving signal, a second driving signal, a third driving signal, a fourth driving signal, a fifth driving signal, and a sixth driving signal corresponding to the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube, and the sixth switching tube. And controlling the on-off states of the first switch tube, the second switch tube, the third switch tube, the fourth switch tube, the fifth switch tube and the sixth switch tube through the control unit 402 according to the first drive signal, the second drive signal, the third drive signal, the fourth drive signal, the fifth drive signal and the sixth drive signal based on a preset power switching mode to form a dual-follow current loop so as to realize a commutation path and electric energy conversion. Therefore, the on-off conditions of each switch tube and each diode can be controlled through the driving signal of each switch tube and the preset power switching state, follow current is switched through the single follow current loop and the double follow current loop, the thermal stress between the switch tubes is reduced, the reverse recovery loss of the diodes is reduced, the electric energy conversion efficiency of the circuit is improved, and the stability of the reliable operation of the inverter is improved.
The above description is only for the purpose of illustrating the preferred embodiments of the present invention and is not to be construed as limiting the invention, and any modifications, equivalents and improvements made within the spirit and principle of the present invention are intended to be included within the scope of the present invention.
Claims (17)
1. A midpoint active clamped three level inverter comprising: the bridge arm comprises a bridge arm unit, a clamping unit connected with the bridge arm unit and a bridge arm output end connected with the bridge arm unit;
the bridge arm unit comprises a first switch tube, a second switch tube, a third switch tube and a fourth switch tube which are sequentially connected in series, and a first diode, a second diode, a third diode and a fourth diode which are in inverse parallel connection with the first switch tube, the second switch tube, the third switch tube and the fourth switch tube in a one-to-one correspondence manner;
the clamping unit comprises a fifth switching tube, a sixth switching tube, a fifth diode and a sixth diode, wherein the fifth switching tube and the sixth switching tube are sequentially connected in series, the fifth diode and the sixth diode are connected in anti-parallel with the fifth switching tube and the sixth switching tube in a one-to-one correspondence mode, one end, far away from the sixth switching tube, of the fifth switching tube is arranged on a connecting line between the first switching tube and the second switching tube, and one end, far away from the fifth switching tube, of the sixth switching tube is arranged on a connecting line between the third switching tube and the fourth switching tube;
the bridge arm output end is arranged on a connecting line between the second switching tube and the third switching tube;
the fifth switch tube or the fifth diode and the second switch tube or the second diode form a first freewheeling circuit, the sixth switch tube or the sixth diode and the third switch tube or the third diode form a second freewheeling circuit, and the first freewheeling circuit and the second freewheeling circuit form a dual freewheeling circuit for changing a freewheeling path;
the fifth diode and the sixth diode are silicon carbide diodes.
2. The midpoint active clamp three-level inverter of claim 1, further comprising: the voltage division unit is respectively connected with the bridge arm unit and the clamping unit and comprises a first voltage division capacitor and a second voltage division capacitor which are sequentially connected in series, one end, far away from the second voltage division capacitor, of the first voltage division capacitor is connected with one end, far away from the second switch tube, of the first switch tube, and one end, far away from the first voltage division capacitor, of the second voltage division capacitor is connected with one end, far away from the third switch tube, of the fourth switch tube.
3. The midpoint active clamp three-level inverter according to claim 2, wherein an input terminal of the first switch tube is connected to a terminal of the first voltage-dividing capacitor far from the second voltage-dividing capacitor, an output terminal of the first switch tube is connected to an input terminal of the second switch tube and an input terminal of a fifth switch tube, an output terminal of the second switch tube is connected to an input terminal of the third switch tube and an output terminal of the bridge arm, an output terminal of the third switch tube is connected to an input terminal of the fourth switch tube and an output terminal of the sixth switch tube, and an output terminal of the fourth switch tube is connected to a terminal of the second voltage-dividing capacitor far from the first voltage-dividing capacitor.
4. The midpoint active clamp three level inverter of claims 1-3, wherein the first diode, the second diode, the third diode, and the fourth diode comprise a first silicon diode, a second silicon diode, a third silicon diode, and a fourth silicon diode in a one-to-one correspondence.
5. The midpoint active clamp three-level inverter of claims 1-3, wherein the first, second, third, fourth, fifth, and sixth switching transistors comprise a first MOS transistor, a second MOS transistor, a third MOS transistor, a fourth MOS transistor, a fifth MOS transistor, and a sixth MOS transistor, or a first transistor, a second transistor, a third transistor, a fourth transistor, a fifth transistor, and a sixth transistor, in a one-to-one correspondence.
6. A method of controlling a midpoint active clamped three-level inverter, for use in the midpoint active clamped three-level inverter of any one of claims 1-5, the method comprising:
acquiring a first driving signal, a second driving signal, a third driving signal, a fourth driving signal, a fifth driving signal and a sixth driving signal corresponding to the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube and the sixth switching tube;
and controlling the on-off states of the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube and the sixth switching tube based on a preset power switching mode according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal and the sixth driving signal to form a double-follow current loop so as to realize a current conversion path and electric energy conversion.
7. The method of controlling a midpoint active clamp three-level inverter of claim 6, wherein the predetermined power switching modes include a forward power switching mode and a reverse power switching mode.
8. The method of controlling a midpoint active clamped three level inverter of claim 7,
the forward power switching modalities include:
the first mode is as follows: controlling the first switch tube and the second switch tube to be switched on;
mode two: on the basis of the mode one, controlling the first switching tube, the second switching tube and the sixth switching tube to be switched on;
mode three: on the basis of the mode two, the first switching tube is controlled to be turned off, and the fifth diode, the second switching tube, the sixth switching tube and the third diode are controlled to be turned on;
and, modality four: and on the basis of the mode III, the sixth switching tube is controlled to be switched off, and the fifth diode and the second switching tube are controlled to be switched on.
9. The method as claimed in claim 8, wherein the step of controlling the on/off states of the first switch tube, the second switch tube, the third switch tube, the fourth switch tube, the fifth switch tube and the sixth switch tube based on a preset power switching mode according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal to form a dual-freewheel loop to realize a commutation path and an electric energy conversion comprises:
switching the output level of the output end of the bridge arm from a first preset level to a second preset level on the basis of a mode one, a mode two and a mode three in sequence according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal;
and/or switching the output level of the output end of the bridge arm from a second preset level to a first preset level sequentially through the mode three, the mode four and the mode one according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal.
10. The method of controlling a midpoint active clamped three level inverter of claim 8, wherein said reverse power switching modes comprise:
a fifth mode: controlling the third switching tube and the fifth switching tube to be turned off, and controlling the first diode and the second diode to be turned on;
a sixth mode: on the basis of the mode five, controlling the fifth switching tube and the second diode to be switched on;
and, modality seven: and on the basis of the mode six, controlling the fifth switching tube, the second diode, the sixth diode and the third switching tube to be switched on.
11. The method as claimed in claim 10, wherein the step of controlling the on/off states of the first switch tube, the second switch tube, the third switch tube, the fourth switch tube, the fifth switch tube and the sixth switch tube based on a preset power switching mode according to the first drive signal, the second drive signal, the third drive signal, the fourth drive signal, the fifth drive signal and the sixth drive signal to form a dual-freewheel loop to realize a commutation path and an electric energy conversion comprises:
switching the output level of the output end of the bridge arm from a first preset level to a second preset level on the basis of a mode five, a mode six and a mode seven in sequence according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal;
and/or switching the output level of the output end of the bridge arm from a second preset level to a first preset level sequentially through the mode seven, the mode six and the mode five according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal.
12. A control apparatus of a midpoint active clamp three-level inverter, for use in the midpoint active clamp three-level inverter of any one of claims 1-5, the apparatus comprising:
the acquisition unit is used for acquiring a first driving signal, a second driving signal, a third driving signal, a fourth driving signal, a fifth driving signal and a sixth driving signal corresponding to the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube and the sixth switching tube;
and the control unit is used for controlling the on-off states of the first switching tube, the second switching tube, the third switching tube, the fourth switching tube, the fifth switching tube and the sixth switching tube based on a preset power switching mode according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal and the sixth driving signal to form a double-follow current loop so as to realize a commutation path and electric energy conversion.
13. The apparatus of claim 12 wherein the predetermined power switching modes include a forward power switching mode and a reverse power switching mode.
14. The control apparatus for a midpoint active clamped three level inverter of claim 13,
the forward power switching modalities include:
the first mode is as follows: controlling the first switch tube and the second switch tube to be switched on;
mode two: on the basis of the mode one, controlling the first switching tube, the second switching tube and the sixth switching tube to be switched on;
mode three: on the basis of the mode two, the first switching tube is controlled to be turned off, and the fifth diode, the second switching tube, the sixth switching tube and the third diode are controlled to be turned on;
and, modality four: and on the basis of the mode III, the sixth switching tube is controlled to be switched off, and the fifth diode and the second switching tube are controlled to be switched on.
15. The apparatus for controlling a midpoint active clamped three level inverter of claim 14, wherein said control unit comprises:
the first switching module is used for switching the output level of the output end of the bridge arm from a first preset level to a second preset level on the basis of a mode one, a mode two and a mode three in sequence according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal;
and/or the second switching module is used for sequentially switching the output level of the output end of the bridge arm from the second preset level to the first preset level through the mode three, the mode four and the mode one according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal.
16. The apparatus for controlling a midpoint active clamped three level inverter of claim 14, wherein said reverse power switching modes comprise:
a fifth mode: controlling the third switching tube and the fifth switching tube to be turned off, and controlling the first diode and the second diode to be turned on;
a sixth mode: on the basis of the mode five, controlling the fifth switching tube and the second diode to be switched on;
and, modality seven: and on the basis of the mode six, controlling the fifth switching tube, the second diode, the sixth diode and the third switching tube to be switched on.
17. The apparatus for controlling a midpoint active clamped three level inverter of claim 16, wherein said control unit comprises:
the third switching module is used for switching the output level of the output end of the bridge arm from the first preset level to the second preset level on the basis of the mode five, the mode six and the mode seven in sequence according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal;
and/or the fourth switching module is configured to switch the output level of the bridge arm output end from the second preset level to the first preset level sequentially through the mode seven, the mode six and the mode five according to the first driving signal, the second driving signal, the third driving signal, the fourth driving signal, the fifth driving signal and the sixth driving signal.
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| CN202010594975.7A CN111711375A (en) | 2020-06-28 | 2020-06-28 | Neutral point active clamping three-level inverter, control method and control device |
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Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN113098310A (en) * | 2021-05-24 | 2021-07-09 | 青岛大学 | Active clamping three-level inverter circuit and control method thereof |
| CN113224962A (en) * | 2021-05-24 | 2021-08-06 | 青岛大学 | Active clamping three-level inverter circuit and method |
| CN113872460A (en) * | 2021-11-05 | 2021-12-31 | 阳光电源股份有限公司 | Switching modulation method for inverter and ANPC type three-level inverter circuit |
| CN114665735A (en) * | 2022-05-26 | 2022-06-24 | 浙江日风电气股份有限公司 | ANPC three-level inverter topology circuit, control method and control device |
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2020
- 2020-06-28 CN CN202010594975.7A patent/CN111711375A/en active Pending
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN113098310A (en) * | 2021-05-24 | 2021-07-09 | 青岛大学 | Active clamping three-level inverter circuit and control method thereof |
| CN113224962A (en) * | 2021-05-24 | 2021-08-06 | 青岛大学 | Active clamping three-level inverter circuit and method |
| CN113098310B (en) * | 2021-05-24 | 2022-06-07 | 青岛大学 | Active clamping three-level inverter circuit and control method thereof |
| CN113872460A (en) * | 2021-11-05 | 2021-12-31 | 阳光电源股份有限公司 | Switching modulation method for inverter and ANPC type three-level inverter circuit |
| CN114665735A (en) * | 2022-05-26 | 2022-06-24 | 浙江日风电气股份有限公司 | ANPC three-level inverter topology circuit, control method and control device |
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