CN111525713A - Torque pulsation weakening method of concentrated winding outer rotor magnetic field modulation motor - Google Patents
Torque pulsation weakening method of concentrated winding outer rotor magnetic field modulation motor Download PDFInfo
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- CN111525713A CN111525713A CN202010321621.5A CN202010321621A CN111525713A CN 111525713 A CN111525713 A CN 111525713A CN 202010321621 A CN202010321621 A CN 202010321621A CN 111525713 A CN111525713 A CN 111525713A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02K—DYNAMO-ELECTRIC MACHINES
- H02K1/00—Details of the magnetic circuit
- H02K1/06—Details of the magnetic circuit characterised by the shape, form or construction
- H02K1/12—Stationary parts of the magnetic circuit
- H02K1/14—Stator cores with salient poles
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02K—DYNAMO-ELECTRIC MACHINES
- H02K1/00—Details of the magnetic circuit
- H02K1/06—Details of the magnetic circuit characterised by the shape, form or construction
- H02K1/12—Stationary parts of the magnetic circuit
- H02K1/16—Stator cores with slots for windings
- H02K1/165—Shape, form or location of the slots
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02K—DYNAMO-ELECTRIC MACHINES
- H02K1/00—Details of the magnetic circuit
- H02K1/06—Details of the magnetic circuit characterised by the shape, form or construction
- H02K1/22—Rotating parts of the magnetic circuit
- H02K1/27—Rotor cores with permanent magnets
- H02K1/2786—Outer rotors
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02K—DYNAMO-ELECTRIC MACHINES
- H02K3/00—Details of windings
- H02K3/04—Windings characterised by the conductor shape, form or construction, e.g. with bar conductors
- H02K3/28—Layout of windings or of connections between windings
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/05—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation specially adapted for damping motor oscillations, e.g. for reducing hunting
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/14—Electronic commutators
- H02P6/16—Circuit arrangements for detecting position
- H02P6/18—Circuit arrangements for detecting position without separate position detecting elements
- H02P6/182—Circuit arrangements for detecting position without separate position detecting elements using back-emf in windings
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Permanent Magnet Type Synchronous Machine (AREA)
- Iron Core Of Rotating Electric Machines (AREA)
Abstract
The invention discloses a torque pulsation weakening method of a concentrated winding outer rotor magnetic field modulation motor, which aims at main odd harmonic and even harmonic in a back electromotive force of the motor respectively and adopts a method of establishing a target function to adjust modulation pole coefficient combination and rotor axial segmentation to suppress. In the method, the torque ripple of the motor is reduced as an objective function, and the optimal modulation pole coefficient combination is obtained by a method of combining analytical calculation and a finite element method so as to inhibit the influence of main odd harmonics; the rotor of the concentrated winding magnetic field modulation motor is divided into two sections in the axial direction, the permanent magnets of the two sections are magnetized in N polarity and S polarity respectively, and the upper permanent magnet and the lower permanent magnet are placed in a staggered mode by one pole distance so as to inhibit the influence of even harmonic waves. The torque ripple suppression method is simple to operate and obvious in effect, and the concentrated winding outer rotor magnetic field modulation motor has the characteristics of high torque density and low torque ripple.
Description
Technical Field
The invention relates to a torque ripple weakening method of a concentrated winding outer rotor magnetic field modulation motor, and belongs to the technical field of design and analysis of a motor body.
Background
The wheel hub motor technology is also called as the wheel built-in motor technology, and the most important characteristic of the wheel hub motor technology is that power, transmission and braking devices are integrated into a wheel hub, so that the mechanical part of an electric vehicle is greatly simplified. In order to reduce the size of the motor, solve the problems of friction and noise caused by a speed reducer and increase the power density, a magnetic gear structure and a magnetic field modulation type permanent magnet hub motor are sequentially proposed. Unlike mechanical gears, magnetic gears transfer energy through a magnetic field without direct contact between the two components, thus circumventing the problems of mechanical contact. However, early magnetic gear efficiency and torque density were not high, and thus sufficient attention was not paid. In 2001, a new type of coaxial magnetic gear based on magnetic field modulation was proposed by professor k. The topological structure consists of two rotating permanent magnet rotors and a magnetic field modulation module, wherein the magnetic field modulation module is formed by alternating magnetic conductive materials and non-magnetic conductive materials, and the modulation of magnetic fields generated by the two rotors is realized by changing a magnetic conductance function of an air gap, so that the control target of low speed and large torque is realized. The magnetic gear motor combines a permanent magnet motor and a magnetic gear, wherein the partial structure of the magnetic gear motor can adopt the working modes of fixing a magnetic adjusting module and rotating a high-pole-pair permanent magnet array and also can adopt various modes of fixing the high-pole-pair permanent magnet array and rotating the magnetic adjusting module. The existing research experience shows that the magnetic gear motor has several problems: (1) the cost is high. The consumption of the permanent magnet is large, so that the cost of the motor is higher; (2) the structure is complex. Because of the existence of the magnetic adjusting module, two to three air gaps are generally formed, so that the processing difficulty is high; (3) and (4) heat dissipation. Compared with the traditional permanent magnet motor, the structure is more complex, iron loss is increased by abundant harmonic waves, and the high heat generation and the difficult heat dissipation are easily caused.
Aiming at the problems of complex structure and high processing difficulty of a magnetic gear motor, scholars at home and abroad propose a plurality of magnetic field modulation motor topologies according to a magnetic gear effect and a field modulation theory. The field modulation motor replaces a rotating magnetic field generated by a permanent magnet rotor with small pole pair number in a coaxial magnetic gear with a rotating magnetic field generated by a three-phase armature winding, and the rotating magnetic field generated by the armature winding after alternating current is introduced into the armature winding generates a low-speed rotating harmonic magnetic field which is the same as the pole pair number of the permanent magnet rotor with high pole pair number through the modulation effect of a magnetic adjusting module so as to drive the rotor to rotate. The single-air-gap magnetic field modulation motor adopts the stator teeth to replace a magnetic modulation module, is similar to a common permanent magnet motor, has simple structure, high torque density and high reliability, and can be applied to the occasions of low-speed direct drive and large torque.
In the selection of the motor winding, although the traditional distributed winding can make the sine degree of the counter potential better, the traditional distributed winding can cause the end winding to be long and the mutual inductance between phases to be larger, and the problem can be solved by adopting the concentrated winding. According to the classical winding theory, however, the concentrated windings have no weakening effect on higher harmonics, thereby causing the torque ripple of the motor to increase. In addition, for the motor with the stator adopting the split tooth structure, the speed ratio can be improved under the condition of the same number of slots, and the heat radiation performance of the motor can be improved under the condition of the same speed ratio. Meanwhile, compared with a surface-mounted permanent magnet structure, the alternating pole structure is applied in order to save the using amount of the permanent magnet and reduce the production cost. However, due to the asymmetric flux density of the air gap below the magnetic pole, the counter electromotive force of the motor is asymmetric due to the introduced even harmonic, and large torque pulsation is caused. Therefore, a solution is needed to be provided for the torque ripple problem of the concentrated winding outer rotor magnetic field modulation motor adopting the alternating pole structure.
Disclosure of Invention
The technical problem to be solved by the invention is as follows: the torque ripple weakening method of the concentrated winding outer rotor magnetic field modulation motor can effectively weaken torque ripple while improving the mean value of torque, thereby improving the torque performance of the motor.
The invention adopts the following technical scheme for solving the technical problems:
a torque pulsation weakening method of a concentrated winding outer rotor magnetic field modulation motor comprises an odd harmonic weakening method and an even harmonic weakening method;
the specific process of the odd harmonic weakening method is as follows:
step a, establishing a magnetomotive force-magnetic conductance model of the concentrated winding outer rotor magnetic field modulation motor by utilizing Fourier series;
b, analyzing and calculating the magnetomotive force-magnetic conductance model, and combining a winding function to obtain a counter potential expression;
c, calculating to obtain torque according to the back electromotive force expression, obtaining a function expression of a torque mean value and a torque ripple component from the torque, performing parameter optimization by taking torque ripple inhibition as an optimization objective function, and establishing the optimization objective function;
d, changing the values of the modulated pole tooth width coefficient and the pitch coefficient in the optimized objective function by adopting an analytical method, calculating the value of the optimized objective function so as to obtain a reasonable value interval of the modulated pole tooth width coefficient and the pitch coefficient, and obtaining the optimal modulated pole tooth width coefficient and the optimal pitch coefficient by adopting a finite element method for the reasonable value interval;
the specific process of the even harmonic attenuation method is as follows:
the mode of axially segmenting the outer rotor is adopted, so that the counter electromotive force even harmonic induced by the outer rotor in the armature winding has a phase difference of 180 degrees, specifically: the outer rotor is averagely divided into two sections, namely a first section of outer rotor and a second section of outer rotor, first permanent magnets and first iron core poles are alternately arranged on the inner wall of the first section of outer rotor along the circumferential direction, second permanent magnets and second iron core poles are alternately arranged on the inner wall of the second section of outer rotor along the circumferential direction, the first permanent magnets and the second permanent magnets are staggered by one pole angle, the magnetizing polarity of the first permanent magnets is N pole, and the magnetizing polarity of the second permanent magnets is S pole.
As a preferable scheme of the present invention, the magnetomotive force-flux guide model in step a is:
wherein, Fm(θ, t) is a permanent magnet magnetomotive force function with respect to rotor position angle θ and time t, PrIs the number of pole pairs of the rotor, omega is the rotational speed of the rotor, FcIs a coefficient of αmFor permanent magnet pole arcs, P (theta) is the air gap permeance function about the rotor position angle theta, Z is the number of stator slots, P0、p2The coefficients are α, the tooth width coefficient of the modulation pole is α, and k is the pitch coefficient.
As a preferable scheme of the present invention, the counter potential expression in step b is:
wherein e isA(t) is the back-emf over time t, ω is the rotor speed, FmiIs a coefficient in the permanent magnet magnetomotive force function, LaIs the axial length of the motor, rgIs the air gap radius, NjAs a factor of a winding function, PrIs the number of rotor pole pairs, PsIs the number of pole pairs of armature winding, P0、P1、P2Are coefficients in the function of the permeance of the air gap, and Z is the number of the stator slots.
As a preferred embodiment of the present invention, the optimization objective function in step c is:
wherein TRI represents an optimization objective function, TeruRepresenting the torque ripple component function, TecuRepresenting the mean function of torque, Fmi、Fm1Are all coefficients in the permanent magnet magnetomotive force function, P0、P1、P2All coefficients are in the function of the permeance of the air gap, N is the coefficient of the winding function, Z is the number of stator slots, PrIs the number of rotor pole pairs, PsThe number of pole pairs of the armature winding.
Compared with the prior art, the invention adopting the technical scheme has the following technical effects:
1. the invention adopts a split tooth structure, and one main tooth is provided with two modulation poles, so that the reduction ratio is improved under the condition of limited space and the heat dissipation is facilitated; by analyzing the relationship between the tooth width coefficient and the tooth pitch coefficient of the modulation pole and the motor performance, the optimal coefficient combination can be obtained to eliminate the counter potential higher harmonic, so that the counter potential sine degree is increased.
2. The invention adopts the rotor alternate pole structure, saves the using amount of the permanent magnet and reduces the manufacturing cost of the motor; the armature winding adopts a concentrated winding form, so that the length of the end part and the interphase mutual inductance are reduced, and the reliability and the fault-tolerant capability of the motor are improved.
3. The invention adopts a rotor axial segmented structure, the upper and lower sections of rotor permanent magnets are respectively magnetized with N, S polarity and staggered by an angle of one pole, so that even harmonics in the synthetic counter electromotive force can be cancelled, and the sine degree of the counter electromotive force is improved, thereby reducing torque pulsation and improving the torque performance of the motor.
Drawings
Fig. 1 is a 6 slot 20 pole concentrated winding field modulated motor topology with stator teeth adjusted by the method of the present invention.
Fig. 2 is an exploded view of a field modulated motor employing the method of the present invention.
Fig. 3 is an alternate pole concentrated winding field modulated motor topology for axial segmentation of a rotor according to the present invention.
Fig. 4 is a magnetomotive force-flux guide model established according to a motor structure used in the present invention, in which (a) is a permanent magnet magnetomotive force model and (b) is an air gap flux guide model.
Fig. 5 is a comparison of stator modulated teeth and equal modulated pitch stator tooth structures obtained using the method of the present invention, wherein (a) is a common equal pitch modulated pole structure and (b) is a modulated pole structure optimized using the method of the present invention.
FIG. 6 is a comparison of the motor back electromotive force and FFT analysis waveforms of the stator modulated pole parameter combination and the stator tooth structure with equal modulation tooth pitch obtained by the method of the present invention, wherein (a) is the back electromotive force waveform, and (b) is the FFT analysis result.
Fig. 7 is a comparison of back emf and FFT waveforms for a rotor axial segmented versus unsegmented alternating pole field modulated motor, where (a) is the back emf waveform and (b) is the FFT analysis result.
FIG. 8 is a torque performance comparison of an alternating pole field modulated motor with rotor axial segmentation and no segmentation.
Detailed Description
Reference will now be made in detail to embodiments of the present invention, examples of which are illustrated in the accompanying drawings, wherein like reference numerals refer to the same or similar elements or elements having the same or similar function throughout. The embodiments described below with reference to the accompanying drawings are illustrative only for the purpose of explaining the present invention, and are not to be construed as limiting the present invention.
The invention provides a torque ripple suppression method of a concentrated winding outer rotor magnetic field modulation motor based on axial rotor segmentation.
As shown in fig. 1, a 6 slot 20 pole concentrated winding field modulated motor topology with stator teeth adjusted by the method of the present invention is shown. The rotor is divided into two sections, wherein one section of the permanent magnet is magnetized by N polarity, the other section of the permanent magnet is magnetized by S polarity, and the two sections of the rotor are assembled by staggering the angle of one pole. The concentrated winding outer rotor magnetic field modulation motor comprises an inner stator main tooth body 1, inner stator main tooth split teeth 2, an outer rotor 3, an outer rotor alternating pole permanent magnet 4, an outer rotor alternating pole iron core pole 5 and a concentrated winding 6. Fig. 2 is an exploded view of a field modulated motor employing the present invention. Fig. 3 shows an alternate pole concentrated winding field modulated motor topology using axial segmentation of the rotor according to the present invention.
The influence of different modulation pole coefficient combinations on air gap flux density distribution and the influence of torque performance are calculated by establishing a mathematical model so as to narrow the finite element parameter selection range and weaken the influence of main odd harmonics on torque pulsation.
For convenience of calculation, the modulation tooth width coefficient α and the pitch coefficient k are respectively defined as:
wherein, thetatIs the angle of one modulation tooth, thetapIs the angle between adjacent modulation teeth, PfIs the modulation pole number.
The calculation process mainly comprises the following aspects:
1. using fourier series, a magnetomotive force-flux guide model was built for the machine, as shown in fig. 4. Fig. 4 (a) shows a permanent magnet magnetomotive force model, and fig. 4 (b) shows an air gap flux guide model. The permanent magnet magnetomotive force function and the air gap permeance function are obtained as follows:
wherein theta is the rotor position angle, omega is the rotor speed, Z is the number of stator slots, αmIs a permanent magnet polar arc, PrIs the number of pole pairs of the rotor.
2. The magnetomotive force and the air gap flux density are analyzed and calculated, and a back electromotive force expression is obtained by combining a winding function as follows:
wherein L isaIs the axial length of the motor, rgIs the air gap radius, NjAs a factor of a winding function, PsThe number of pole pairs of the armature winding.
3. Calculating average torque and torque ripple under different modulation polar coefficient combinations, mainly considering fifth and seventh harmonics which have large influence on the torque ripple, obtaining the torque according to a back electromotive force expression, and obtaining a function expression of the torque average value and the torque ripple component by the torque as follows:
wherein, ImIs the armature current amplitude.
And performing parameter optimization by taking the suppression torque ripple as an optimization objective function, thereby establishing the optimization objective function as follows:
4. and changing the values of the modulation pole tooth width coefficient alpha and the tooth pitch coefficient k, and calculating the value of the objective function. The above-mentioned analytic method is combined with the finite element method to obtain the optimum combination of the tooth width coefficient α and the tooth pitch coefficient k to improve the sine degree of the back emf and thus weaken the influence of the odd harmonics on the torque ripple, taking into account the influence of saturation and magnetic leakage, as shown in fig. 5. Fig. 5 (a) shows a general modulated pole structure with an equal pitch, and fig. 5 (b) shows a modulated pole structure optimized by the method of the present invention.
In order to eliminate counter potential even harmonic components caused by the alternating poles, a rotor axial segmentation mode is adopted, so that counter potential even harmonic phases induced in an armature winding by the rotor are 180 degrees different from each other, even harmonic components in counter potential caused by the alternating poles are cancelled, suppression of torque pulsation caused by the even harmonic is achieved, and the purpose of improving the motor torque performance is achieved.
The rotor is divided into an upper section and a lower section, the permanent magnet of the upper half section is magnetized by N polarity, and the permanent magnet of the lower half section is magnetized according to S polarity after rotating by an angle of one pole. According to the winding complementation principle, even harmonics in the counter potential are opposite in phase, so that the influence of even harmonic components of the counter potential on the torque can be eliminated.
Fig. 6 (a), (b) show the comparison of the motor back electromotive force and FFT analysis waveform of the stator modulated pole parameter combination and the stator tooth structure with equal modulated tooth pitch obtained by the method of the present invention. Fig. 7 (a), (b) show the back emf and FFT waveforms of a rotor axially segmented versus an unsegmented alternating pole field modulated motor. Fig. 8 shows torque performance of an alternating pole field modulated machine with rotor axial segmentation compared to unsegmented.
The above embodiments are only for illustrating the technical idea of the present invention, and the protection scope of the present invention is not limited thereby, and any modifications made on the basis of the technical scheme according to the technical idea of the present invention fall within the protection scope of the present invention.
Claims (4)
1. A torque pulsation weakening method of a concentrated winding outer rotor magnetic field modulation motor is characterized by comprising an odd harmonic weakening method and an even harmonic weakening method;
the specific process of the odd harmonic weakening method is as follows:
step a, establishing a magnetomotive force-magnetic conductance model of the concentrated winding outer rotor magnetic field modulation motor by utilizing Fourier series;
b, analyzing and calculating the magnetomotive force-magnetic conductance model, and combining a winding function to obtain a counter potential expression;
c, calculating to obtain torque according to the back electromotive force expression, obtaining a function expression of a torque mean value and a torque ripple component from the torque, performing parameter optimization by taking torque ripple inhibition as an optimization objective function, and establishing the optimization objective function;
d, changing the values of the modulated pole tooth width coefficient and the pitch coefficient in the optimized objective function by adopting an analytical method, calculating the value of the optimized objective function so as to obtain a reasonable value interval of the modulated pole tooth width coefficient and the pitch coefficient, and obtaining the optimal modulated pole tooth width coefficient and the optimal pitch coefficient by adopting a finite element method for the reasonable value interval;
the specific process of the even harmonic attenuation method is as follows:
the mode of axially segmenting the outer rotor is adopted, so that the counter electromotive force even harmonic induced by the outer rotor in the armature winding has a phase difference of 180 degrees, specifically: the outer rotor is averagely divided into two sections, namely a first section of outer rotor and a second section of outer rotor, first permanent magnets and first iron core poles are alternately arranged on the inner wall of the first section of outer rotor along the circumferential direction, second permanent magnets and second iron core poles are alternately arranged on the inner wall of the second section of outer rotor along the circumferential direction, the first permanent magnets and the second permanent magnets are staggered by one pole angle, the magnetizing polarity of the first permanent magnets is N pole, and the magnetizing polarity of the second permanent magnets is S pole.
2. The torque ripple attenuation method of the concentrated winding outer rotor field modulated motor according to claim 1, wherein the magnetomotive force-flux guide model of step a is:
wherein, Fm(θ, t) is a permanent magnet magnetomotive force function with respect to rotor position angle θ and time t, PrIs the number of pole pairs of the rotor, omega is the rotational speed of the rotor, FcIs a coefficient of αmFor permanent magnet pole arcs, P (theta) is the air gap permeance function about the rotor position angle theta, Z is the number of stator slots, P0、p2The coefficients are α, the tooth width coefficient of the modulation pole is α, and k is the pitch coefficient.
3. The torque ripple reduction method of the concentrated winding outer rotor field modulated motor according to claim 1, wherein the back electromotive force expression of step b is:
wherein e isA(t) is the back-emf over time t, ω is the rotor speed, FmiIs a coefficient in the permanent magnet magnetomotive force function, LaIs the axial length of the motor, rgIs the air gap radius, NjAs a factor of a winding function, PrIs the number of rotor pole pairs, PsIs the number of pole pairs of armature winding, P0、P1、P2Are coefficients in the function of the permeance of the air gap, and Z is the number of the stator slots.
4. The torque ripple reduction method of the concentrated winding outer rotor field modulated motor of claim 1, wherein the optimization objective function of step c is:
wherein TRI represents an optimization objective function, TeruRepresenting the torque ripple component function, TecuRepresenting the mean function of torque, Fmi、Fm1Are all coefficients in the permanent magnet magnetomotive force function, P0、P1、P2All coefficients are in the function of the permeance of the air gap, N is the coefficient of the winding function, Z is the number of stator slots, PrIs the number of rotor pole pairs, PsThe number of pole pairs of the armature winding.
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Cited By (10)
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| CN112087076A (en) * | 2020-09-10 | 2020-12-15 | 东南大学 | Outer rotor sectional type vernier motor integrated with speed reducer |
| CN112421919A (en) * | 2020-11-09 | 2021-02-26 | 华中科技大学 | Permanent magnet motor topology construction method based on working magnetic field harmonic wave orientation and motor |
| CN112436706A (en) * | 2020-11-24 | 2021-03-02 | 江苏大学 | Loss analysis and suppression method for magnetic field modulation permanent magnet motor |
| CN113489274A (en) * | 2021-07-12 | 2021-10-08 | 南京航空航天大学 | Bilateral alternate pole type hybrid excitation brushless motor |
| CN113572281A (en) * | 2021-08-04 | 2021-10-29 | 东南大学 | Low-speed large-torque motor stator |
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| CN112087076A (en) * | 2020-09-10 | 2020-12-15 | 东南大学 | Outer rotor sectional type vernier motor integrated with speed reducer |
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| GB2599611B (en) * | 2020-11-24 | 2023-01-04 | Univ Jiangsu | Loss analysis and suppression method for field-modulated permanent magnet motor |
| GB2599611A (en) * | 2020-11-24 | 2022-04-06 | Univ Jiangsu | Loss analysis and suppression method for magnetic field-modulated permanent magnet motor |
| WO2022110274A1 (en) * | 2020-11-24 | 2022-06-02 | 江苏大学 | Loss analysis and suppression method for magnetic field-modulated permanent-magnet electric motor |
| CN112436706A (en) * | 2020-11-24 | 2021-03-02 | 江苏大学 | Loss analysis and suppression method for magnetic field modulation permanent magnet motor |
| CN113489274A (en) * | 2021-07-12 | 2021-10-08 | 南京航空航天大学 | Bilateral alternate pole type hybrid excitation brushless motor |
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| CN113595276B (en) * | 2021-07-28 | 2022-08-02 | 华中科技大学 | Permanent magnet motor tooth socket torque reduction method and device |
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| CN113890289A (en) * | 2021-09-10 | 2022-01-04 | 华中科技大学 | Design method of multi-magnetomotive permanent magnet array and flux reversal motor |
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| CN113839481A (en) * | 2021-10-25 | 2021-12-24 | 南通大学 | Novel rhombus modulation pole vernier permanent magnet motor |
| CN114048649A (en) * | 2021-11-09 | 2022-02-15 | 华能澜沧江水电股份有限公司 | Method for weakening low-frequency vibration of stator of hydraulic generator |
| CN114048649B (en) * | 2021-11-09 | 2024-04-12 | 华能澜沧江水电股份有限公司 | Method for weakening stator low-frequency vibration of hydraulic generator |
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