CN111371323A - BOOST power conversion circuit and control method thereof - Google Patents
BOOST power conversion circuit and control method thereof Download PDFInfo
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- CN111371323A CN111371323A CN202010260983.8A CN202010260983A CN111371323A CN 111371323 A CN111371323 A CN 111371323A CN 202010260983 A CN202010260983 A CN 202010260983A CN 111371323 A CN111371323 A CN 111371323A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
Abstract
The invention discloses a BOOST power conversion circuit and a control method thereof, the conversion circuit is additionally provided with an initial voltage establishment circuit of a flying capacitor C1 on the basis of an input-output common ground type three-level BOOST converter, the initial voltage establishment circuit consists of a first resistor R1, a second resistor R2 and a third resistor R3, and the voltage at the input end of the BOOST power conversion circuit is lower than the starting threshold voltage V of the BOOST power conversion circuitstartAn initial voltage is established for the first capacitor C1, and the functions are: firstly, the forward voltage of the second switch tube T2 is reduced; secondly, the reverse voltage borne by the fourth diode D4 is reduced, so that the second switch tube T2 is protected, and meanwhile, the fourth diode D4 with smaller reverse voltage stress can be selected.
Description
Technical Field
The invention relates to the technical field of power electronics, in particular to a BOOST power conversion circuit of a photovoltaic grid-connected inverter applied to multi-path MPPT and a control method thereof.
Background
The Boost circuit is a Boost power conversion circuit, and can Boost input voltage and then output the boosted input voltage, so that power conversion is realized. Generally, a Boost circuit includes a two-level Boost circuit and a multi-level Boost circuit, the two-level Boost circuit is generally applied to the occasions with lower voltage levels, and the multi-level Boost circuit is applied to the occasions with higher voltage levels. Compared with a two-level Boost circuit, the multi-level Boost circuit realizes multi-level by improving a self topological structure, and further realizes high-voltage and high-power output. The multi-level Boost circuit has the outstanding advantages that the voltage stress of the power device can be reduced, the voltage stress borne by the power device is half of that of the two-level Boost circuit, so that the power device with a smaller voltage withstanding grade can be used for realizing higher-grade voltage output, the circuit efficiency can be improved, and the system cost can be reduced.
Compared with a symmetrical three-level Boost circuit (shown in a figure 1-b), the input and output common-ground type three-level Boost circuit (shown in a figure 1-a) of the photovoltaic grid-connected inverter has the advantages of no influence of common-mode signals, half reduction of the number of energy storage inductors, high operation efficiency and the like, and is a more optimal choice for the photovoltaic grid-connected inverter. When the input-output common-ground type three-level Boost circuit is applied to a multi-path MPPT photovoltaic grid-connected inverter, the following two problems mainly exist:
first, when the input voltage is initially turned on and the flying capacitor has a high initial voltage equal to zero, the input voltage is fully applied to the second switch transistor T2, and in a severe case, the input voltage may cause an overvoltage breakdown on the switch transistor T2. For example: since the front stage of the photovoltaic grid-connected inverter is generally connected in parallel by multiple MPPTs (as shown in fig. 13), when the input voltage of one MPPT reaches the initial starting voltage V of the MPPTstartAt this time, assuming that the initial voltage of the flying capacitor is equal to zero, the voltage across the second switch transistor T2 is equal to VinIn the extreme case, Vin1500V, this results in a transient overvoltage breakdown of the second switching transistor.
Secondly, when the MPPT of a certain path is not started after the bus voltage is established, since the initial voltage of the flying capacitor voltage is equal to zero, the output bus voltage is completely applied to the fourth diode D4, and overvoltage breakdown of the diode is caused in a serious case. For example: when the MPPT is not connected with the photovoltaic cell panel or the photovoltaic cell panel has lower output voltage at the moment and the output direct-current bus voltage is established at the momentWhen the initial voltage of the flying capacitor is equal to zero, the fourth diode D4 will bear the reverse voltage stress Vout(see FIG. 1-a), in the extreme case, VoutAt 1500V, the fourth diode D4 will experience the entire bus voltage of 1500V. At this time, a diode with a high voltage withstanding value needs to be selected, and the diode with a high voltage withstanding value has a high tube voltage drop and poor reverse recovery characteristics, which seriously affects the circuit efficiency in use.
The above two potential problems may bring serious challenges to the device design of the circuit, and therefore appropriate measures must be taken to obtain a method for ensuring the safety of the second switching tube and reducing the voltage stress of the fourth diode, so as to ensure the circuit efficiency and reduce the system cost.
Disclosure of Invention
In order to solve the above technical problems in the prior art, in one aspect, the present invention provides a BOOST power conversion circuit, including a power source Vin, an inductor L1, a first switch module, a second switch module, a third diode D3, a fourth diode D4, and a flying capacitor C1; the power source Vin, the inductor L1, the first switch module and the second switch module form a first closed loop; the flying capacitor voltage setting circuit comprises a first switch S1 and a flying capacitor initial voltage setting circuit, wherein the flying capacitor initial voltage setting circuit comprises a first resistor, a second resistor and a third resistor; the first resistor is connected in parallel with the fourth diode, the second resistor is connected in parallel with the first capacitor, one end of the third resistor is connected to the negative end of the first capacitor, and the other end of the third resistor is connected to the negative end of the direct current bus; a second closed loop formed by the power source Vin, the inductor L1, the third diode D3, the second resistor R2, the first capacitor C1, the first switch S1 and the second switch tube module; the power source Vin, the inductor L1, the first switch module, the first switch S1, the second resistor R2, the first capacitor C1, the first resistor R1 and the fourth diode D4 are connected in parallel, and an output bus forms a third closed loop; the flying capacitor initial voltage establishing circuit is used for enabling the voltage stress of the second switch module to be smaller than the input voltage of the boost power conversion circuit and enabling the voltage stress borne by the fourth diode to be smaller than the bus voltage of the power conversion circuit, wherein the input voltage is the voltage difference between an input anode and an input cathode, and the bus voltage is the voltage difference between a positive bus voltage and a negative bus voltage.
The first switch module comprises a first switch tube T1 and a first diode D1, the second switch module comprises a second switch tube T2 and a second diode D2, the negative pole end of the diode is connected with the collector electrode of the switch tube, and the positive pole end of the diode is connected with the emitter electrode of the switch tube. The three-phase inverter further comprises a third bus capacitor C3 and a fourth bus capacitor C4, wherein the first switch module, the second switch module, the third diode D3, the fourth diode D4, the third bus capacitor C3 and the fourth bus capacitor C4 form a fourth closed loop. The direct current bus-bar power supply device further comprises a load unit, wherein one end of the load unit is connected with the positive pole of the direct current bus-bar, and the other end of the load unit is connected with the negative pole of the direct current bus-bar.
According to the flying capacitor initial voltage establishing circuit added in the invention, when any path of MPPT of the photovoltaic grid-connected inverter is electrified, the first switch S1 is kept to be switched off, and at the moment, the input voltage Vin, the inductor L1, the third diode D3, the second resistor R2, the first capacitor C1 and the third resistor R3 form a loop. If the first MPPT1 input voltage reaches the MPPT working threshold voltage VstartAt this time, the dc bus voltage is equal to the input voltage of the current first MPPT 1. Input voltage VinThe flying capacitor C1 and R3 are connected in parallel through the inductor L1, the third diode D3 and the second capacitor R2 to form a circuit branch, and then V isC1＝αVin＝βVout。
Once the flying capacitor C1 voltage is established, the switch S1 of the first MPPT1 may be closed, the circuit enters a normal operating state, and since the flying capacitor voltage is already established, the situation that the switch tube is subjected to overvoltage and breaks down due to the flying capacitor voltage being equal to zero when the switch S1 is closed may be avoided.
If the MPPT2 input voltage is lower than the MPPT working threshold voltage VstartThe normal operation of the BOOST converter cannot be met, the switch S1 is kept in an off state, and the MPPT1 and the MPPT2 share the DC bus VoutThe dc bus voltage is established by MPPT 1. According to the kirchhoff loop voltage law, the direct current bus voltage is connected in parallel through a first resistor R1, a second resistor R2, a flying capacitor C1 and a third resistor R3 to establish a circuit relation, and finally V can be known under the steady state conditionC1＝γVout. Accordingly, the initial voltage of the flying capacitor of the MPPT without starting operation is established once the input voltage of the MPPT2 meets the operation threshold voltage V of the BOOST converterstartThe switch S1 can be closed to operate normally, and due to the voltage dividing effect of the flying capacitor, the reverse voltage of the diode D4 is prevented from being high, so that the purpose of reducing the reverse withstand voltage of the diode D4 is achieved, the device selection is facilitated, the working efficiency of the circuit system is improved, and the cost is reduced.
On the other hand, when the voltage at the input end of the BOOST power conversion circuit is lower than the starting voltage of the BOOST power conversion circuit, the flying capacitor initial voltage establishing circuit enables the voltage stress borne by the second switching tube to be smaller than the input voltage, wherein the input voltage is the voltage difference between the input anode and the input cathode; the flying capacitor initial voltage establishing circuit enables the voltage stress born by the fourth diode to be smaller than the bus voltage of the boost power conversion circuit, and the bus voltage is the voltage difference between the positive bus voltage and the negative bus voltage.
Drawings
FIG. 1-a is a schematic diagram of a three-level BOOST circuit with input and output common ground;
FIG. 1-b is a topological structure diagram of a symmetric three-level BOOST circuit;
FIG. 2 is a waveform diagram of driving signals when D < 0.5;
FIG. 3 is a path diagram of switching mode a when D < 0.5;
FIG. 4 is a path diagram of switching mode b with D < 0.5;
FIG. 5 is a path diagram of switching mode c with D < 0.5;
FIG. 6 is a path diagram of the switching mode D when D < 0.5;
FIG. 7 is a waveform diagram of driving signals when D > 0.5;
FIG. 8 is a path diagram of switch mode a when D > 0.5;
FIG. 9 is a path diagram of switching mode b when D > 0.5;
FIG. 10 is a path diagram of switching mode c for D > 0.5;
FIG. 11 is a path diagram of switching mode D when D > 0.5;
FIG. 12-a is a schematic diagram of a BOOST BOOST power conversion circuit when a switch is closed according to an embodiment of the present application;
12-b is a schematic diagram of a BOOST power conversion circuit when a switch is turned off according to an embodiment of the present application;
fig. 13 is a schematic diagram of an application in which output terminals of a plurality of Boost circuits are connected in parallel to a photovoltaic power generation system;
Detailed Description
In order to make those skilled in the art better understand the technical solutions provided by the embodiments of the present application, the following describes the operation principle of the conventional three-level Boost circuit as an example.
As shown in FIG. 1-a, the resistor R1 is a load unit, and the resistors C3 and C4 are bus capacitors at the output side of the Boost circuit and are based on the input voltage VinAnd an output voltage VoutThe Boost circuit respectively works in two working modes of duty ratio D <0.5 and D > 0.5:
1. when V isin＞0.5VoutWhen the duty ratio D is less than 0.5;
in this operation mode, the waveform diagram of the drive signal is shown in fig. 2, and the current flow paths in each switching mode are shown in fig. 3 to 6, in which the current flow paths are shown, and C2 and C3 are bus capacitors. In the figure, T is the switching period, and T1 and T2 drive signals are different in phase angle of 180 degrees.
As in fig. 3, switching mode a: t1 is turned on, T2 is turned off, D4 is turned on, D3 is turned off, and the flying capacitor voltage is controlled as follows: vC1＝0.5VoutThe voltage borne across the inductor L1 is greater than zero, i.e. Vin-0.5VoutWhen the voltage stress is more than 0.5V, the inductive current rises linearly, and the voltage stress of D3 is 0.5VoutD4 is on with no reverse voltage stress.
As shown in fig. 4 and 6, the switching modes are b and d: the two switching modes are completely the same and appear twice in the same period. Both T1 and T2 are in the off state. The inductor current freewheels through D3 and D4, D3 and D4 are conducted, and no counter voltage stress exists.
As shown in fig. 5, switching mode c: t1 is turned off, T2 is turned on, D3 is turned on, D4 is turned off, and the voltage stress is:
Vout-VC1＝0.5Vout；
according to the principle of conservation of voltage at two ends of the inductor in volt-seconds, namely in a working period, the product of the voltage at two ends of the inductor and time is 0, and the following can be obtained: (V)in-Vout+VC1)·DT+(Vin-Vout)·(1-2D)T+(Vin-VC1) DT ═ 0; after simplification, the method can be obtained: vout＝Vin(1-D), it can be seen from this equation that the output voltage can be controlled by controlling the duty ratio D of T1 and T2.
2. When V isinLess than 0.5VoutWhen the duty ratio D is more than 0.5;
in this operation mode, the waveform diagram of the driving signal is shown in fig. 7, and the current flow paths in each switching mode are shown in fig. 8 to 11, in which the solid line represents the current path, and C2 and C3 are bus capacitors.
As shown in fig. 8 and 10, switching modes a and c: the two switching mode current flow paths are identical and occur at different stages of a cycle. T1 and T2 are turned on, and D3 and D4 are turned off. The voltage across the inductor L1 is VinThe inductor current rises linearly. The voltage stress of D3 and D4 are both 0.5Vout。
As shown in fig. 9, switching mode b: t1 is turned on, T2 is turned off, D4 is turned on, and D3 is turned off. D3 voltage stress of 0.5Vout。
As shown in fig. 11, switching mode d: t2 is ON, T1 is OFF, D3 is ON, and D4 is OFF. D4 voltage stress of 0.5Vout. According to the principle of conservation of voltage at two ends of the inductor in volt-seconds, the following can be obtained: vout＝Vin/(1-D)。
In summary, under various operating conditions in the steady state, the voltage stress of D3 and D4 is half of the output voltage, i.e. 0.5VoutThe diode devices can be selected according to the voltage stress when being selected.
As the power station in the photovoltaic power generation field generally comprises a plurality of inverters, the output ends of DC-DC in the plurality of inverters are connected in parallel, if a certain DC-DC output is connectedThe input end is not successfully connected with the photovoltaic module, so that other paths of DC-DC in parallel are successfully connected with the photovoltaic module, and because the output ends are connected in parallel, the bus voltage of the output end of the DC-DC in parallel is already established, so that the diode in the DC-DC of which the input end is not successfully connected with the photovoltaic module bears the back voltage of the bus voltage. For example, as shown in fig. 1-a, when multiple MPPTs are used in parallel, under the condition that the initial voltage of the flying capacitor is not established, the MPPT started at the first power-on will cause the transient overvoltage damage of the second switching tube T2 under the action of a higher input voltage; when the output ends of the multi-path Boost circuits are connected in parallel, namely a multi-path common output bus, if other paths are electrified, but the Boost circuits of the paths are not electrified, the bus voltage exists at the moment, because the flying capacitor voltage and the input voltage of the paths are both 0, the voltage between the cathode of D3 and the anode of D2 can be approximately equal in potential, and at the moment, the D4 bears the whole bus voltage VoutIf D4 is at 0.5VoutThe stress is selected, and D4 is broken down by the overvoltage.
In order that those skilled in the art will better understand the invention and thus more clearly define the scope of the invention as claimed, it is described in detail below with respect to certain specific embodiments thereof. It should be noted that the following is only a few embodiments of the present invention, and the specific direct description of the related structures is only for the convenience of understanding the present invention, and the specific features do not of course directly limit the scope of the present invention.
For the reasons, the DC-DC provided by the embodiment of the application can be used for protecting the diode bearing the back voltage, so that the type selection is easy, the cost is reduced, and the safety of the switching tube is ensured.
As shown in fig. 12-a and 12-b, in one aspect, the present invention provides a BOOST power conversion circuit, which includes a power source Vin, an inductor L1, a first switch module, a second switch module, a third diode D3, a fourth diode D4, and a flying capacitor C1; the power source Vin, the inductor L1, the first switch module and the second switch module form a first closed loop;
further comprising a first switch S1 and a flying capacitor initial voltage setup circuit comprising a first resistor, a second resistor and a third resistor; the first resistor is connected in parallel with the fourth diode, the second resistor is connected in parallel with the first capacitor, one end of the third resistor is connected to the negative end of the first capacitor, and the other end of the third resistor is connected to the negative end of the direct current bus; a second closed loop formed by the power Vin, the inductor L1, the third diode D3, the second resistor R2, the first capacitor C1, the first switch S1 and the second switch tube module; the power source Vin, the inductor L1, the first switch module, the first switch S1, the second resistor R2 and the first capacitor C1 are connected in parallel, the first resistor R1 and the fourth diode D4 are connected in parallel, and an output bus forms a third closed loop; the flying capacitor initial voltage establishing circuit is used for enabling the voltage stress of the second switch module to be smaller than the input voltage of the boost power conversion circuit and enabling the voltage stress borne by the fourth diode to be smaller than the bus voltage of the power conversion circuit, wherein the input voltage is the voltage difference between the input positive pole and the input negative pole, and the bus voltage is the voltage difference between the positive bus voltage and the negative bus voltage.
The first switch module comprises a first switch tube T1 and a first diode D1, the second switch module comprises a second switch tube T2 and a second diode D2, the negative pole end of the diode is connected with the collector electrode of the switch tube, and the positive pole end of the diode is connected with the emitter electrode of the switch tube. The three-phase inverter further comprises a third bus capacitor C3 and a fourth bus capacitor C4, wherein the first switch module, the second switch module, the third diode D3, the fourth diode D4, the third bus capacitor C3 and the fourth bus capacitor C4 form a fourth closed loop. The direct current bus-bar power supply device further comprises a load unit, wherein one end of the load unit is connected with the positive pole of the direct current bus-bar, and the other end of the load unit is connected with the negative pole of the direct current bus-bar.
According to the flying capacitor initial voltage establishing circuit added in the invention, when any path of MPPT of the photovoltaic grid-connected inverter is electrified, the first switch S1 is kept to be disconnected, at the moment, the input voltage Vin, the inductor L1, the third diode D3, the second resistor R2, the first capacitor C1 and the third resistor R3 form a loop, if the input voltage of the first path of MPPT1 reaches the working threshold voltage Vstart of the MPPT, at the moment, the direct current bus voltage is equal to the input voltage of the current first path of MPPT1, the input voltage Vin is connected with the flying capacitor C1 and the second capacitor R3 in parallel through the inductor L1, the third diode D3 and the second capacitor R2 to form a circuit branch, VC1 is β when the Vin α is β, once the voltage of the flying capacitor C1 is established, the switch S1 of the first path of MPPT1 can be closed, the circuit enters a normal working state, and as the voltage of the flying capacitor S1 is already closed, the flying capacitor is enabled to cause the breakdown of the flying capacitor to be over-zero.
If the input voltage of the MPPT2 is lower than the operating threshold voltage Vstart of the MPPT, the normal operation of the BOOST converter cannot be satisfied, the switch S1 keeps the off state, and since the MPPT1 and the MPPT2 share the dc bus Vout, the dc bus voltage is established by the MPPT 1. According to kirchhoff loop voltage law, a circuit relationship is established by connecting a flying capacitor C1 and a third resistor R3 in parallel through a first resistor R1 and a second resistor R2, and finally VC1 is known to be gamma Vout under a steady-state condition. Therefore, the initial voltage of the flying capacitor of the MPPT which is not started to operate can be established, once the input voltage of the MPPT2 meets the operation threshold voltage Vstart of the BOOST converter, the switch S1 can be closed to enable the flying capacitor to normally operate, and due to the voltage division effect of the flying capacitor, the reverse voltage of the diode D4 is prevented from being higher, the purpose of reducing the reverse withstand voltage of the diode D4 is achieved, the device selection is facilitated, the working efficiency of a circuit system is improved, and the cost is reduced.
On the other hand, when the voltage at the input end of the BOOST power conversion circuit is lower than the starting voltage of the BOOST power conversion circuit, the flying capacitor initial voltage establishing circuit enables the voltage stress borne by the second switching tube to be smaller than the input voltage, wherein the input voltage is the voltage difference between the input anode and the input cathode; the flying capacitor initial voltage establishing circuit enables the voltage stress born by the fourth diode to be smaller than the bus voltage of the boost power conversion circuit, and the bus voltage is the voltage difference between the positive bus voltage and the negative bus voltage.
Such alterations and modifications as are made obvious by those skilled in the art and guided by the teachings herein are intended to be within the scope of the invention as claimed.
Claims (5)
1. A BOOST power conversion circuit comprises a power source Vin, an inductor L1, a first switch module, a second switch module, a third diode D3, a fourth diode D4 and a flying capacitor C1; the power source Vin, the inductor L1, the first switch module and the second switch module form a first closed loop;
the method is characterized in that: the flying capacitor voltage setting circuit comprises a first switch S1 and a flying capacitor initial voltage setting circuit, wherein the flying capacitor initial voltage setting circuit comprises a first resistor, a second resistor and a third resistor; the first resistor is connected in parallel with the fourth diode, the second resistor is connected in parallel with the first capacitor, one end of the third resistor is connected to the negative end of the first capacitor, and the other end of the third resistor is connected to the negative end of the direct current bus;
a second closed loop formed by the power Vin, the inductor L1, the third diode D3, the second resistor R2, the first capacitor C1, the first switch S1 and the second switch tube module;
the power source Vin, the inductor L1, the first switch module, the first switch S1, the second resistor R2, the first capacitor C1, the first resistor R1 and the fourth diode D4 are connected in parallel, and an output bus forms a third closed loop;
the flying capacitor initial voltage establishing circuit is used for enabling the voltage stress of the second switch module to be smaller than the input voltage of the boost power conversion circuit and enabling the voltage stress borne by the fourth diode to be smaller than the bus voltage of the power conversion circuit, wherein the input voltage is the voltage difference between an input anode and an input cathode, and the bus voltage is the voltage difference between a positive bus voltage and a negative bus voltage.
2. The BOOST power conversion circuit of claim 1, wherein: the first switch module comprises a first switch tube T1 and a first diode D1, the second switch module comprises a second switch tube T2 and a second diode D2, the negative pole end of the diode is connected with the collector electrode of the switch tube, and the positive pole end of the diode is connected with the emitter electrode of the switch tube.
3. The BOOST power conversion circuit according to claim 1 or 2, wherein: the three-phase inverter further comprises a third bus capacitor C3 and a fourth bus capacitor C4, wherein the first switch module, the second switch module, the third diode D3, the fourth diode D4, the third bus capacitor C3 and the fourth bus capacitor C4 form a fourth closed loop.
4. The BOOST power conversion circuit of claim 3, wherein: the direct current bus-bar power supply device further comprises a load unit, wherein one end of the load unit is connected with the positive pole of the direct current bus-bar, and the other end of the load unit is connected with the negative pole of the direct current bus-bar.
5. A method of controlling a BOOST BOOST power conversion circuit according to any one of claims 1 to 4, characterized in that: when the voltage of the input end of the boost power conversion circuit is lower than the starting voltage of the boost power conversion circuit, the flying capacitor initial voltage establishing circuit enables the voltage stress borne by the second switch tube to be smaller than the input voltage, wherein the input voltage is the voltage difference between the input anode and the input cathode;
the flying capacitor initial voltage establishing circuit enables the voltage stress born by the fourth diode to be smaller than the bus voltage of the boost power conversion circuit, and the bus voltage is the voltage difference between the positive bus voltage and the negative bus voltage.
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| CN202010260983.8A CN111371323A (en) | 2020-04-03 | 2020-04-03 | BOOST power conversion circuit and control method thereof |
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN114421761A (en) * | 2022-03-30 | 2022-04-29 | 阳光电源股份有限公司 | Three-level converter with flying capacitor and control method |
| CN115694192A (en) * | 2021-07-26 | 2023-02-03 | 中兴通讯股份有限公司 | Voltage conversion circuit, control method, power supply device, and storage medium |
-
2020
- 2020-04-03 CN CN202010260983.8A patent/CN111371323A/en active Pending
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN115694192A (en) * | 2021-07-26 | 2023-02-03 | 中兴通讯股份有限公司 | Voltage conversion circuit, control method, power supply device, and storage medium |
| CN115694192B (en) * | 2021-07-26 | 2024-04-26 | 中兴通讯股份有限公司 | Voltage conversion circuit, control method, power supply device, and storage medium |
| CN114421761A (en) * | 2022-03-30 | 2022-04-29 | 阳光电源股份有限公司 | Three-level converter with flying capacitor and control method |
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