CN111211685A - DC-DC converter, bidirectional DC-DC converter and uninterruptible power supply comprising bidirectional DC-DC converter - Google Patents

DC-DC converter, bidirectional DC-DC converter and uninterruptible power supply comprising bidirectional DC-DC converter Download PDF

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Publication number
CN111211685A
CN111211685A CN201811390543.3A CN201811390543A CN111211685A CN 111211685 A CN111211685 A CN 111211685A CN 201811390543 A CN201811390543 A CN 201811390543A CN 111211685 A CN111211685 A CN 111211685A
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CN
China
Prior art keywords
inductor
diode
switching tube
converter
capacitor
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Granted
Application number
CN201811390543.3A
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Chinese (zh)
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CN111211685B (en
Inventor
李化良
欧阳华奋
郑大为
袁沛华
刘学钢
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Eaton Corp
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Eaton Corp
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Priority to CN201811390543.3A priority Critical patent/CN111211685B/en
Priority to PCT/EP2019/025413 priority patent/WO2020104068A1/en
Publication of CN111211685A publication Critical patent/CN111211685A/en
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Publication of CN111211685B publication Critical patent/CN111211685B/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/0068—Battery or charger load switching, e.g. concurrent charging and load supply
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
    • H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
    • H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
    • H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J9/00—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting
    • H02J9/04—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source
    • H02J9/06—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source with automatic change-over, e.g. UPS systems
    • H02J9/061—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source with automatic change-over, e.g. UPS systems for DC powered loads
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/1557—Single ended primary inductor converters [SEPIC]
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Charge And Discharge Circuits For Batteries Or The Like (AREA)

Abstract

The invention provides a DC-DC converter, a bidirectional DC-DC converter and an uninterruptible power supply comprising the bidirectional DC-DC converter, wherein the DC-DC converter comprises: the first inductor, the first switching tube and the second inductor are connected in sequence; the first diode, the third inductor and the second diode are connected in sequence; a first capacitor connected between a node formed by connecting one end of the first switching tube and the first inductor and an anode of the second diode; and a second capacitor connected between a node formed by connecting the other end of the first switch tube and the second inductor and the cathode of the first diode. The DC-DC converter can charge the rechargeable battery in a voltage reduction or voltage boosting mode, or discharge the rechargeable battery in a voltage reduction or voltage boosting mode, and can be applied to the parallel connection of uninterruptible power supplies.

Description

DC-DC converter, bidirectional DC-DC converter and uninterruptible power supply comprising bidirectional DC-DC converter
Technical Field
The invention relates to the field of electronic circuits, in particular to a DC-DC converter, a bidirectional DC-DC converter and an uninterruptible power supply comprising the bidirectional DC-DC converter.
Background
A DC-DC converter is an electrical device widely used in uninterruptible power supplies. The input end of the DC-DC converter is connected to the rechargeable battery, and the output end of the DC-DC converter is connected to the positive and negative direct current buses in the uninterruptible power supply. When the commercial power fails, the DC-DC converter boosts the direct current in the rechargeable battery and outputs the boosted direct current to the positive and negative direct current buses.
Fig. 1 is a circuit diagram of a first prior art DC-DC converter connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a charging mode. As shown in fig. 1, the DC-DC converter 1 includes an inductor L11, a capacitor C11, and a diode D12, and an igbt T11 and an inductor L13, which are connected in this order between the positive DC bus 11 and the positive electrode of the rechargeable battery B, one end of the inductor L11, one end of the capacitor C11, and the collector of the igbt T11 are connected, the other end of the capacitor C11, the anode of the diode D12, and one end of the inductor L13 are connected, and the negative electrode of the rechargeable battery B, the other end of the inductor L13, and the emitter of the igbt T11 are connected to the negative DC bus 12.
In fig. 1, at this time, the DC-DC converter 1 can only be controlled to transfer the electric energy on the capacitance between the positive and negative DC buses to the rechargeable battery B, but cannot transfer the electric energy in the rechargeable battery B to the capacitance between the positive and negative DC buses, and thus cannot transfer the energy in both directions. To achieve bidirectional transfer of energy, the cost of the circuit modules of the ups is increased.
In practical applications of an uninterruptible power supply, it is often necessary to connect multiple uninterruptible power supply power modules in parallel in order to increase power density.
Fig. 2 is a circuit diagram of two uninterruptible power supplies including the DC-DC converter shown in fig. 1 connected in parallel, and as shown in fig. 2, the negative pole of the rechargeable battery B is connected to the negative DC buses 121, 122 of the two uninterruptible power supplies at the same time, so that each control device (not shown in fig. 2) cannot independently control the voltage on the negative DC bus of the corresponding uninterruptible power supply. As can be seen, the DC-DC converter 1 shown in fig. 1 cannot be applied to parallel connection of a plurality of uninterruptible power supplies.
Fig. 3 is a circuit diagram of the DC-DC converter shown in fig. 1 connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a discharge mode. As shown in fig. 3, the cathode of the diode D12 is connected to the positive dc bus 11, the other end of the inductor L11 is connected to the positive electrode of the rechargeable battery B, and the cathode of the rechargeable battery B, the emitter of the igbt T11, and one end of the inductor L13 are connected to the negative dc bus 12.
In fig. 3, at this time, the DC-DC converter 1 can only be controlled to transfer the electric energy in the rechargeable battery B to the capacitor between the positive and negative DC buses, and bidirectional transfer of energy cannot be achieved. To achieve bidirectional transfer of energy, the cost of the circuit modules of the ups is increased.
Fig. 4 is a circuit diagram of two ups including the DC-DC converter shown in fig. 3 connected in parallel, and as shown in fig. 4, the negative pole of rechargeable battery B is also connected to the negative DC bus of the two ups. Each control device (not shown in fig. 4) is therefore likewise unable to independently control the voltage on the negative dc bus of the corresponding ups. As can be seen, the DC-DC converter 1 cannot be applied to parallel connection of a plurality of uninterruptible power supplies.
Fig. 5 is a circuit diagram of a second prior art DC-DC converter connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a charging mode. As shown in fig. 5, the DC-DC converter 2 includes an igbt T22, a capacitor C21, and an inductor L21, and an inductor L23 and a diode D21, which are connected in this order between the positive DC bus 21 and the positive electrode of the rechargeable battery B. One end of the inductor L23, the emitter of the insulated gate bipolar transistor T22 and one end of the capacitor C21 are connected, the cathode of the diode D21, the other end of the capacitor C21 and one end of the inductor L21 are connected, and the cathode of the rechargeable battery B, the anode of the diode D21 and the other end of the inductor L23 are connected to the negative direct current bus 22.
In fig. 5, at this time, the DC-DC converter 2 can only be controlled to transmit the electric energy on the capacitance between the positive and negative DC buses to the rechargeable battery B, but cannot transmit the electric energy in the rechargeable battery B to the capacitance between the positive and negative DC buses, and cannot realize bidirectional energy transmission. To achieve bidirectional transfer of energy, the cost of the circuit modules of the ups is increased.
Fig. 6 is a circuit diagram of two ups including the DC-DC converter shown in fig. 5 connected in parallel, and as shown in fig. 6, the negative electrode of the rechargeable battery B is simultaneously connected to the negative DC bus of the two ups, so each control device (not shown in fig. 6) cannot independently control the voltage on the negative DC bus of the corresponding ups. Therefore, the DC-DC converter 2 cannot be applied to parallel connection of uninterruptible power supplies.
Fig. 7 is a circuit diagram of the DC-DC converter shown in fig. 5 connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a discharge mode. As shown in fig. 7, the other end of the inductor L21 is connected to the positive dc bus 21, the collector of the igbt T22 is connected to the positive electrode of the rechargeable battery B, and the negative electrode of the rechargeable battery B, the other end of the inductor L23, and the anode of the diode D21 are connected to the negative dc bus 22.
In fig. 7, at this time, the DC-DC converter 2 can only be controlled to transfer the electric energy in the rechargeable battery B to the capacitor between the positive and negative DC buses, and bidirectional transfer of energy cannot be achieved. To achieve bidirectional transfer of energy, the cost of the circuit modules of the ups is increased.
Fig. 8 is a circuit diagram of two uninterruptible power supplies including the DC-DC converter shown in fig. 7 connected in parallel, and as shown in fig. 7, the negative pole of rechargeable battery B is connected to the negative DC bus of the two uninterruptible power supplies. Each control device (not shown in fig. 7) is therefore unable to independently control the voltage on the negative dc bus of the corresponding ups. Therefore, the DC-DC converter 2 cannot be applied to parallel connection of uninterruptible power supplies.
Disclosure of Invention
In view of the above technical problems in the prior art, the present invention provides a DC-DC converter, including:
the first inductor, the first switching tube and the second inductor are connected in sequence;
the first diode, the third inductor and the second diode are connected in sequence;
a first capacitor connected between a node formed by connecting one end of the first switching tube and the first inductor and an anode of the second diode; and
and the second capacitor is connected between a node formed by connecting the other end of the first switch tube and the second inductor and the cathode of the first diode.
Preferably, when the first switch tube is turned on, the first inductor, the first switch tube and the second inductor form a first current path, and the first capacitor, the first switch tube, the second capacitor and the third inductor form a second current path; when the first switch tube is cut off, the first diode, the third inductor and the second diode form a third current path.
Preferably, the first switch tube is a first insulated gate bipolar transistor, a collector of the first switch tube is connected to a node formed by connecting one end of the first inductor with the first capacitor, an emitter of the first switch tube is connected to a node formed by connecting one end of the second inductor with the second capacitor, the other end of the first inductor and the other end of the second inductor are respectively used for being connected to a positive electrode and a negative electrode of a first dc power supply device, and a cathode of the second diode and an anode of the first diode are respectively used for being connected to a positive electrode and a negative electrode of a second dc power supply device.
Preferably, the DC-DC converter further includes:
a diode connected in reverse parallel with the first switching tube;
the second switch tube is connected with the first diode in an inverse parallel mode; and
and the third switching tube is connected with the second diode in inverse parallel.
Preferably, the control device is further configured to provide a pulse width modulation signal to the first switching tube to alternately turn on and off.
Preferably, a control device is also included for
Controlling the second switching tube and the third switching tube to be cut off, and providing a pulse width modulation signal for the first switching tube to enable the first switching tube to be alternately switched on and off; or
And controlling the first switching tube to be switched off, and providing the same pulse width modulation signals for the second switching tube and the third switching tube, so that the second switching tube is switched on and switched off alternately, and the third switching tube is switched on and switched off alternately.
The present invention also provides a DC-DC converter including:
the first switch tube, the first inductor and the second switch tube are connected in sequence;
the second inductor, the first diode and the third inductor are connected in sequence;
a first capacitor connected between a cathode of the first diode and one end of the first inductor; and
a second capacitor connected between the anode of the first diode and the other end of the first inductor.
Preferably, when the first switch tube and the second switch tube are both turned on, the first switch tube, the first inductor and the second switch tube form a first current path; when the first switch tube and the second switch tube are both turned off, the second inductor, the first diode and the third inductor form a second current path, and the first capacitor, the first inductor, the second capacitor and the first diode form a third current path.
Preferably, the first switch tube is a first insulated gate bipolar transistor, and an emitter of the first switch tube is connected to a node formed by connecting one end of the first inductor and the first capacitor; the second switch tube is a second insulated gate bipolar transistor, and a collector electrode of the second switch tube is connected to a node formed by connecting the other end of the first inductor with the second capacitor; the collector of the first insulated gate bipolar transistor and the emitter of the second insulated gate bipolar transistor are respectively used for being connected to the positive pole and the negative pole of the first direct current power supply device, and the third inductor and the second inductor are respectively used for being connected to the positive pole and the negative pole of the second direct current power supply device.
Preferably, the DC-DC converter further includes:
a third switching tube connected in reverse parallel with the first diode;
the second diode is connected with the first switching tube in an inverse parallel mode; and
and the third diode is connected with the second switching tube in an inverse parallel mode.
Preferably, the pulse width modulation circuit further comprises a control device for providing the same pulse width modulation signal to the first switching tube and the second switching tube, so that the first switching tube is alternately turned on and off and the second switching tube is alternately turned on and off.
Preferably, a control device is also included for
Controlling the third switching tube to be switched off, and providing the same pulse width modulation signals for the first switching tube and the second switching tube to enable the first switching tube to be switched on and switched off alternately and enable the second switching tube to be switched on and switched off alternately; or
And controlling the first switching tube and the second switching tube to be cut off, and providing a pulse width modulation signal to the third switching tube to enable the third switching tube to be alternately switched on and off.
The present invention also provides a bidirectional DC-DC converter, comprising:
the first inductor and the first switching tube are connected;
a first diode connected in inverse parallel with the first switching tube;
the second inductor and the second diode are connected;
a second switch tube connected in reverse parallel with the second diode;
a first capacitor, one end of which is connected to the cathode of the first diode, and the other end of which is connected to a node formed by connecting the anode of the second diode and one end of the second inductor;
wherein an anode of the first diode is electrically connected to the other end of the second inductor.
Preferably, the first switch tube is a first insulated gate bipolar transistor, a collector of the first switch tube is connected to a node formed by connecting one end of the first inductor with the first capacitor, and an emitter of the first switch tube and the other end of the first inductor are respectively used for connecting to a negative electrode and a positive electrode of the first dc power supply device; the second switch tube is a second insulated gate bipolar transistor, an emitter of the second switch tube is connected to a node formed by connecting one end of the second inductor with the first capacitor, and a collector of the second switch tube and the other end of the second inductor are respectively used for being connected to a positive electrode and a negative electrode of a second direct current power supply device.
Preferably, the bidirectional DC-DC converter further includes:
a third inductor connected to an anode of the first diode;
a second capacitor connected between an anode of the first diode and the other end of the second inductor;
a third diode, a cathode of which is connected to the other end of the second inductor;
a third switching tube connected in reverse parallel with the third diode;
the first inductor and the third inductor are respectively used for being connected to the positive pole and the negative pole of the first direct current power supply device, and the cathode of the second diode and the anode of the third diode are respectively used for being connected to the positive pole and the negative pole of the second direct current power supply device.
Preferably, a control device is also included for
Controlling the second switching tube to be cut off, and providing a pulse width modulation signal for the first switching tube to enable the first switching tube to be alternately switched on and off; or
And controlling the first switching tube to be cut off, and providing a pulse width modulation signal to the second switching tube to enable the second switching tube to be alternately switched on and off.
Preferably, a control device is also included for
Controlling the second switching tube and the third switching tube to be cut off, and providing a pulse width modulation signal for the first switching tube to enable the first switching tube to be alternately switched on and off; or
And controlling the first switching tube to be switched off, and providing the same pulse width modulation signal for the second switching tube and the third switching tube to enable the second switching tube to be switched on and switched off alternately and enable the third switching tube to be switched on and switched off alternately.
The invention also provides an uninterruptible power supply, comprising:
a DC-DC converter as described above, or a bidirectional DC-DC converter as described above, connected between the positive and negative DC busses and the rechargeable battery;
the input end of the power factor correction circuit is used for being connected to an alternating current power supply, and the output end of the power factor correction circuit is connected to the positive direct current bus and the negative direct current bus; and
and the input end of the inverter is connected to the positive and negative direct current buses, and the output end of the inverter is used for providing alternating current.
The DC-DC converter can charge the rechargeable battery in a voltage reduction or voltage boosting mode, or discharge the rechargeable battery in a voltage reduction or voltage boosting mode, and can be applied to the parallel connection of uninterruptible power supplies. The bidirectional DC-DC converter of the invention can also realize bidirectional transmission of energy.
Drawings
Embodiments of the invention are further described below with reference to the accompanying drawings, in which:
fig. 1 is a circuit diagram of a first prior art DC-DC converter connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a charging mode.
Fig. 2 is a circuit diagram of two uninterruptible power supplies including the DC-DC converter shown in fig. 1 connected in parallel.
Fig. 3 is a circuit diagram of the DC-DC converter shown in fig. 1 connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a discharge mode.
Fig. 4 is a circuit diagram of two uninterruptible power supplies including the DC-DC converter shown in fig. 3 connected in parallel.
Fig. 5 is a circuit diagram of a second prior art DC-DC converter connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a charging mode.
Fig. 6 is a circuit diagram of two uninterruptible power supplies including the DC-DC converter of fig. 5 connected in parallel.
Fig. 7 is a circuit diagram of the DC-DC converter shown in fig. 5 connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a discharge mode.
Fig. 8 is a circuit diagram of two uninterruptible power supplies including the DC-DC converter shown in fig. 7 connected in parallel.
Fig. 9 is a circuit diagram of a DC-DC converter according to a first embodiment of the present invention.
Fig. 10 and 11 are circuit diagrams of the DC-DC converter shown in fig. 9 connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a charging mode.
Fig. 12 and 13 are circuit diagrams of the DC-DC converter shown in fig. 9 connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a discharge mode.
Fig. 14 is a circuit diagram of two uninterruptible power supplies including the DC-DC converter shown in fig. 10 connected in parallel.
Fig. 15 is a circuit diagram of two uninterruptible power supplies including the DC-DC converter shown in fig. 12 connected in parallel.
Fig. 16 is a circuit diagram of a DC-DC converter according to a second embodiment of the present invention.
Fig. 17 is a circuit diagram of the DC-DC converter of fig. 16 connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a charging mode.
Fig. 18 and 19 are circuit diagrams of the DC-DC converter shown in fig. 16 connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a discharge mode.
Fig. 20 is a circuit diagram of two uninterruptible power supplies including the DC-DC converter shown in fig. 17 connected in parallel.
Fig. 21 is a circuit diagram of two uninterruptible power supplies including the DC-DC converter shown in fig. 18 connected in parallel.
Fig. 22 is a circuit diagram of a DC-DC converter according to a third embodiment of the present invention.
Fig. 23 is a circuit diagram of the DC-DC converter shown in fig. 22 connected between a DC bus of an uninterruptible power supply and a rechargeable battery.
Fig. 24 is an equivalent circuit diagram of the DC-DC converter shown in fig. 23 in the charging mode.
Fig. 25 is an equivalent circuit diagram of the DC-DC converter shown in fig. 23 in a discharge mode.
Fig. 26 is a circuit diagram of two uninterruptible power supplies including the DC-DC converter shown in fig. 22 connected in parallel.
Fig. 27 is a circuit diagram of a bidirectional DC-DC converter according to a fourth embodiment of the present invention.
Fig. 28 is a circuit diagram of the bi-directional DC-DC converter of fig. 27 connected between a DC bus and a rechargeable battery of an uninterruptible power supply.
Fig. 29 and 30 are equivalent circuit diagrams of the bidirectional DC-DC converter in the charging mode.
Fig. 31 and 32 are equivalent circuit diagrams of the bidirectional DC-DC converter in the discharge mode.
Fig. 33 is a circuit diagram of a bidirectional DC-DC converter according to a fifth embodiment of the present invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention will be further described in detail by embodiments with reference to the accompanying drawings.
Fig. 9 is a circuit diagram of a DC-DC converter according to a first embodiment of the present invention. The DC-DC converter 3 comprises an inductor L31, an insulated gate bipolar transistor T31 and an inductor L32 which are connected in sequence, a diode D33, an inductor L33 and a diode D32 which are connected in sequence, a capacitor C31 and a capacitor C32, wherein one end of the capacitor C31 is connected to a node formed by connecting an inductor L31 and a collector of the insulated gate bipolar transistor T31, and the other end of the capacitor C31 is connected to an anode of a diode D32; one end of the capacitor C32 is connected to a node formed by connecting one end of the inductor L32 and the emitter of the igbt T31, and the other end is connected to the cathode of the diode D33.
Wherein, one end of the inductor L31 and the other end of the inductor L32 are respectively used for connecting to the positive electrode and the negative electrode of a DC power supply device (such as a capacitor or a rechargeable battery), and the cathode of the diode D32 and the anode of the diode D33 are respectively used as the positive electrode output terminal and the negative electrode output terminal of the DC-DC converter 3 for connecting to the positive electrode and the negative electrode of another DC power supply device (such as a capacitor or a rechargeable battery).
As can be seen from fig. 1 and 9, the DC-DC converter 3 differs from the DC-DC converter 1 shown in fig. 1 in that it further includes an inductor L32 connected to the emitter of the igbt T31, a capacitor C32 connected between the emitter of the igbt T31 and the inductor L33, and a diode D33, and the cathode of the diode D33 is connected to a node formed by connecting the capacitor C32 and the inductor L33.
The operation principle of the DC-DC converter 3 in the charging mode will be described with reference to fig. 10 and 11.
Fig. 10 and 11 are circuit diagrams of the DC-DC converter shown in fig. 9 connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a charging mode. As shown in fig. 10 and 11, the inductor L31 and the inductor L32 are connected to the positive dc bus bar 31 and the negative dc bus bar 32, respectively, and the cathode of the diode D32 and the anode of the diode D33 are connected to the positive electrode and the negative electrode of the rechargeable battery B, respectively.
The gate (i.e., the control terminal) of the igbt T31 is supplied with a pulse width modulated signal to be alternately turned on and off.
When the igbt T31 is turned on, as shown in fig. 10, the positive dc bus 31, the inductor L31, the igbt T31, the inductor L32, and the negative dc bus 32 form a current path, wherein the current direction is shown by the single arrow with a dotted line in fig. 10, and at this time, the inductor L31 and the inductor L32 store energy. Meanwhile, the inductor L33, the capacitor C31, the igbt T31, and the capacitor C32 form another current path, the current direction of which is shown by the dashed double arrow in fig. 10, and the capacitor C31 and the capacitor C32 discharge and store energy into the inductor L33.
When the igbt T31 is turned off, as shown in fig. 11, the positive dc bus 31, the inductor L31, the capacitor C31, the diode D32, the rechargeable battery B, the diode D33, the capacitor C32, the inductor L32, and the negative dc bus 32 form a current path, the current direction of which is shown by the single arrow with a broken line in fig. 11, and the inductor L31 and the inductor L32 release energy and store the energy in the capacitor C31, the rechargeable battery B, and the capacitor C32. Meanwhile, the diode D33, the inductor L33, the diode D32 and the rechargeable battery B form another current path, the current direction of which is shown by the dashed double arrow in fig. 11, and the inductor L33 releases energy and stores the energy into the rechargeable battery B.
As can be seen from fig. 10 and 11, the electric energy on the capacitor between the positive dc bus 31 and the negative dc bus 32 is finally stored in the rechargeable battery B, so that the rechargeable battery B is charged.
Assume that the capacitance C31 and the capacitance C32 have large capacitance values such that the ripple voltage thereof is negligible, and the voltages at the two ends of the capacitances C31 and C32 are U, respectivelyC1、UC2The voltage value between the positive direct current bus and the negative direct current bus is Udc, the voltage value of the rechargeable battery is Uo, and the voltage at a node formed by connecting an inductor L31, a capacitor C31 and a collector electrode of an insulated gate bipolar transistor T31 is UB1The voltage at the node formed by the connection of the capacitor C31, the anode of the diode D32 and the inductor L33 is UA1The voltage at the node formed by connecting the inductor L32, the capacitor C32 and the emitter of the IGBT T31 is UB2The voltage at the node formed by the connection of the capacitor C32, the cathode of the diode D33 and the inductor L33 is UA2. The period of the pwm signal is T, the duty cycle of the pwm signal is d, and the on time and the off time of the igbt T31 in one period of the pwm signal are Ton and Toff, respectively. One period of the pulse width modulated signal is taken as an example for explanation as follows.
When the igbt T31 is turned on, the following equation is satisfied:
UB1＝UB2and U isA1＝UA2-UC1-UC2
Then U isB1-UB20 and UA1-UA2＝-UC1-UC2
When the insulated gate bipolar transistor T31 is turned off, the following equation is satisfied:
UB1＝UB2+UC1+UC2+ UO and UA1＝UA2+Uo
Then U isB1-UB2＝Uo+UC1+UC2And U isA1-UA2＝Uo
In one switching period T, the following equation is satisfied:
Figure BDA0001873941410000101
the average voltage of the inductor L33 during one switching cycle is 0, and therefore,
(UB1-UB2) Average value of (1) ═ Udc
(UA1-UA2) is-UL3＝0
Then
Figure BDA0001873941410000102
Figure BDA0001873941410000103
Then
Figure BDA0001873941410000104
Figure BDA0001873941410000105
When the duty ratio d is less than 0.5, the rechargeable battery B is charged in a voltage reduction mode. When the duty ratio d is greater than 0.5, boost charging is performed on the rechargeable battery B.
The operation principle of the DC-DC converter 3 in the discharge mode will be described with reference to fig. 12 and 13.
Fig. 12 and 13 are circuit diagrams of the DC-DC converter shown in fig. 9 connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a discharge mode. The cathode of the diode D32 in the DC-DC converter 3 is connected to the positive DC bus 31, the anode of the diode D33 is connected to the negative DC bus 32, and the inductor L31 and the inductor L32 are connected to the positive electrode and the negative electrode of the rechargeable battery B, respectively.
The gate of the igbt T31 is supplied with a pulse width modulated signal to be alternately turned on and off.
When the igbt T31 is turned on, as shown in fig. 12, the rechargeable battery B, the inductor L31, the igbt T31 and the inductor L32 form a current path, the direction of which is shown by the single-headed arrow with a broken line in fig. 12, and the electric energy in the rechargeable battery B is stored in the inductor L31 and the inductor L32. Meanwhile, the inductor L33, the capacitor C31, the igbt T31, and the capacitor C32 form another current path, the current direction of which is shown by the dashed double arrows in fig. 12, and at this time, the capacitor C31 and the capacitor C32 discharge energy and store the energy onto the inductor L33.
When the igbt T31 is turned off, as shown in fig. 13, the rechargeable battery B, the inductor L31, the capacitor C31, the diode D32, the positive dc bus 31, the negative dc bus 32, the diode D33, the capacitor C32, and the inductor L32 form a current path, wherein the current direction is shown by a single arrow with a dotted line in fig. 13, and the inductor L31 and the inductor L32 discharge and store energy to the capacitor between the positive dc bus 31 and the negative dc bus 32. Meanwhile, the negative direct current bus bar 32, the diode D33, the inductor L33, the diode D32 and the positive direct current bus bar 31 form another current path, wherein the current direction is shown by a dotted double arrow in fig. 13, and the inductor L33 releases and stores energy to the capacitor between the positive direct current bus bar 31 and the negative direct current bus bar 32.
As can be seen from fig. 12 and 13, the electric energy in the rechargeable battery B is finally stored in the capacitor between the positive dc bus 31 and the negative dc bus 32, and the discharge of the rechargeable battery B is realized.
Assuming that the voltage value between the positive dc bus 31 and the negative dc bus 32 is Udc and the voltage value of the rechargeable battery B is Uo, based on the same derivation procedure as described above, it can be obtained:
Udc/Uo＝d/(1-d)。
when the duty ratio d is less than 0.5, the rechargeable battery B is discharged in a voltage reduction mode, and when the duty ratio d is more than 0.5, the rechargeable battery B is discharged in a voltage boosting mode.
Fig. 14 is a circuit diagram of two uninterruptible power supplies including the DC-DC converter shown in fig. 10 connected in parallel, and as shown in fig. 14, the negative electrode of the rechargeable battery B is connected to the negative DC bus 321 of one of the uninterruptible power supplies in order of a diode, a capacitor and an inductor, and is connected to the negative DC bus 322 of the other uninterruptible power supply in order of a diode, a capacitor and an inductor. The negative dc buses 321, 322 of the two upss are isolated from each other, and each control device (not shown in fig. 14) can independently charge the rechargeable battery B with the electric energy on the capacitor between the positive and negative dc buses of the corresponding ups, thereby independently controlling the voltage on the negative dc bus of each ups.
Fig. 15 is a circuit diagram of connecting two uninterruptible power supplies including the DC-DC converter shown in fig. 12 in parallel, in which the negative DC bus 321 'of one uninterruptible power supply is connected to the negative electrode of the rechargeable battery B sequentially through a diode, a capacitor and an inductor, and the negative DC bus 322' of the other uninterruptible power supply is connected to the negative electrode of the rechargeable battery B sequentially through a diode, a capacitor and an inductor, as shown in fig. 15. The negative dc buses 321 ', 322' of the two ups are isolated from each other, and each control device (not shown in fig. 15) can discharge and store the rechargeable battery B in the capacitor between the positive and negative dc buses of the corresponding ups, thereby independently controlling the voltage on the negative dc bus of each ups.
Fig. 16 is a circuit diagram of a DC-DC converter according to a second embodiment of the present invention. As shown in fig. 16, the DC-DC converter 4 includes an igbt T42, an inductor L43, and an igbt T43 connected in sequence, an inductor L42, a diode D41, and an inductor L41 connected in sequence, and a capacitor C41 and a capacitor C42, where one end of the capacitor C41 is connected to an emitter of the igbt T42, the other end is connected to a cathode of the diode D41, one end of the capacitor C42 is connected to a collector of the igbt T43, and the other end is connected to an anode of the diode D41.
Wherein, the collector of the igbt T42 and the emitter of the igbt T43 are respectively used to connect to the positive electrode and the negative electrode of a DC power supply device (such as a capacitor or a rechargeable battery), and one end of the inductor L41 and one end of the inductor L42 are respectively used as the positive output terminal and the negative output terminal of the DC-DC converter 4 and are used to connect to the positive electrode and the negative electrode of another DC power supply device (such as a capacitor or a rechargeable battery).
As can be seen from fig. 5 and 16, the DC-DC converter 4 is different from the DC-DC converter 2 shown in fig. 5 in that it further includes an igbt T43, a capacitor C42, and an inductor L42, wherein the capacitor C42 is connected between one end of the inductor L43 and the anode of the diode D41, the collector of the igbt T43 is connected to a node formed by connecting one end of the inductor L43 and the capacitor C42, and the inductor L42 is connected to the anode of the diode D41.
The operation principle of the DC-DC converter 4 in the charge mode and the discharge mode will be described below with reference to fig. 17 to 19.
Fig. 17 is a circuit diagram of the DC-DC converter of fig. 16 connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a charging mode. The collector of the igbt T42 is connected to the positive dc bus 41, the emitter of the igbt T43 is connected to the negative dc bus 42, and the inductor L41 and the inductor L42 are connected to the positive electrode and the negative electrode of the rechargeable battery B, respectively.
Fig. 18 and 19 are circuit diagrams of the DC-DC converter shown in fig. 16 connected between a DC bus of an uninterruptible power supply and a rechargeable battery and in a discharge mode. The collector of the insulated gate bipolar transistor T42 and the emitter of the insulated gate bipolar transistor T43 are connected to the positive and negative electrodes of the rechargeable battery B, respectively, and the inductor L41 and the inductor L42 are connected to the positive dc bus 41 and the negative dc bus 42, respectively.
The operation principle of the DC-DC converter 4 in the charging mode and the discharging mode is the same, and the operation principle thereof in the discharging mode will be described only with reference to fig. 18 and 19. In the discharge mode, the same pulse width modulated signal is provided to the gates of the igbt T42 and T43, causing the igbt T42 to turn on and off alternately and the igbt T43 to turn on and off alternately.
When the igbt T42 and the igbt T43 are both turned on, as shown in fig. 18, the rechargeable battery B, the igbt T42, the inductor L43, and the igbt T43 form a current path, the direction of the current is shown by a single arrow with a broken line in fig. 18, and the electric energy in the rechargeable battery B is stored in the inductor L43. Meanwhile, the rechargeable battery B, the insulated gate bipolar transistor T42, the capacitor C41, the inductor L41, the positive dc bus 41, the negative dc bus 42, the inductor L42, the capacitor C42 and the insulated gate bipolar transistor T43 form another current path, wherein the current direction is shown by a dashed double arrow in fig. 18, and at this time, the rechargeable battery B, the capacitor C41 and the capacitor C42 release energy and are stored in the inductor L41, the capacitor between the positive dc bus 41 and the negative dc bus 42, and the inductor L42.
When the igbts T42 and T43 are both turned off, as shown in fig. 19, the inductor L43, the capacitor C42, the diode D41 and the capacitor C41 form a current path, the current direction of which is shown by the single arrow with the dotted line in fig. 19, and the inductor L43 releases energy and stores the energy into the capacitor C41 and the capacitor C42. Meanwhile, the negative dc bus 42, the inductor L42, the diode D41, the inductor L41 and the positive dc bus 41 form another current path, the current direction of which is shown by the dashed double arrow in fig. 19, and at this time, the inductor L41 and the inductor L42 release energy and store the energy to the capacitor between the positive dc bus 41 and the negative dc bus 42.
As can be seen from fig. 18 and 19, the electric energy in the rechargeable battery B is finally stored in the capacitor between the positive dc bus 41 and the negative dc bus 42.
Assuming that the voltage value between the positive dc bus 41 and the negative dc bus 42 is Udc, the voltage value of the rechargeable battery B is Uo, and the voltage at the node formed by the connection of the inductor L41, the capacitor C41 and the cathode of the diode D41 is UB1The voltage at the node formed by connecting the inductor L42, the capacitor C42 and the anode of the diode D41 is UB2The voltage at the node formed by the connection of the capacitor C41, the emitter of the insulated gate bipolar transistor T42 and the inductor L43 is UA1Capacitor C42 and insulated gate bipolar transistor T4The voltage at the node formed by the connection of the collector of 3 and the inductor L43 is UA2The inductance values of the inductor L41, the inductor L42, and the inductor L43 are L1、L2、L3The current in the inductor L43 is iL3The current in inductor L41 and inductor L42 is iL1L2The voltages of the capacitor C41 and the capacitor C42 are respectively UC1And UC2The period of the pwm signal is T, the duty ratio of the pwm signal is d, and the on-time and the off-time of the igbt T42, T43 in one period of the pwm signal are Ton and Toff, respectively. The description will be given taking one period of the pulse width modulation signal as an example.
When both the insulated gate bipolar transistors T42, T43 are turned on, the following equation is satisfied:
Figure BDA0001873941410000141
then
Figure BDA0001873941410000148
Figure BDA0001873941410000143
Then
Figure BDA0001873941410000144
Figure BDA0001873941410000145
When the insulated gate bipolar transistors T42, T43 are both off, the following equation is satisfied:
Figure BDA0001873941410000146
then
Figure BDA0001873941410000147
Figure BDA0001873941410000151
Then
Figure BDA0001873941410000152
Figure BDA0001873941410000153
The average voltage of the inductor L43 in one switching cycle is 0, and thus the following equation is satisfied:
Figure BDA0001873941410000154
then (U)C1+UC2)*Toff＝Uo*Ton
Figure BDA0001873941410000155
Figure BDA0001873941410000156
Udc*Toff＝(Uo+UC1+UC2-Udc)*Ton
Udc*Toff＝(Uo+UC1+UC2-Udc)*Ton
Udc*Toff＝(Uo-Udc)*Ton+(UC1+UC2)*Ton
Figure BDA0001873941410000157
Figure BDA0001873941410000158
Figure BDA0001873941410000159
Figure BDA00018739414100001510
Figure BDA00018739414100001511
When the duty ratio d is less than 0.5, the rechargeable battery B is discharged in a voltage reduction mode, and when the duty ratio d is more than 0.5, the rechargeable battery B is discharged in a voltage boosting mode.
Fig. 20 is a circuit diagram of two ups including the DC-DC converter shown in fig. 17 connected in parallel, and as shown in fig. 20, each control device (not shown in fig. 20) can independently charge rechargeable battery B with power on the capacitor between the positive and negative DC buses of the corresponding ups, thereby independently controlling the voltage on the negative DC bus of each ups.
Fig. 21 is a circuit diagram of two ups including the DC-DC converter shown in fig. 18 connected in parallel, and as shown in fig. 21, each control device (not shown in fig. 21) can store the electric energy in the rechargeable battery B on the capacitor between the positive and negative DC buses of the corresponding ups, thereby independently controlling the voltage on the negative DC bus of each ups.
Fig. 22 is a circuit diagram of a DC-DC converter according to a third embodiment of the present invention. As shown in fig. 22, the DC-DC converter 5 is different from the DC-DC converter 3 shown in fig. 9 in that it further includes a diode D51 connected in inverse parallel with the igbt T51, and igbts T52 and T53 connected in inverse parallel with the diodes D52 and D53, respectively.
The DC-DC converter 5 is different from the DC-DC converter 4 shown in fig. 16 in that it further includes an insulated gate bipolar transistor T51 connected in inverse parallel with the diode D51, and diodes D52 and D53 connected in inverse parallel with the insulated gate bipolar transistors T52 and T53, respectively.
The other end of the inductor L51 and the other end of the inductor L52 are respectively used for being connected to the positive electrode and the negative electrode of a DC power supply device (such as a capacitor or a rechargeable battery), and the cathode of the diode D52 and the anode of the diode D53 are respectively used as the positive electrode output terminal and the negative electrode output terminal of the DC-DC converter 5 and are respectively used for being connected to the positive electrode and the negative electrode of another DC power supply device (such as a capacitor or a rechargeable battery). Or the cathode of the diode D52 and the anode of the diode D53 are respectively used for connecting to the positive pole and the negative pole of a direct current power supply device (such as a capacitor or a rechargeable battery), and the other end of the inductor L51 and the other end of the inductor L52 are respectively used as the positive pole output terminal and the negative pole output terminal of the DC-DC converter 5 for connecting to the positive pole and the negative pole of another direct current power supply device (such as a capacitor or a rechargeable battery).
Fig. 23 is a circuit diagram of the DC-DC converter shown in fig. 22 connected between a DC bus of an uninterruptible power supply and a rechargeable battery. As shown in fig. 23, one ends of the inductor L51 and the inductor L52 are connected to the positive dc bus 51 and the negative dc bus 52, respectively, the cathode of the diode D52 and the collector of the igbt T52 are connected to the anode of the rechargeable battery B, and the anode of the diode D53 and the emitter of the igbt T53 are connected to the cathode of the rechargeable battery B.
The operation principle of the DC-DC converter 5 in the charge mode and the discharge mode is described below with reference to fig. 24 and 25, respectively.
In the charging mode, the control device (not shown in fig. 23) controls the igbts T52 and T53 to be turned off, and supplies a pulse width modulation signal to the gate of the igbts T51 to be alternately turned on and off. Fig. 24 is an equivalent circuit diagram of the DC-DC converter shown in fig. 23 in the charging mode, which is the same as the circuits shown in fig. 10 and 11, and the specific control process is not repeated here, and the step-down charging or the step-up charging of the rechargeable battery B can also be realized.
In the discharge mode, the control device (not shown in fig. 23) controls the igbt T51 to be turned off, supplies the same pulse width modulation signal to the gates of the igbts T52 and T53, and alternately turns on and off the igbts T52 and turns on and off the igbts T53. Fig. 25 is an equivalent circuit diagram of the DC-DC converter shown in fig. 23 in the discharging mode, which is the same as the circuit shown in fig. 18 to 19, and the specific control process is not repeated here, and the rechargeable battery B can also realize the voltage boosting discharge or the voltage reducing discharge.
As can be seen from fig. 24 and 25, the DC-DC converter 5 of the present embodiment is a bidirectional DC-DC converter, and no additional charger or DC converter is required, thereby saving cost. The rechargeable battery B can realize voltage boosting discharge or voltage reducing discharge, and can also realize voltage reducing charge or voltage boosting charge. In the process of charging the rechargeable battery B, the capacitance between the positive direct current bus and the negative direct current bus can be deeply discharged by changing the duty ratio of the pulse width modulation signal, and the rechargeable battery B is charged by using the capacitance voltage close to 0V without generating impact current.
Fig. 26 is a circuit diagram of two uninterruptible power supplies including the DC-DC converter shown in fig. 22 connected in parallel, and each control device (not shown in fig. 26) can individually control the DC-DC converter in the corresponding uninterruptible power supply, and the detailed control manner thereof is not described herein again.
Fig. 27 is a circuit diagram of a bidirectional DC-DC converter according to a fourth embodiment of the present invention. As shown in fig. 27, the bidirectional DC-DC converter 6 includes an inductor L61 and an igbt T61 connected to each other, a diode D61 connected in inverse parallel with the igbt T61, an inductor L63 and a diode D62 connected to each other, an igbt T62 connected in inverse parallel with the diode D62, and a capacitor C61, wherein one end of the capacitor C61 is connected to a collector of the igbt T61 (i.e., a cathode of the diode D61), the other end is connected to a node formed by connecting an emitter of the igbt T62 (i.e., an anode of the diode D62) and the inductor L63, and an anode of the diode D61 is electrically connected to the other end of the inductor L63.
Wherein, one end of the inductor L61 and the anode of the diode D61 are respectively used for connecting to the positive electrode and the negative electrode of a DC power supply device (such as a capacitor or a rechargeable battery), and the cathode of the diode D62 and the other end of the inductor L63 are respectively used as the positive electrode output terminal and the negative electrode output terminal of the bidirectional DC-DC converter 6 for connecting to the positive electrode and the negative electrode of another DC power supply device (such as a capacitor or a rechargeable battery). Or the cathode of the diode D62 and the other end of the inductor L63 are respectively used for connecting to the positive pole and the negative pole of a DC power supply device (such as a capacitor or a rechargeable battery), and one end of the inductor L61 and the anode of the diode D61 are respectively used as the positive pole output terminal and the negative pole output terminal of the bidirectional DC-DC converter 6 for connecting to the positive pole and the negative pole of another DC power supply device (such as a capacitor or a rechargeable battery).
As will be understood from fig. 1 and 27, the bidirectional DC-DC converter 6 is different from the DC-DC converter 1 shown in fig. 1 in that it further includes a diode D61 connected in inverse parallel with the igbt T61, and an igbt T62 connected in inverse parallel with the diode D62.
As can be seen from fig. 5 and 27, the bidirectional DC-DC converter 6 is different from the DC-DC converter 2 shown in fig. 5 in that it further includes a diode D62 connected in inverse parallel with the igbt T62, and an igbt T61 connected in inverse parallel with the diode D61.
Fig. 28 is a circuit diagram of the bi-directional DC-DC converter shown in fig. 27 connected between the DC bus of the ups and the rechargeable battery, where inductor L61 is connected to the positive DC bus 61, the cathode of diode D62 and the collector of igbt T62 are connected to the positive pole of rechargeable battery B, and the negative pole of rechargeable battery B, inductor L63, the anode of diode D61 and the emitter of igbt T61 are connected to the negative DC bus 62.
The operation principle of the bidirectional DC-DC converter 6 in the charging mode and the discharging mode will be described below with reference to the equivalent circuit diagram of the converter.
Fig. 29 and 30 are equivalent circuit diagrams of the bidirectional DC-DC converter 6 in the charging mode.
In the charging mode, the control device (not shown in fig. 28) controls the igbt T62 to be turned off, and supplies the gate of the igbt T61 with a pulse width modulation signal to be alternately turned on and off.
As shown in fig. 29, when the igbt T61 is turned on, the positive dc bus 61, the inductor L61, the igbt T61, and the negative dc bus 62 form a current path, the direction of which is shown by the single-headed arrow with a broken line in fig. 29, and the inductor L61 stores energy. Meanwhile, the inductor L63, the capacitor C61 and the igbt T61 form another current path, wherein the current direction is shown by the dashed double arrow in fig. 29, and the capacitor C61 releases energy and stores the energy into the inductor L63.
As shown in fig. 30, when the igbt T61 is turned off, the positive dc bus 61, the inductor L61, the capacitor C61, the diode D62, the rechargeable battery B and the negative dc bus 62 form a current path, and the current direction is shown by a single arrow with a broken line in fig. 30, and the inductor L61 releases and stores energy into the capacitor C61 and the rechargeable battery B. At the same time, the inductor L63, the diode D62 and the rechargeable battery B form another current path, the current direction of which is shown by the dashed double arrow in fig. 30, and the inductor L63 releases energy and stores it in the rechargeable battery B.
As can be seen from fig. 29 and fig. 30, the electric energy on the capacitor between the positive dc bus 61 and the negative dc bus 62 is finally stored in the rechargeable battery B, and the rechargeable battery B is charged.
Assuming that the capacitor C61 has a large capacitance value such that its ripple voltage is negligible, the voltage across it is UC1The voltage value between the positive dc bus 61 and the negative dc bus 62 is Udc, and the voltage value of the rechargeable battery B is UoThe voltage of the negative DC bus 62, the negative electrode of the rechargeable battery B and the emitter of the IGBT T61 is U2The voltage at the node formed by connecting the inductor L61, the capacitor C61 and the collector of the IGBT T61 is UB1The voltage at the node formed by the connection of the capacitor C61, the anode of the diode D62 and the inductor L63 is UA1The period of the pwm signal is T, the duty ratio of the pwm signal is d, and the on time and the off time of the igbt T61 in one period of the pwm signal are Ton and Toff, respectively. The description will be given taking one period of the pulse width modulation signal as an example.
When the igbt T61 is turned on, the following equation is satisfied:
UB1＝U2and U isA1＝U2A UC1
Then U isB1-U20 and UA1-U2＝-UC1
When the insulated gate bipolar transistor T61 is turned off, the following equation is satisfied:
UB1＝U2+UC1+ UO and UA1＝U2+Uo
UB1-U2＝Uo+UC1And U isA1-U2＝Uo
In one switching cycle, the following equation is satisfied:
Figure BDA0001873941410000191
Figure BDA0001873941410000192
the average voltage of the inductor L63 during one switching cycle is 0, and therefore,
(UB1-U2) Average value of (1) ═ Udc
(UA1-U2) is-UL3＝0
Figure BDA0001873941410000193
Figure BDA0001873941410000194
Figure BDA0001873941410000201
From this, Uo/Udc is d/(1-d). When the duty ratio d is less than 0.5, the rechargeable battery B is charged in a voltage reduction mode. When the duty ratio d is greater than 0.5, boost charging is performed on the rechargeable battery B.
Fig. 31 and 32 are equivalent circuit diagrams of the bidirectional DC-DC converter 6 in the discharge mode.
In the discharge mode, the control device (not shown in fig. 28) controls the igbt T61 to be turned off, and supplies a pulse width modulation signal to the gate of the igbt T62 to be alternately turned on and off.
As shown in fig. 31, when the igbt T62 is turned on, the rechargeable battery B, the igbt T62 and the inductor L63 form a current path, the direction of which is shown by the single arrow with a broken line in fig. 31, and the inductor L63 stores energy. Meanwhile, the rechargeable battery B, the insulated gate bipolar transistor T62, the capacitor C61, the inductor L61, the positive dc bus 61 and the negative dc bus 62 form another current path, wherein the current direction is shown by a dashed double arrow in fig. 31, and at this time, the rechargeable battery B and the capacitor C61 release energy and store the energy into the inductor L61 and the capacitor between the positive dc bus 61 and the negative dc bus 62.
As shown in fig. 32, when the igbt T62 is turned off, the inductor L63, the diode D61 and the capacitor C61 form a current path, the current direction of which is shown by the single arrow with a broken line in fig. 32, and the inductor L63 discharges energy and stores the energy into the capacitor C61. Meanwhile, the inductor L61, the positive dc bus 61, the negative dc bus 62 and the diode D61 form another current path, the current direction of which is shown by the dashed double arrow in fig. 32, and at this time, the inductor L61 releases energy and stores the energy to the capacitor between the positive dc bus 61 and the negative dc bus 62.
As can be seen from fig. 31 and 32, the electric energy in the rechargeable battery B is finally stored in the capacitor between the positive dc bus 61 and the negative dc bus 62, and the discharge of the rechargeable battery B is realized.
Assuming that the capacitor C61 has a large capacitance value such that its ripple voltage is negligible, the voltage across it is UC1The voltage value between the positive dc bus 61 and the negative dc bus 62 is Udc, the voltage value of the rechargeable battery is Uo, and the voltage of the negative electrodes of the dc bus 61 and the rechargeable battery B is U2The voltage at the node formed by connecting the inductor L61, the capacitor C61 and the cathode of the diode D61 is UB1Capacitor C61, IGBT pairThe voltage at the node formed by the connection of the emitter of the polar transistor T62 and the inductor L63 is UA1The inductance values of the inductor L61 and the inductor L63 are L1And L3The currents in inductor L61 and inductor L63 are i respectivelyL1And iL3The period of the pwm signal is T, the duty ratio of the pwm signal is d, and the on time and the off time of the igbt T62 in one period of the pwm signal are Ton and Toff, respectively. The description will be given taking one period of the pulse width modulation signal as an example.
When the igbt T62 is turned on, the following equation is satisfied:
Figure BDA0001873941410000211
Figure BDA0001873941410000212
Figure BDA0001873941410000213
then
Figure BDA0001873941410000214
Figure BDA0001873941410000215
When the insulated gate bipolar transistor T62 is turned off, the following equation is satisfied:
Figure BDA0001873941410000216
Figure BDA0001873941410000217
Figure BDA0001873941410000218
then
Figure BDA0001873941410000219
Figure BDA00018739414100002110
Figure BDA0001873941410000221
The average voltage of the inductor L63 during one switching cycle is 0, and therefore,
Figure BDA0001873941410000222
then (U)C1)*Toff＝Uo*Ton
Figure BDA0001873941410000223
Figure BDA0001873941410000224
Then U isdc*Toff＝(Uo+UC1-Udc)*Ton
Udc*Toff＝(Uo-Udc)*Ton+(UC1)*Ton
Figure BDA0001873941410000225
Figure BDA0001873941410000226
Figure BDA0001873941410000227
Figure BDA0001873941410000228
Figure BDA0001873941410000229
From this, Udc/Uo is d/(1-d). When the duty ratio d is less than 0.5, the rechargeable battery B is discharged in a voltage reduction mode. When the duty ratio d is greater than 0.5, the rechargeable battery B is boosted and discharged.
The bidirectional DC-DC converter 6 can controllably realize the transmission of the electric energy on the capacitor between the positive direct current bus and the negative direct current bus to the rechargeable battery B, and realize the transmission of the electric energy in the rechargeable battery B to the capacitor between the positive direct current bus and the negative direct current bus, thereby realizing the bidirectional transmission of the energy.
Fig. 33 is a circuit diagram of a bidirectional DC-DC converter according to a fifth embodiment of the present invention. As shown in fig. 33, the bidirectional DC-DC converter 7 differs from the bidirectional DC-DC converter 6 of fig. 27 in that it further includes an inductor L72, a capacitor C72, and an insulated gate bipolar transistor T73 with an anti-parallel diode D73. Wherein the inductor L72 is connected to the anode of the diode D71 and the emitter of the igbt T71, the capacitor C72 is connected between the anode of the diode D71 and the inductor L73, and the collector of the igbt T73 (i.e., the cathode of the diode D73) is connected to the node formed by the connection of the capacitor C72 and the inductor L73.
Since the topology of the bidirectional DC-DC converter 7 is identical to that of the DC-DC converter 5, the operation principle thereof will not be described herein. The bidirectional DC-DC converter 7 can also be applied to parallel connection of uninterruptible power supplies.
In other embodiments of the present invention, a switch transistor such as a Metal Oxide Semiconductor Field Effect Transistor (MOSFET) is used instead of the igbt in the above embodiments.
The invention also provides an uninterruptible power supply, which comprises the DC-DC converter or the bidirectional DC-DC converter of the embodiment, a power factor correction circuit (PFC) and an inverter; wherein the DC-DC converter or bidirectional DC-DC converter is connected between the positive and negative DC bus and the rechargeable battery, the input of the PFC is connected to an alternating current power supply (e.g. mains), the output thereof is connected to the positive and negative DC bus, the input of the inverter is connected to the positive and negative DC bus, and the output thereof is used for supplying alternating current to the load.
Although the present invention has been described by way of preferred embodiments, the present invention is not limited to the embodiments described herein, and various changes and modifications may be made without departing from the scope of the present invention.

Claims (18)

1. A DC-DC converter, comprising:
the first inductor, the first switching tube and the second inductor are connected in sequence;
the first diode, the third inductor and the second diode are connected in sequence;
a first capacitor connected between a node formed by connecting one end of the first switching tube and the first inductor and an anode of the second diode; and
and the second capacitor is connected between a node formed by connecting the other end of the first switch tube and the second inductor and the cathode of the first diode.
2. The DC-DC converter according to claim 1, wherein when the first switch tube is turned on, the first inductor, the first switch tube and the second inductor form a first current path, and the first capacitor, the first switch tube, the second capacitor and the third inductor form a second current path; when the first switch tube is cut off, the first diode, the third inductor and the second diode form a third current path.
3. The DC-DC converter according to claim 2, wherein the first switch transistor is a first igbt, a collector of the first igbt is connected to a node formed by connecting one end of the first inductor to the first capacitor, and an emitter of the first igbt is connected to a node formed by connecting one end of the second inductor to the second capacitor, wherein the other end of the first inductor and the other end of the second inductor are respectively connected to a positive electrode and a negative electrode of a first DC power supply, and a cathode of the second diode and an anode of the first diode are respectively connected to a positive electrode and a negative electrode of a second DC power supply.
4. The DC-DC converter according to any one of claims 1 to 3, further comprising:
a diode connected in reverse parallel with the first switching tube;
the second switch tube is connected with the first diode in an inverse parallel mode; and
and the third switching tube is connected with the second diode in inverse parallel.
5. A DC-DC converter according to any of claims 1-3, further comprising a control device for providing a pulse width modulated signal to the first switching tube to alternately switch on and off.
6. DC-DC converter according to claim 4, characterized in that it further comprises control means for
Controlling the second switching tube and the third switching tube to be cut off, and providing a pulse width modulation signal for the first switching tube to enable the first switching tube to be alternately switched on and off; or
And controlling the first switching tube to be switched off, and providing the same pulse width modulation signals for the second switching tube and the third switching tube, so that the second switching tube is switched on and switched off alternately, and the third switching tube is switched on and switched off alternately.
7. A DC-DC converter, comprising:
the first switch tube, the first inductor and the second switch tube are connected in sequence;
the second inductor, the first diode and the third inductor are connected in sequence;
a first capacitor connected between a cathode of the first diode and one end of the first inductor; and
a second capacitor connected between the anode of the first diode and the other end of the first inductor.
8. The DC-DC converter according to claim 7, wherein when the first and second switching tubes are both conductive, the first switching tube, the first inductor and the second switching tube form a first current path; when the first switch tube and the second switch tube are both turned off, the second inductor, the first diode and the third inductor form a second current path, and the first capacitor, the first inductor, the second capacitor and the first diode form a third current path.
9. The DC-DC converter of claim 8,
the first switch tube is a first insulated gate bipolar transistor, and an emitter electrode of the first switch tube is connected to a node formed by connecting one end of the first inductor with the first capacitor;
the second switch tube is a second insulated gate bipolar transistor, and a collector electrode of the second switch tube is connected to a node formed by connecting the other end of the first inductor with the second capacitor;
the collector of the first insulated gate bipolar transistor and the emitter of the second insulated gate bipolar transistor are respectively used for being connected to the positive pole and the negative pole of the first direct current power supply device, and the third inductor and the second inductor are respectively used for being connected to the positive pole and the negative pole of the second direct current power supply device.
10. The DC-DC converter according to any one of claims 7 to 9, further comprising:
a third switching tube connected in reverse parallel with the first diode;
the second diode is connected with the first switching tube in an inverse parallel mode; and
and the third diode is connected with the second switching tube in an inverse parallel mode.
11. A DC-DC converter according to any of claims 7-9, further comprising a control device for providing the same pulse width modulated signal to the first and second switching tubes, for alternately switching the first switching tube on and off and for alternately switching the second switching tube on and off.
12. A DC-DC converter according to claim 10, further comprising control means for controlling the DC-DC converter
Controlling the third switching tube to be switched off, and providing the same pulse width modulation signals for the first switching tube and the second switching tube to enable the first switching tube to be switched on and switched off alternately and enable the second switching tube to be switched on and switched off alternately; or
And controlling the first switching tube and the second switching tube to be cut off, and providing a pulse width modulation signal to the third switching tube to enable the third switching tube to be alternately switched on and off.
13. A bidirectional DC-DC converter, comprising:
the first inductor and the first switching tube are connected;
a first diode connected in inverse parallel with the first switching tube;
the second inductor and the second diode are connected;
a second switch tube connected in reverse parallel with the second diode;
a first capacitor, one end of which is connected to the cathode of the first diode, and the other end of which is connected to a node formed by connecting the anode of the second diode and one end of the second inductor;
wherein an anode of the first diode is electrically connected to the other end of the second inductor.
14. The bi-directional DC-DC converter of claim 13,
the first switch tube is a first insulated gate bipolar transistor, a collector of the first switch tube is connected to a node formed by connecting one end of the first inductor with the first capacitor, and an emitter of the first switch tube and the other end of the first inductor are respectively used for being connected to a negative electrode and a positive electrode of the first direct current power supply device;
the second switch tube is a second insulated gate bipolar transistor, an emitter of the second switch tube is connected to a node formed by connecting one end of the second inductor with the first capacitor, and a collector of the second switch tube and the other end of the second inductor are respectively used for being connected to a positive electrode and a negative electrode of a second direct current power supply device.
15. The bi-directional DC-DC converter of claim 14, further comprising:
a third inductor connected to an anode of the first diode;
a second capacitor connected between an anode of the first diode and the other end of the second inductor;
a third diode, a cathode of which is connected to the other end of the second inductor;
a third switching tube connected in reverse parallel with the third diode;
the first inductor and the third inductor are respectively used for being connected to the positive pole and the negative pole of the first direct current power supply device, and the cathode of the second diode and the anode of the third diode are respectively used for being connected to the positive pole and the negative pole of the second direct current power supply device.
16. A bi-directional DC-DC converter according to claim 13 or 14, further comprising control means for controlling the DC-DC converter
Controlling the second switching tube to be cut off, and providing a pulse width modulation signal for the first switching tube to enable the first switching tube to be alternately switched on and off; or
And controlling the first switching tube to be cut off, and providing a pulse width modulation signal to the second switching tube to enable the second switching tube to be alternately switched on and off.
17. A bi-directional DC-DC converter according to claim 15, further comprising control means for controlling the DC-DC converter
Controlling the second switching tube and the third switching tube to be cut off, and providing a pulse width modulation signal for the first switching tube to enable the first switching tube to be alternately switched on and off; or
And controlling the first switching tube to be switched off, and providing the same pulse width modulation signal for the second switching tube and the third switching tube to enable the second switching tube to be switched on and switched off alternately and enable the third switching tube to be switched on and switched off alternately.
18. An uninterruptible power supply, comprising:
a DC-DC converter as claimed in any one of claims 1 to 12, or a bidirectional DC-DC converter as claimed in any one of claims 13 to 17, connected between positive and negative DC busses and a rechargeable battery;
the input end of the power factor correction circuit is used for being connected to an alternating current power supply, and the output end of the power factor correction circuit is connected to the positive direct current bus and the negative direct current bus; and
and the input end of the inverter is connected to the positive and negative direct current buses, and the output end of the inverter is used for providing alternating current.
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Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN112421135A (en) * 2020-11-20 2021-02-26 四川长虹电器股份有限公司 Series energy storage battery direct current conversion system and control method thereof
CN112583267A (en) * 2020-12-15 2021-03-30 山特电子（深圳）有限公司 Bidirectional DC-DC converter and uninterruptible power supply comprising same

Citations (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20120195077A1 (en) * 2009-07-10 2012-08-02 Thales Novel architecture of a compensator for power factors and harmonics for a power distribution system
CN103441668A (en) * 2013-08-26 2013-12-11 华南理工大学 High-gain boost DC-DC converter allowing pseudo continuous work
US20140009106A1 (en) * 2012-07-09 2014-01-09 Davide Andrea Limiting excessive currents during connection of a battery or cell in parallel with other batteries, cells or capacitive loads
CN105846532A (en) * 2015-01-13 2016-08-10 伊顿制造（格拉斯哥）有限合伙莫尔日分支机构 Uninterrupted power source and control method therefor
CN105991021A (en) * 2015-02-02 2016-10-05 山特电子（深圳）有限公司 Bidirectional dc-dc converter
KR20170050644A (en) * 2015-10-30 2017-05-11 포항공과대학교 산학협력단 Duplex dc-dc converter of non insulation type
US10014777B1 (en) * 2017-08-09 2018-07-03 Texas Instruments Incorporated Buck-boost DC-DC converter
CN207638560U (en) * 2017-12-06 2018-07-20 华盛新能源科技（深圳）有限公司 A kind of bidirectional DC-DC converter for electric vehicle
CN108809094A (en) * 2018-05-11 2018-11-13 山特电子（深圳）有限公司 uninterruptible power supply, DC-DC converter and its control method and control device
CN108832710A (en) * 2017-12-28 2018-11-16 伊顿公司 Charge and discharge balance converter for uninterruptible power supply

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE102017006819A1 (en) * 2016-09-22 2018-03-22 Sew-Eurodrive Gmbh & Co Kg System and method for operating a system

Patent Citations (12)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20120195077A1 (en) * 2009-07-10 2012-08-02 Thales Novel architecture of a compensator for power factors and harmonics for a power distribution system
US20140009106A1 (en) * 2012-07-09 2014-01-09 Davide Andrea Limiting excessive currents during connection of a battery or cell in parallel with other batteries, cells or capacitive loads
CN103441668A (en) * 2013-08-26 2013-12-11 华南理工大学 High-gain boost DC-DC converter allowing pseudo continuous work
CN105846532A (en) * 2015-01-13 2016-08-10 伊顿制造（格拉斯哥）有限合伙莫尔日分支机构 Uninterrupted power source and control method therefor
US20170373530A1 (en) * 2015-01-13 2017-12-28 Eaton Manufacturing LP, Glasgow Succursale De Morges Uninterruptible power supply and control method therefor
CN105991021A (en) * 2015-02-02 2016-10-05 山特电子（深圳）有限公司 Bidirectional dc-dc converter
US20180278158A1 (en) * 2015-02-02 2018-09-27 Santak Electronic (Shenzhen) Co., Ltd. Bidirectional dc-dc converter
KR20170050644A (en) * 2015-10-30 2017-05-11 포항공과대학교 산학협력단 Duplex dc-dc converter of non insulation type
US10014777B1 (en) * 2017-08-09 2018-07-03 Texas Instruments Incorporated Buck-boost DC-DC converter
CN207638560U (en) * 2017-12-06 2018-07-20 华盛新能源科技（深圳）有限公司 A kind of bidirectional DC-DC converter for electric vehicle
CN108832710A (en) * 2017-12-28 2018-11-16 伊顿公司 Charge and discharge balance converter for uninterruptible power supply
CN108809094A (en) * 2018-05-11 2018-11-13 山特电子（深圳）有限公司 uninterruptible power supply, DC-DC converter and its control method and control device

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
JUN KIKUCHI: "Three-Phase PWM Boost-Buck Rectifiers With Power-Regenerating Capability", 《IEEE TRANSACTIONS ON INDUSTRY APPLICATIONS》, vol. 38, no. 5, pages 1361 - 1369, XP011073530 *

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN112421135A (en) * 2020-11-20 2021-02-26 四川长虹电器股份有限公司 Series energy storage battery direct current conversion system and control method thereof
CN112583267A (en) * 2020-12-15 2021-03-30 山特电子（深圳）有限公司 Bidirectional DC-DC converter and uninterruptible power supply comprising same

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