CN111147116A - Signal synthesis method and device, storage medium, and electronic device - Google Patents

Signal synthesis method and device, storage medium, and electronic device Download PDF

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CN111147116A
CN111147116A CN201911224382.5A CN201911224382A CN111147116A CN 111147116 A CN111147116 A CN 111147116A CN 201911224382 A CN201911224382 A CN 201911224382A CN 111147116 A CN111147116 A CN 111147116A
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paths
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CN111147116B (en
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付俭伟
马春香
武宏伟
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Beijing Wanji Technology Co Ltd
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0617—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal for beam forming
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
    • Y02D30/00—Reducing energy consumption in communication networks
    • Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks

Abstract

The invention provides a signal synthesis method and device, a storage medium and an electronic device, wherein the method comprises the following steps: for an array antenna with N channels, acquiring M channels of signals of M channels with normal working states in the N channels, wherein N and M are positive integers, and N is larger than or equal to M; calculating to obtain a constructed carrier signal according to the calculated first digital synthesis signal; respectively calculating the sampling delay and the phase delay of the M paths of signals and the constructed carrier signals; adjusting the M paths of signals according to the determined sampling delay and the determined phase delay to obtain adjusted M paths of adjustment signals; the technical scheme is adopted to solve the problems that in the related technology, the beam forming algorithm is high in operation complexity, sensitive in error, low in frequency utilization rate and the like.

Description

Signal synthesis method and device, storage medium, and electronic device
Technical Field
The present invention relates to the field of communications, and in particular, to a signal synthesis method and apparatus, a storage medium, and an electronic apparatus.
Background
The beam forming algorithm is that multi-channel signals are synthesized into a single-channel signal according to a certain method, and the single-channel signal is used for suppressing noise in the signals and improving the signal-to-noise ratio. Beamforming algorithms are central in the research of smart antennas. The beamforming algorithm may be classified into an adaptive algorithm based on direction estimation, a method based on a training signal or constructing a carrier signal, and a beamforming method based on a signal structure according to the object based on.
The self-adaptive beam forming algorithm based on the direction estimation has high operation complexity and is sensitive to errors, meanwhile, special requirements are placed on the structure of the antenna, and meanwhile, the calculation complexity is increased rapidly along with the increase of the number of the arrays; based on a beam forming algorithm for constructing carrier signals, the prior carrier and symbol recovery is needed for transmitting training signals, and the utilization rate of a frequency spectrum is reduced. The beam forming algorithm based on the signal structure has the problems of poor real-time performance and low convergence speed.
Aiming at the problems of high operation complexity, sensitive error, reduced frequency utilization rate and the like of a beam forming algorithm in the related technology, an effective technical scheme is not provided.
Disclosure of Invention
The embodiment of the invention provides a signal synthesis method and device, a storage medium and an electronic device, which are used for at least solving the problems of high operation complexity, sensitive error, reduced frequency utilization rate and the like of a beam forming algorithm in the related technology.
According to an embodiment of the present invention, there is provided a signal synthesis method including: for an array antenna with N channels, acquiring M channels of signals of M channels with normal working states in the N channels, wherein N and M are positive integers, and N is larger than or equal to M; calculating to obtain a constructed carrier signal according to the calculated first digital synthesis signal; respectively calculating the sampling delay and the phase delay of the M paths of signals and the constructed carrier signals; adjusting the M paths of signals according to the determined sampling delay and the determined phase delay to obtain adjusted M paths of adjustment signals; and synthesizing the M paths of adjusting signals to obtain a first digital synthesis signal.
In this embodiment of the present invention, before synthesizing the M channels of adjustment signals to obtain a digital synthesis signal, the method further includes:
respectively determining the convolution sizes of the M paths of signals and the constructed carrier signals through the following formulas:
Figure BDA0002301489210000021
wherein, Cr(k) Representing the real part, S, of the constituent carrier signalrAnd (d + k) is a real part of the M paths of signals, d is all sampling delays, the value range is 0 to R, R is L/(cT), wherein L is the maximum distance between every two array elements of the array antenna, c is the light speed, T is the sampling period of a chip corresponding to the array antenna, and the corresponding signal delay d when the convolution size is maximum is taken as the sampling delay of the current channel signal.
In the embodiment of the invention, the phase delay of the M paths of signals and the constructed carrier signals is calculated by the following formula:
Figure BDA0002301489210000022
wherein, N is the number of sampling points, S (k + i) is a complex field expression of the M-channel signals, C (k + i) is the constructed carrier signal, and the constructed carrier signal is a signal of which the input signal of the array antenna is not subjected to amplitude modulation.
In an embodiment of the invention, the first digital composite signal is determined by the following formula:
Figure BDA0002301489210000023
wherein d isi' is the sampling delay, sigma, of the ith signali(k) The phase delay of the ith signal.
In this embodiment of the present invention, before calculating the sampling delay and the phase delay of the M-channel signal and the configured carrier signal respectively, the method further includes: the real part signal and the imaginary part signal C of the carrier signal are calculated by the following formular(k) And Ci(k):
Figure BDA0002301489210000031
Wherein ε (k) is determined by the following equation:
Figure BDA0002301489210000032
determining, wherein δ: (k) To construct an average value of the phase difference between the carrier phase difference epsilon (k) and the first digital composite signal
Figure BDA0002301489210000033
The difference of (a).
In the embodiment of the present invention, the above is determined by the following formula
Figure BDA0002301489210000034
Figure BDA0002301489210000035
Wherein the phase difference △ (k) of any adjacent sample point is determined by the following equation:
Figure BDA0002301489210000036
wherein the instantaneous phase samples of the first digital synthesis signal S' (k) are determined by the following formula
Figure BDA0002301489210000037
Figure BDA0002301489210000038
In the embodiment of the invention, the phase compensation delta (k) is calculated and adjusted in real time by calculating the correlation coefficient of the constructed carrier signal and the digital synthesis signal;
the correlation coefficient is described by the following formula:
Figure BDA0002301489210000039
in the embodiment of the present invention, acquiring M channels of signals with normal working states from N channels of signals with N channels includes: respectively acquiring the following information of the N channels of signals of the N channels: a real-time mean of the signal, a real-time energy spectrum of the signal, and a real-time correlation coefficient of the signal, wherein the real-time correlation coefficient is determined by the following equation:
Figure BDA00023014892100000310
wherein, c (k) represents a currently constructed carrier signal, s (k) represents an expression of each channel signal in a complex domain, and p(s) represents a real-time energy spectrum of the current channel signal; m paths of signals selected from the N paths of signals meet the following conditions: the real-time mean value of the M paths of signals meets a first preset condition, the real-time energy spectrum of the M paths of signals meets a second preset condition, and the real-time correlation coefficient of the M paths of signals meets a third preset condition.
According to another embodiment of the present invention, there is also provided a signal synthesizing apparatus including: the acquisition module is used for acquiring M paths of signals of M channels with normal working states in the N channels for the array antenna with the N channels, wherein N and M are positive integers, and N is larger than or equal to M; the determining module is used for calculating to obtain a constructed carrier signal according to the calculated first digital synthesis signal; respectively calculating the sampling delay and the phase delay of the M paths of signals and the constructed carrier signals; adjusting the M paths of signals according to the determined sampling delay and the determined phase delay to obtain adjusted M paths of adjustment signals; and synthesizing the M paths of adjusting signals to obtain a first digital synthesis signal.
According to another embodiment of the present invention, there is also provided a storage medium having a computer program stored therein, wherein the computer program is arranged to perform the signal synthesis method of any one of the above when executed.
According to another embodiment of the present invention, there is also provided an electronic device including a memory in which a computer program is stored and a processor configured to execute the computer program to perform the method of any one of the above signal synthesis methods.
According to the invention, M paths of signals of M channels with normal working states in the N channels are obtained for the array antenna with the N channels, wherein N and M are positive integers, and N is larger than or equal to M; calculating to obtain a constructed carrier signal according to the calculated first digital synthesis signal; respectively calculating the sampling delay and the phase delay of the M paths of signals and the constructed carrier signals; adjusting the M paths of signals according to the determined sampling delay and the determined phase delay to obtain adjusted M paths of adjustment signals; the technical scheme is adopted, the beam forming algorithm has the problems of high operation complexity, sensitive error, reduced frequency utilization rate and the like, and further provides a signal synthesis implementation scheme with low complexity and high accuracy.
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The accompanying drawings, which are included to provide a further understanding of the invention and are incorporated in and constitute a part of this application, illustrate embodiment(s) of the invention and together with the description serve to explain the invention without limiting the invention. In the drawings:
fig. 1 is a block diagram of a hardware configuration of a computer terminal of a signal synthesis method according to an embodiment of the present invention;
FIG. 2 is a flow diagram of a signal synthesis method according to an embodiment of the invention;
FIG. 3 is an alternative signal compensation scheme of an embodiment of the present invention;
fig. 4 is a block diagram of a signal synthesizing apparatus according to an embodiment of the present invention;
FIG. 5 is an alternative 4-channel raw signal input schematic of an embodiment of the present invention;
FIG. 6 is a parameter diagram of an alternative raw signal according to an embodiment of the present invention;
FIG. 7 is a schematic illustration of an alternative phase delay of an embodiment of the present invention;
FIG. 8 is a schematic diagram of an alternative adaptive phase compensation adjustment process according to an embodiment of the present invention;
fig. 9 is a schematic structural diagram of an alternative apparatus for adaptive beamforming algorithm according to an embodiment of the present invention.
Detailed Description
The invention will be described in detail hereinafter with reference to the accompanying drawings in conjunction with embodiments. It should be noted that the embodiments and features of the embodiments in the present application may be combined with each other without conflict.
It should be noted that the terms "first," "second," and the like in the description and claims of the present invention and in the drawings described above are used for distinguishing between similar elements and not necessarily for describing a particular sequential or chronological order. It should be understood that the data so used may be interchanged under appropriate circumstances such that embodiments of the application described herein may be used. Furthermore, the terms "comprises," "comprising," and "having," and any variations thereof, are intended to cover a non-exclusive inclusion, such that a process, method, system, article, or apparatus that comprises a list of steps or elements is not necessarily limited to those steps or elements expressly listed, but may include other steps or elements not expressly listed or inherent to such process, method, article, or apparatus.
The method provided by the embodiment of the application can be executed in a computer terminal or a similar operation device. Taking the example of the present invention running on a computer terminal, fig. 1 is a block diagram of a hardware structure of a computer terminal of a signal synthesis method according to an embodiment of the present invention. As shown in fig. 1, the computer terminal 10 may include one or more (only one shown in fig. 1) processors 102 (the processor 102 may include, but is not limited to, a processing device such as a microprocessor MCU or a programmable logic device FPGA) and a memory 104 for storing data, and optionally, a transmission device 106 for communication functions and an input-output device 108. It will be understood by those skilled in the art that the structure shown in fig. 1 is only an illustration and is not intended to limit the structure of the computer terminal. For example, the computer terminal 10 may also include more or fewer components than shown in FIG. 1, or have a different configuration with equivalent functionality to that shown in FIG. 1 or with more functionality than that shown in FIG. 1.
The memory 104 may be used to store computer programs, for example, software programs and modules of application software, such as computer programs corresponding to the signal synthesis method in the embodiment of the present invention, and the processor 102 executes various functional applications and data processing by running the computer programs stored in the memory 104, so as to implement the above-mentioned method. The memory 104 may include high speed random access memory, and may also include non-volatile memory, such as one or more magnetic storage devices, flash memory, or other non-volatile solid-state memory. In some examples, the memory 104 may further include memory located remotely from the processor 102, which may be connected to the computer terminal 10 via a network. Examples of such networks include, but are not limited to, the internet, intranets, local area networks, mobile communication networks, and combinations thereof.
The transmission device 106 is used for receiving or transmitting data via a network. Specific examples of the network described above may include a wireless network provided by a communication provider of the computer terminal 10. In one example, the transmission device 106 includes a Network adapter (NIC), which can be connected to other Network devices through a base station so as to communicate with the internet. In one example, the transmission device 106 may be a Radio Frequency (RF) module, which is used for communicating with the internet in a wireless manner.
In the present embodiment, a signal synthesis method operating on the computer terminal is provided, and fig. 2 is a flowchart of the signal synthesis method according to the embodiment of the present invention, as shown in fig. 2, the flowchart includes the following steps:
step S202, for an array antenna with N channels, obtaining M channels of signals of M channels with normal working states in the N channels, wherein N and M are positive integers, and N is larger than or equal to M;
step S204, calculating to obtain a constructed carrier signal according to the calculated first digital synthesis signal; respectively calculating the sampling delay and the phase delay of the M paths of signals and the constructed carrier signals;
step S206, the M paths of signals are adjusted according to the determined sampling delay and the determined phase delay, and M paths of adjusted signals are obtained;
and step S208, synthesizing the M paths of adjusting signals to obtain a first digital synthesis signal.
According to the invention, M paths of signals of M channels with normal working states in the N channels are obtained for the array antenna with the N channels, wherein N and M are positive integers, and N is larger than or equal to M; calculating to obtain a constructed carrier signal according to the calculated first digital synthesis signal; respectively calculating the sampling delay and the phase delay of the M paths of signals and the constructed carrier signals; adjusting the M paths of signals according to the determined sampling delay and the determined phase delay to obtain adjusted M paths of adjustment signals; the technical scheme is adopted, the beam forming algorithm has the problems of high operation complexity, sensitive error, reduced frequency utilization rate and the like, and further provides a signal synthesis implementation scheme with low complexity and high accuracy.
In this embodiment of the present invention, before synthesizing the M channels of adjustment signals to obtain a digital synthesis signal, the method further includes:
respectively determining the convolution sizes of the M paths of signals and the constructed carrier signals through the following formulas:
Figure BDA0002301489210000071
wherein, Cr(k) Representing the real part, S, of the constituent carrier signalrAnd (d + k) is a real part of the M paths of signals, d is all sampling delays, the value range is 0 to R, R is L/(cT), wherein L is the maximum distance between every two array elements of the array antenna, c is the light speed, T is the sampling period of a chip corresponding to the array antenna, and the corresponding signal delay d when the convolution size is maximum is taken as the sampling delay of the current channel signal.
In the process of calculating the convolution size, from the perspective of signal processing, when the array antenna has a large scale and a high sampling frequency rate, and the intermediate frequency signal has a high frequency, signals acquired by different array elements have delay in phase and have sampling delay of a plurality of periods.
In the embodiment of the invention, the phase delay of the M paths of signals and the constructed carrier signals is calculated by the following formula:
Figure BDA0002301489210000081
wherein, N is the number of sampling points, S (k + i) is a complex field expression of the M-channel signals, C (k + i) is the constructed carrier signal, and the constructed carrier signal is a signal of which the input signal of the array antenna is not subjected to amplitude modulation.
In an embodiment of the invention, the first digital composite signal is determined by the following formula:
Figure BDA0002301489210000082
wherein d isi' is the sampling delay, sigma, of the ith signali(k) The phase delay of the ith signal.
In this embodiment of the present invention, before calculating the sampling delay and the phase delay of the M-channel signal and the configured carrier signal respectively, the method further includes: the real part signal and the imaginary part signal C of the carrier signal are calculated by the following formular(k) And Ci(k):
Figure BDA0002301489210000083
Wherein ε (k) is determined by the following equation:
Figure BDA0002301489210000084
determining, wherein delta (k) is the mean value of the phase difference between the construction carrier phase difference epsilon (k) and the first digital composite signal phase difference
Figure BDA0002301489210000091
The difference of (a).
In the embodiment of the present invention, the determination is made by the following formulaThe above-mentioned
Figure BDA0002301489210000092
Figure BDA0002301489210000093
Wherein the phase difference △ (k) of any adjacent sample point is determined by the following equation:
Figure BDA0002301489210000094
wherein the instantaneous phase samples of the first digital synthesis signal S' (k) are determined by the following formula
Figure BDA0002301489210000095
Figure BDA0002301489210000096
In the embodiment of the invention, the phase compensation delta (k) is calculated and adjusted in real time by calculating the correlation coefficient of the constructed carrier signal and the digital synthesis signal;
the correlation coefficient is described by the following formula:
Figure BDA0002301489210000097
wherein, the correlation coefficient R(s) is maximized by automatically adjusting the magnitude of the phase compensation δ (k). Without loss of generality, given the step length of adjustment of phase compensation is τ, correlation coefficients r(s) under the conditions of phase compensation δ (k), δ (k) - τ and δ (k) + τ are calculated, and the phase compensation with the largest correlation coefficient is taken as the current phase compensation δ (k +1) at the next time.
In the embodiment of the present invention, acquiring M channels of signals with normal working states from N channels of signals with N channels includes: respectively acquiring the following information of the N channels of signals of the N channels: a real-time mean of the signal, a real-time energy spectrum of the signal, and a real-time correlation coefficient of the signal, wherein the real-time correlation coefficient is determined by the following equation:
Figure BDA0002301489210000098
wherein, c (k) represents a currently constructed carrier signal, s (k) represents an expression of each channel signal in a complex domain, and p(s) represents a real-time energy spectrum of the current channel signal; m paths of signals selected from the N paths of signals meet the following conditions: the real-time mean value of the M paths of signals meets a first preset condition, the real-time energy spectrum of the M paths of signals meets a second preset condition, and the real-time correlation coefficient of the M paths of signals meets a third preset condition.
The technical solution of the signal synthesis flow is explained below with reference to an example, but the technical solution of the embodiment of the present invention is not limited thereto.
An alternative example of the embodiments of the present invention provides a beamforming algorithm based on constructing carrier signals, the method comprising the steps of: performing Hilbert transform on each channel signal (the result obtained after the Hilbert transform can be understood as a linear time-invariant system of the channel signal) to obtain the expression of each channel signal in a complex domain; calculating a real-time mean value, a real-time energy spectrum and a real-time correlation coefficient of each channel signal, judging the working state of each channel of digital signals according to preset judgment parameters, and giving the working state of each channel at present; the phase difference between each of the signals determined to be normal and the structural carrier signal is calculated, the phase of each of the signals is corrected according to the phase difference to obtain digital signals with the same phase, and the obtained signals are digitally combined to obtain a final combined digital signal. Calculating the phase of the digital signal at each sampling point by using the finally synthesized digital signal, and simultaneously calculating the phase difference between the current sampling point and the last sampling point; in order to weaken the influence of amplitude variation and noise on the obtained phase difference, calculating the average value of the phase difference of a plurality of sampling points, thereby obtaining the average instantaneous phase difference; furthermore, the average instantaneous phase is added with a phase compensation to obtain the corrected average phase difference, so that the digital waveform of the structural carrier signal can be directly calculated. By calculating the correlation coefficient between the constructed carrier signal and the synthesized signal, the adaptive algorithm is used to realize the real-time adjustment of the phase compensation, and the difference between the constructed carrier signal and the actual carrier signal is reduced, as shown in fig. 3.
It should be noted that, for a narrowband signal, the signal acquired by any one channel may be represented as:
Sr(n)＝s(n)cos(wn)；
where s (n) denotes the amplitude modulation of the signal and w denotes the angular frequency of the intermediate frequency signal of the signal. After the signal is subjected to Hilbert transform, the signal Sr(n) is delayed in phase by pi/2, resulting in the following signals:
Si(n)＝s(n)sin(wn)；
according to the euler theorem, the expression of real signals in the complex domain can be obtained:
S(n)＝s(n)cos(wn)+is(n)sin(wn)＝s(n)eiwn。
further, detecting the working state of each channel in real time based on the digital signals acquired by each channel to judge whether the working state of each channel is normal or not; the channel detection is based on the following three indexes, namely the real-time mean value of each channel signal, the real-time energy spectrum of the channel signal and the real-time correlation coefficient of the channel signal, wherein the real-time mean value of the waveform of the digital signal acquired by the channel which normally works is near 0, and if the calculated signal mean value exceeds a certain maximum zero drift threshold value
Figure BDA0002301489210000116
The method shows that the path of signal has larger direct current component and works abnormally, wherein the mean value calculation formula of the channel signal is as follows:
Figure BDA0002301489210000111
wherein, N represents the number of sampling points for calculating the average value of the channel signal, if the real-time average value obtained by calculation E(s) is smaller than a given threshold value
Figure BDA0002301489210000112
The current channel is indicated to work normally, otherwise, the current channel is indicated to work abnormally.
The waveform energy spectrum of the digital signal collected by the channel which works normally is larger than a given minimum energy spectrum threshold value
Figure BDA0002301489210000115
Indicating that there is currently input of signal energy. If the calculated signal energy spectrum does not meet the requirement of the threshold, the current channel is indicated to be abnormal in work, wherein the calculation formula of the real-time energy spectrum of the channel signal is as follows:
Figure BDA0002301489210000113
the real-time energy spectrum of the channel signal is determined by the signal intensity of the signal source, the intensity of the signals reaching each channel is different, and the calculated signal energy spectrum is different, so that a fixed energy spectrum threshold value is difficult to directly give out to check the working state of the current channel. The energy input of the signal source received by each channel of the array antenna is approximately the same, so that the maximum real-time energy spectrum and a factor F of each path of signal obtained by current calculation can be selecteds(0<Fs<1) As threshold value of the energy spectrum detected by the current channel, i.e.
Figure BDA0002301489210000114
Wherein, P1(s),...,Pm(s) represents the real-time energy spectrum of the signals from channel 1 to channel m, if the real-time energy spectrum calculated by the current channel is less than the threshold value
Figure BDA0002301489210000123
The current channel is indicated to work normally, otherwise, the current channel works abnormally.
The constructed carrier signal is an input signal without amplitude modulation, obviously, the digital signal collected by the channel which normally works and the constructed carrier signal are highly correlated, so whether the waveform of the input signal of the current channel is normal can be judged by calculating the correlation coefficient between the digital signal and the constructed carrier signal of each channel, wherein the real-time correlation coefficient between the channel signal and the constructed carrier signal can be calculated by the following formula:
Figure BDA0002301489210000121
wherein, c (k) represents a constructed carrier signal obtained by current construction, s (k) represents a representation of each channel signal in a complex number domain, and p(s) represents a real-time energy spectrum of the current signal. The larger the value of the real-time correlation coefficient of the channel signal is calculated, the better the quality of the waveform of the signal of the current channel is. Threshold value given a certain real-time correlation coefficient
Figure BDA0002301489210000122
If the calculated real-time correlation coefficient of the current channel signal is larger than the threshold value, the current channel works normally, otherwise, the current channel works normally.
Further, according to the given calculation method, whether the real-time mean value, the real-time energy spectrum and the real-time correlation coefficient of the current channel meet given judgment conditions or not is calculated respectively, if three indexes calculated according to the digital signal of the current channel all meet threshold requirements, the working state of the current channel is normal, and otherwise, the working state of the current channel is abnormal.
Furthermore, a fixed delay K sampling points exist between the generated reference waveform and the input signal, and the waveform obtained by Hilbert transform is delayed by K sampling points; for an array antenna with a large scale, because the spatial distance between channels is large, the waveform delay acquired by each channel signal may differ by several digital signal fundamental frequency periods, the maximum distance between every two array elements of the array antenna is L, and the number of sampling points with the maximum relative delay between two channels can be calculated as M ═ L/(cT), where c is the speed of light and T is the sampling period of an AD chip. Respectively calculating the real part of an input waveform and the first M convolutions of a constructed carrier signal, wherein the input signal is delayed by d sampling points, and the corresponding convolution calculation formula is as follows:
Figure BDA0002301489210000131
wherein, Cr(k) Representing a real part for constructing a carrier signal, respectively calculating the convolution size of d between 0 and M under all possible conditions, simultaneously finding out the corresponding signal delay d 'when the convolution is maximum, and then delaying the digital signals of the real part and the imaginary part of the current channel signal by d' sampling points to obtain delayed signals; the calculation formula of the phase delay of each channel signal after delay and the construction carrier signal is as follows:
Figure BDA0002301489210000132
wherein c (k) represents a structure carrier signal in the complex domain.
Further, in practical applications, since the source is far away from the array antenna, the phase delay of the digital signal of each channel relative to the structure carrier signal changes slowly in a period of time, so that the phase calculated at the last time can be used to estimate the phase difference between the current channel signal and the structure carrier signal. The signal in the complex domain of each channel is multiplied by the corresponding channel phase delay σ (k) to obtain digital signals with the same phase. According to the result of channel detection, the values of the sampling points at the corresponding moments of the digital signals with the consistent phases of all the normal working channels are algebraically added to obtain a single-path digital signal after beam forming, the signal is used as a signal finally generated by the beam forming system and is provided for a subsequent module to use, and then the digital signal of beam forming is as follows:
Figure BDA0002301489210000133
further, the phase of each sampling point of the digital composite signal is calculated by the following formula:
Figure BDA0002301489210000134
then the phase difference of two adjacent sampling points is calculated,
Figure BDA0002301489210000135
in order to reduce the influence of single sampling noise on the calculation of the phase angle, the average value of the phase difference of each N sampling points before and after the current sampling point is used as the average phase difference of the current sampling point
Figure BDA0002301489210000141
Then there is
Figure BDA0002301489210000142
Further, the average phase difference calculated by the method is caused by signal amplitude modulation
Figure BDA0002301489210000143
The actual phase difference from the baseband is not equal, the actual phase difference and the average phase difference of the carrier signal
Figure BDA0002301489210000144
The difference between them is denoted as δ (k), then the formula is satisfied:
Figure BDA0002301489210000145
wherein ε (k) represents the actual phase difference of the carrier signals; the constructed carrier signal can then be expressed as:
Figure BDA0002301489210000146
wherein, Cr(k) And Ci(k) Representing the real and imaginary parts of the constructed carrier signal, respectively.
Furthermore, a correlation coefficient is calculated according to the carrier signal and the signal after beam forming, and the value of the correlation coefficient is improved by automatically adjusting the magnitude of the phase compensation delta (k), thereby realizing the effect of self-adaptive phase compensation. The step length of adjustment of phase compensation is recorded as tau, correlation coefficients of the obtained structure carrier signal and the synthesized signal under the sizes of the phase compensation as delta (k) and delta (k) -tau and delta (k) + tau are respectively calculated and are respectively represented as R (delta (k)), R (delta (k) -tau) and R (delta (k) + tau), if the value of R (delta (k)) is maximum, the phase compensation keeps delta (k) unchanged, if the value of R (delta (k) -tau) is maximum, the phase compensation is adjusted as delta (k) -tau, and if the value of R (delta (k) + tau) is maximum, the phase compensation is adjusted as delta (k) + tau.
The technical scheme of the embodiment of the invention provides a beam forming algorithm based on a constructed carrier signal, which constructs the carrier signal of an information source by estimating the instantaneous phase difference of the signal in real time; the estimated phase difference of the signals is corrected in real time by calculating the correlation coefficient of the constructed carrier signals and the synthesized signals, the calculation accuracy of the constructed carrier signals is guaranteed, and the algorithm does not need to assume the layout mode of the array antenna in advance, so the algorithm can be widely applied to array antennas in various forms. In addition, the technical scheme of the invention can calculate the real-time mean value, the real-time energy spectrum and the real-time correlation coefficient of the input signals in the process of beam forming, detect the working state of each path of digital signals according to the preset judgment parameters, and automatically shield the signals of channels with abnormal working, so that the algorithm has certain robustness, and the quality of the final synthesized signals is further ensured.
Through the above description of the embodiments, those skilled in the art can clearly understand that the method according to the above embodiments can be implemented by software plus a necessary general hardware platform, and certainly can also be implemented by hardware, but the former is a better implementation mode in many cases. Based on such understanding, the technical solutions of the present invention may be embodied in the form of a software product, which is stored in a storage medium (e.g., ROM/RAM, magnetic disk, optical disk) and includes instructions for enabling a terminal device (e.g., a mobile phone, a computer, a server, or a network device) to execute the method according to the embodiments of the present invention.
In this embodiment, a signal synthesis apparatus is further provided, and the system is used to implement the foregoing embodiments and preferred embodiments, and the description already made is omitted. As used below, the term "module" may be a combination of software and/or hardware that implements a predetermined function. Although the means described in the embodiments below are preferably implemented in software, an implementation in hardware, or a combination of software and hardware is also possible and contemplated.
Fig. 4 is a block diagram of a signal synthesizing apparatus according to an embodiment of the present invention, as shown in fig. 4, the apparatus including:
the acquiring module 40 is configured to acquire, for an array antenna having N channels, M channels of signals of M channels in a normal operating state in the N channels, where N and M are positive integers, and N is greater than or equal to M;
a determining module 42, configured to calculate a configuration carrier signal according to the calculated first digital composite signal; respectively calculating the sampling delay and the phase delay of the M paths of signals and the constructed carrier signals; adjusting the M paths of signals according to the determined sampling delay and the determined phase delay to obtain adjusted M paths of adjustment signals; and synthesizing the M paths of adjusting signals to obtain a first digital synthesis signal.
According to the invention, M paths of signals of M channels with normal working states in the N channels are obtained for the array antenna with the N channels, wherein N and M are positive integers, and N is larger than or equal to M; calculating to obtain a constructed carrier signal according to the calculated first digital synthesis signal; respectively calculating the sampling delay and the phase delay of the M paths of signals and the constructed carrier signals; adjusting the M paths of signals according to the determined sampling delay and the determined phase delay to obtain adjusted M paths of adjustment signals; the technical scheme is adopted, the beam forming algorithm has the problems of high operation complexity, sensitive error, reduced frequency utilization rate and the like, and further provides a signal synthesis implementation scheme with low complexity and high accuracy.
In this embodiment of the present invention, the determining module 42 is further configured to determine the convolution magnitudes of the M channels of signals and the constructed carrier signal respectively according to the following formulas:
Figure BDA0002301489210000163
wherein, Cr(k) Representing the real part, S, of the constituent carrier signalrAnd (d + k) is a real part of the M paths of signals, d is all sampling delays, the value range is 0 to R, R is L/(cT), wherein L is the maximum distance between every two array elements of the array antenna, c is the light speed, T is the sampling period of a chip corresponding to the array antenna, and the corresponding signal delay d when the convolution size is maximum is taken as the sampling delay of the current channel signal.
In this embodiment of the present invention, the determining module 42 is further configured to calculate the phase delay between the M-channel signal and the configured carrier signal by the following formula:
Figure BDA0002301489210000161
wherein, N is the number of sampling points, S (k + i) is a complex field expression of the M-channel signals, C (k + i) is the constructed carrier signal, and the constructed carrier signal is a signal of which the input signal of the array antenna is not subjected to amplitude modulation.
In an embodiment of the present invention, the determining module 42 is further configured to determine the first digital composite signal by the following formula:
Figure BDA0002301489210000162
wherein d isi' is the sampling delay, sigma, of the ith signali(k) The phase delay of the ith signal.
In the embodiment of the present invention, the determining module 42 is further configured to calculate the real part signal and the imaginary part signal C of the carrier signal by the following formular(k) And Ci(k):
Figure BDA0002301489210000171
Wherein ε (k) is determined by the following equation:
Figure BDA0002301489210000172
determining, wherein delta (k) is the mean value of the phase difference between the construction carrier phase difference epsilon (k) and the first digital composite signal phase difference
Figure BDA0002301489210000173
The difference of (a).
In the embodiment of the present invention, the determining module 42 is further configured to determine the above-mentioned value through the following formula
Figure BDA0002301489210000174
Figure BDA0002301489210000175
Wherein the phase difference △ (k) of any adjacent sample point is determined by the following equation:
Figure BDA0002301489210000176
wherein the instantaneous phase samples of the first digital synthesis signal S' (k) are determined by the following formula
Figure BDA0002301489210000177
Figure BDA0002301489210000178
In the embodiment of the present invention, the determining module 42 is further configured to calculate and adjust the phase compensation δ (k) in real time by calculating a correlation coefficient between the constructed carrier signal and the digital composite signal;
a determining module 42, further configured to determine the correlation coefficient by the following formula:
Figure BDA0002301489210000179
wherein the magnitude of delta (k) is compensated by automatically adjusting the phaseWhen the correlation coefficient R(s) is small, the correlation coefficient R(s) has a maximum value. Without loss of generality, given the step length of adjustment of phase compensation is τ, correlation coefficients r(s) under the conditions of phase compensation δ (k), δ (k) - τ and δ (k) + τ are calculated, and the phase compensation with the largest correlation coefficient is taken as the current phase compensation δ (k +1) at the next time.
In this embodiment of the present invention, the obtaining module 40 is further configured to obtain the following information of the N channels of signals of the N channels, respectively: a real-time mean of the signal, a real-time energy spectrum of the signal, and a real-time correlation coefficient of the signal, wherein the real-time correlation coefficient is determined by the following equation:
Figure BDA0002301489210000181
wherein, c (k) represents a currently constructed carrier signal, s (k) represents an expression of each channel signal in a complex domain, and p(s) represents a real-time energy spectrum of the current channel signal; m paths of signals selected from the N paths of signals meet the following conditions: the real-time mean value of the M paths of signals meets a first preset condition, the real-time energy spectrum of the M paths of signals meets a second preset condition, and the real-time correlation coefficient of the M paths of signals meets a third preset condition.
It should be noted that, the above modules may be implemented by software or hardware, and for the latter, the following may be implemented, but not limited to: the modules are all positioned in the same processor; alternatively, the modules are respectively located in different processors in any combination.
The following describes the technical solutions of the above signal synthesis methods with reference to alternative embodiments, but the embodiments and exemplary technical solutions of the present invention are not limited thereto.
In the alternative embodiment of the present invention, the maximum distance between any two array elements is 50mm, the sampling frequency of the AD chip is 50MHz, and the frequency of the intermediate frequency signal is 10MHz, for example, "the number of channels of the array antenna is 4 (as shown in fig. 5, the original signal input by 4 channels), and the maximum distance between any two array elements is 50 mm.
Optionally, for convenience of description, directly acquiring a signal and marking the signal as an I-path signal; firstly, performing Hilbert transform on each acquired channel signal to obtain a Q channel signal of which the current signal delays by 90 degrees; in order to implement real-time hilbert transform of a digital signal, a Finite long single-bit impulse response (FIR) filter with a certain order may be selected to implement hilbert transform of a channel signal, in this embodiment, the order of the FIR filter is 10, and under the condition of ensuring the calculation accuracy, the use of calculation resources is reduced, and a calculation formula for implementing hilbert transform using the FIR filter is as follows:
Figure BDA0002301489210000191
wherein, N is the order of the hilbert transform FIR filter, and then the I-channel digital signal and the Q-channel digital signal of each channel jointly constitute a complex signal of a 4-channel signal.
And then calculating a signal calculation real-time mean value, a real-time energy spectrum and a real-time correlation coefficient of each channel to judge the working state of each channel at present. Firstly, calculating a real-time mean value of signals according to the I-path signals of each channel; the smaller the number of sampling points for calculating the real-time mean value is, the more the calculation result can reflect the working state of the current channel in time; on the contrary, the more the number of sampling points is, the more stable and reliable the calculation result is. In this embodiment, the number of sampling points for calculating the real-time average value is 521, and then the calculation formula of the real-time average value of each channel is:
Figure BDA0002301489210000192
it can be seen that E (k +1) ═ E (k) +(S) is satisfiedr(k+257)-Sr(k-256))/256, and the iterative calculation of the real-time mean value of the channel signal can be conveniently realized by the formula. In this alternative embodiment, the threshold value of the real-time mean value of the channel signal is not taken to be 100, if the calculation result is E (k)>100, the channel is abnormal, otherwise, the channel is abnormalThe channel works normally.
The modulation amplitude s (k) of each sample of the channel signal is calculated by the formula:
Figure BDA0002301489210000193
similarly, if the number of sampling points for calculating the real-time energy spectrum is 512, the real-time energy spectrum of each channel is calculated by the following formula:
Figure BDA0002301489210000194
it can be seen that, when P (k +1) ═ P (k)) + (s (k +257) -s (k-256))/256 is satisfied, iterative computation of the real-time power spectrum of the channel signal can be conveniently achieved by the above formula. Calculating the maximum real-time power spectrum P of all channelsmax(k)＝max{P1(k),P2(k),P3(k),P4(k) In which P is1(k),P2(k),P3(k) And P4(k) The real-time power spectra of channel 1, channel 2, channel 3 and channel 4 are shown, respectively. In this embodiment, it is not taken that the threshold coefficient of the energy spectrum is 0.5, if the real-time power spectrum P (k) is obtained by calculation<0.5Pmax(k) And indicating that the current channel works abnormally, otherwise indicating that the current channel works normally.
In order to calculate the real-time correlation coefficient of each channel signal, first, the real-time correlation between each channel signal and the constructed carrier signal is calculated, and similarly, the number of sampling points for calculating the real-time correlation is taken as 512, then the calculation formula of the real-time correlation of each channel is as follows:
Figure BDA0002301489210000201
wherein, C (k) represents that the structure carrier signal in the complex domain is obtained by calculation; it can be seen that the formula σ (k +1) ═ σ (k) - (S (k-256) C (k-256) + S (k +256) C (k +256))/256 is satisfied, and the iterative calculation of the real-time correlation of the channel signals can be very conveniently realized through the formula. The real-time correlation coefficient of the channel signal can be calculated by calculating the real-time correlation and the real-time power spectrum, and the calculation formula is as follows:
Figure BDA0002301489210000202
in the embodiment, the threshold value of the real-time correlation coefficient of the channel is not taken to be 0.5, and if the calculated real-time correlation coefficient R (k) is less than 0.5, the current channel is indicated to be abnormal in work; otherwise, the current channel is indicated to work normally.
Then, the working state of the current channel is judged according to the real-time mean value, the real-time energy spectrum and the real-time correlation coefficient of the channel signals obtained through calculation, if all three indexes obtained through calculation of the digital signals of the current channel meet the threshold requirement, the comprehensive judgment result of the working state of the current channel is normal, otherwise, the comprehensive judgment result of the working state of the current channel is abnormal, for example, the original signals, the real-time mean value, the real-time energy spectrum and the real-time correlation coefficient of the channel 1 are shown in fig. 6.
Then, the number of the sampling points of the maximum delay of any two channels obtained by calculating the distance between two array elements is 0, so that only the phase difference between the digital signals of any two channels is reflected in the intermediate frequency signal. The delay of the carrier signal and the input signal is constructed as an input delay taking a real-time average when calculating the average phase difference, and the number of sampling points taking the real-time average is 512 in this embodiment, then the input delay of the carrier signal and the channel signal is constructed as 256. Therefore, the expression of the complex field of each channel digital signal is delayed by 256 sampling points, and the calculation delay between the constructed carrier signal and the input signal is eliminated; in this embodiment, taking the sampling length for calculating the phase delay between each input signal and the structured carrier signal as 512, the equation for calculating the phase delay of the input signal is:
Figure BDA0002301489210000211
from the above formula, the phase delay of each channel signal can be calculated in this embodiment, for example, the phase delay of 4 channels is as shown in fig. 7.
The complex signal of the 4-channel signal obtained by the hilbert transform is multiplied by the corresponding phase delay, so that the phase of the input signal can be adjusted to be the same as that of the structural carrier signal, and further the input signal with the same phase can be obtained. In an alternative embodiment of the invention, it is assumed that the digital signals of all channels meet the threshold requirement, i.e. the operating state of all channels is normal. Then, after the phase adjustment of the digital signals of all channels, the values of the sampling points at the corresponding time are algebraically added to obtain a single-path complex signal after the beam forming, and the single-path complex signal is used as a signal finally generated by the beam forming system and is provided for a subsequent module for use.
Figure BDA0002301489210000212
Where S' (k) is a digital signal finally synthesized from the digital signals of 4 channels.
The phase of each sample can then be calculated from the combined digital signal
Figure BDA0002301489210000213
Then calculating the phase difference between two adjacent sampling points
Figure BDA0002301489210000214
Since the phase difference calculated from the adjacent sampling points is greatly influenced by noise, the average value of the phase difference calculated within a period of time is required to be the instantaneous average phase difference of the current sampling point, in this embodiment, the number of sampling points for calculating the average phase difference is 32, and then the average phase difference is calculated
Figure BDA0002301489210000215
The calculation formula of (2) is as follows:
Figure BDA0002301489210000216
due to amplitude modulation of the signalAverage phase difference calculated as described above
Figure BDA0002301489210000221
Is not equal to the actual phase difference e (k) of the carrier signal, and therefore there is a difference between the actual phase difference of the carrier signal and the average phase difference △ (k) denoted as δ (k), then the equation is satisfied:
Figure BDA0002301489210000222
likewise, the structured carrier signal obtained in this embodiment can be expressed as:
Figure BDA0002301489210000223
the smaller the difference between the constructed carrier signal and the actual carrier signal is, the larger the correlation coefficient between the constructed carrier signal and the input signal of each normal channel is, so that the signal after beam forming can be used for evaluating the deviation between the current constructed baseband and the actual carrier signal; by adjusting the value of the phase compensation delta (k), the constructed carrier signal and the beam-formed signal have higher correlation coefficient. In this embodiment, let the compensation at the current time be a, and the step size of the adjustment of the phase compensation be b, then the flow of the adaptive phase compensation adjustment algorithm is shown in fig. 8.
The method comprises the steps of respectively calculating correlation coefficients of a constructed carrier signal and a synthesized signal obtained under the condition that phase compensation is a, a-b and a + b, then calculating correlation coefficients of the constructed carrier signal and a beam synthesized signal obtained under the condition of different phase compensation, and then updating the current phase compensation a to a compensation phase corresponding to the maximum correlation coefficient, so that the constructed carrier signal is not too large in deviation with an actual carrier signal.
According to the above-described adaptive beamforming algorithm process, the apparatus for constructing an adaptive beamforming algorithm based on carrier signals includes a hilbert transform module for acquiring digital waveforms of all channels, a real-time channel operating state detection module, a real-time digital signal phase calculation and phase compensation module, and a carrier signal calculation and beamforming construction module, as shown in fig. 9.
Module M201: the system comprises a Hilbert transform module, a signal acquisition module and a signal processing module, wherein the Hilbert transform module is used for acquiring digital waveforms of channel signals under the condition of a certain sampling rate and converting real signals into complex signals through Hilbert transform;
the module M202: the channel working state real-time detection module judges the working state of each channel of digital signals according to preset judgment parameters by calculating the real-time mean value, the real-time energy spectrum and the real-time correlation coefficient of each channel of signals in real time and outputs the working state of each channel of channels;
module M203: the digital signal phase real-time calculation and phase compensation module obtains the phase of the synthesized digital signal at each sampling point through calculation to obtain the phase difference of two adjacent sampling points, and further calculates the average value of the phase differences of a plurality of sampling points to obtain the average instantaneous phase difference; the compensation phase is introduced to increase the correlation coefficient of the constructed carrier signal and the synthesized digital signal, so that the calculation precision of the phase difference of the sampling points of the carrier signal can be improved.
A module M204: and constructing a carrier signal calculation and beam forming module, and obtaining the phase difference of sampling points of the carrier signal by utilizing calculation to obtain the constructed carrier signal. The phase difference between each of the signals determined to be normal and the structural carrier signal is calculated, the phase of each of the signals is corrected according to the phase difference to obtain digital signals with the same phase, and the obtained signals are digitally combined to obtain a final combined digital signal.
In summary, compared with the prior art, the technical scheme of the embodiment of the invention has the following advantages and beneficial effects:
1. the adaptive beam forming algorithm based on the carrier signal provided by the optional embodiment of the invention uses an algorithm based on real-time mean, real-time energy spectrum and real-time correlation coefficient detection parameters to detect the working state of each channel in real time in the beam forming process; when a single channel is damaged and the quality of the digital signal of the channel is poor, the algorithm can automatically shield the digital signal of the channel, and the signal of the channel is prevented from participating in beam forming, so that the quality of the finally synthesized digital signal is ensured;
2. the invention provides an estimation algorithm of instantaneous phase difference of sampling points of digital signals based on Hilbert transform, which is used for correcting estimation deviation of the instantaneous phase difference caused by signal modulation by introducing a compensation phase, and then synthesizing the digital signals of reference carriers by using the phase difference of the compensated sampling points. The self-adaptive phase compensation adjustment algorithm ensures that the constructed carrier signal is highly related to the actual carrier signal, and the instantaneous frequency of the constructed carrier signal is correspondingly adjusted along with the frequency change of the input signal, so that the algorithm is ensured to have the processing capacity on the broadband signal;
3. the beam forming algorithm proposed in the alternative embodiment of the present invention does not need to assume the layout of the array antennas in advance, and thus can be widely used in different antenna array layouts.
4. The specific implementation content of the optional embodiment of the invention gives details of a possible implementation method and a possible implementation device of the algorithm, and the algorithm can realize the processing of the digital signals of the array antenna with different channel numbers by repeating the computing unit, and meanwhile, the consumed resources are in direct proportion to the channel number of the array, thereby being very beneficial to the implementation through hardware platforms such as FPGA.
Embodiments of the present invention also provide a storage medium having a computer program stored therein, wherein the computer program is arranged to perform the steps of any of the above method embodiments when executed.
Alternatively, in the present embodiment, the storage medium may be configured to store a computer program for executing the steps of:
s1, for an array antenna with N channels, obtaining M channels of signals of M channels with normal working states in the N channels, wherein N and M are positive integers, and N is larger than or equal to M;
s2, calculating a structure carrier signal according to the calculated first digital composite signal;
s3, respectively calculating the sampling delay and the phase delay of the M paths of signals and the constructed carrier signals; adjusting the M paths of signals according to the determined sampling delay and the determined phase delay to obtain adjusted M paths of adjustment signals;
and S4, synthesizing the M paths of adjusting signals to obtain a first digital synthesis signal.
Optionally, in this embodiment, the storage medium may include, but is not limited to: various media capable of storing computer programs, such as a usb disk, a Read-Only Memory (ROM), a Random Access Memory (RAM), a removable hard disk, a magnetic disk, or an optical disk.
Optionally, for specific examples in this embodiment, reference may be made to examples described in the above embodiments and optional implementation methods, and details of this embodiment are not described herein again.
Optionally, in this embodiment, the storage medium may include, but is not limited to: various media capable of storing program codes, such as a usb disk, a Read-Only Memory (ROM), a Random Access Memory (RAM), a removable hard disk, a magnetic disk, or an optical disk.
Optionally, for specific examples in this embodiment, reference may be made to examples described in the above embodiments and optional implementation methods, and details of this embodiment are not described herein again.
Embodiments of the present invention also provide an electronic device comprising a memory having a computer program stored therein and a processor arranged to run the computer program to perform the steps of any of the above method embodiments.
Optionally, the electronic apparatus may further include a transmission device and an input/output device, wherein the transmission device is connected to the processor, and the input/output device is connected to the processor.
Optionally, in this embodiment, the processor may be configured to execute the following steps by a computer program:
s1, for an array antenna with N channels, obtaining M channels of signals of M channels with normal working states in the N channels, wherein N and M are positive integers, and N is larger than or equal to M;
s2, calculating a structure carrier signal according to the calculated first digital composite signal;
s3, respectively calculating the sampling delay and the phase delay of the M paths of signals and the constructed carrier signals; adjusting the M paths of signals according to the determined sampling delay and the determined phase delay to obtain adjusted M paths of adjustment signals;
and S4, synthesizing the M paths of adjusting signals to obtain a first digital synthesis signal.
It will be apparent to those skilled in the art that the modules or steps of the present invention described above may be implemented by a general purpose computing device, they may be centralized on a single computing device or distributed across a network of multiple computing devices, and alternatively, they may be implemented by program code executable by a computing device, such that they may be stored in a storage device and executed by a computing device, and in some cases, the steps shown or described may be performed in an order different than that described herein, or they may be separately fabricated into individual integrated circuit modules, or multiple ones of them may be fabricated into a single integrated circuit module. Thus, the present invention is not limited to any specific combination of hardware and software.
The above description is only an alternative embodiment of the present invention and is not intended to limit the present invention, and various modifications and variations of the present invention may occur to those skilled in the art. Any modification, equivalent replacement, or improvement made within the principle of the present invention should be included in the protection scope of the present invention.

Claims (11)

1. A signal synthesis method, comprising:
for an array antenna with N channels, acquiring M channels of signals of M channels with normal working states in the N channels, wherein N and M are positive integers, and N is larger than or equal to M;
calculating to obtain a constructed carrier signal according to the calculated first digital synthesis signal;
respectively calculating the sampling delay and the phase delay of the M paths of signals and the constructed carrier signals; adjusting the M paths of signals according to the determined sampling delay and the determined phase delay to obtain adjusted M paths of adjustment signals;
and synthesizing the M paths of adjusting signals to obtain a first digital synthesis signal.
2. The method of claim 1, wherein before synthesizing the M channels of adjustment signals to obtain a digital synthesized signal, the method further comprises:
respectively determining the convolution sizes of the M paths of signals and the constructed carrier signals through the following formulas:
Figure FDA0002301489200000011
wherein, Cr(k) Representing the real part, S, of the constituent carrier signalrAnd (d + k) is a real part of the M paths of signals, d is all sampling delays, the value range is 0 to R, R is L/(cT), wherein L is the maximum distance between every two array elements of the array antenna, c is the light speed, T is the sampling period of a chip corresponding to the array antenna, and the corresponding signal delay d when the convolution size is maximum is taken as the sampling delay of the current channel signal.
3. The method of claim 1, wherein the phase delays of the M signals and the component carrier signal are calculated by the following equation:
Figure FDA0002301489200000012
wherein, N is the number of sampling points, S (k + i) is a complex field expression of the M-channel signal, and C (k + i) is the structure carrier signal.
4. The method of claim 3, wherein the first digital composite signal is determined by the formula:
Figure FDA0002301489200000021
wherein d isi' is the sampling delay, sigma, of the ith signali(k) The phase delay of the ith signal.
5. The method of claim 2, wherein before calculating the sampling delay and phase delay of the M-way signal and the constructed carrier signal, respectively, the method further comprises:
the real part signal and the imaginary part signal C of the construction carrier signal are calculated by the following formular(k) And Ci(k):
Figure FDA0002301489200000022
Wherein ε (k) is determined by the following equation:
Figure FDA0002301489200000023
determining, wherein delta (k) is the phase difference epsilon (k) of the construction carrier and the calculated average value of the phase difference of the first digital composite signal
Figure FDA0002301489200000024
The difference of (a).
6. The method of claim 5, wherein the determination is made by the following equation
Figure FDA0002301489200000025
Figure FDA0002301489200000026
The phase difference delta (k) of any adjacent sampling point is determined by the following formula:
Figure FDA0002301489200000031
wherein the instantaneous phase samples of the first digital synthesis signal S' (k) are determined by the following formula
Figure FDA0002301489200000032
Figure FDA0002301489200000033
7. The method of claim 5, wherein the phase compensation δ (k) is calculated and adjusted in real time by calculating correlation coefficients of the constructed carrier signal and the digitally synthesized signal;
the correlation coefficient is described by the following formula:
Figure FDA0002301489200000034
8. the method of claim 1, wherein obtaining M signals with normal operating status from the N signals of the N channels comprises:
respectively acquiring the following information of the N channels of signals of the N channels: a real-time mean of the signal, a real-time energy spectrum of the signal, and a real-time correlation coefficient of the signal, wherein the real-time correlation coefficient is determined by the following equation:
Figure FDA0002301489200000035
wherein, c (k) represents a currently constructed carrier signal, s (k) represents an expression of each channel signal in a complex domain, and p(s) represents a real-time energy spectrum of the current channel signal;
m paths of signals selected from the N paths of signals meet the following conditions: the real-time mean value of the M paths of signals meets a first preset condition, the real-time energy spectrum of the M paths of signals meets a second preset condition, and the real-time correlation coefficient of the M paths of signals meets a third preset condition.
9. A signal synthesis apparatus, comprising:
the acquisition module is used for acquiring M paths of signals of M channels with normal working states in the N channels for the array antenna with the N channels, wherein N and M are positive integers, and N is larger than or equal to M;
the determining module is used for calculating to obtain a constructed carrier signal according to the calculated first digital synthesis signal; respectively calculating the sampling delay and the phase delay of the M paths of signals and the constructed carrier signals; adjusting the M paths of signals according to the determined sampling delay and the determined phase delay to obtain adjusted M paths of adjustment signals; and synthesizing the M paths of adjusting signals to obtain a first digital synthesis signal.
10. A computer-readable storage medium, in which a computer program is stored, wherein the computer program is configured to carry out the method of any one of claims 1 to 8 when executed.
11. An electronic device comprising a memory and a processor, wherein the memory has stored therein a computer program, and wherein the processor is arranged to execute the computer program to perform the method of any of claims 1 to 8.
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