CN110691055A - Time-frequency offset joint estimation method in OQAM/OFDM - Google Patents

Time-frequency offset joint estimation method in OQAM/OFDM Download PDF

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CN110691055A
CN110691055A CN201911008743.2A CN201911008743A CN110691055A CN 110691055 A CN110691055 A CN 110691055A CN 201911008743 A CN201911008743 A CN 201911008743A CN 110691055 A CN110691055 A CN 110691055A
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time
sampling
matrix
frequency offset
oqam
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陈西宏
刘永进
刘赞
赵宇
谢泽东
张爽
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Air Force Engineering University of PLA
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2689—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation
    • H04L27/2695—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation with channel estimation, e.g. determination of delay spread, derivative or peak tracking
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/0014—Carrier regulation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2657—Carrier synchronisation
    • H04L27/2659—Coarse or integer frequency offset determination and synchronisation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2657—Carrier synchronisation
    • H04L27/266—Fine or fractional frequency offset determination and synchronisation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2668—Details of algorithms
    • H04L27/2673—Details of algorithms characterised by synchronisation parameters
    • H04L27/2675—Pilot or known symbols
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/0014—Carrier regulation
    • H04L2027/0024—Carrier regulation at the receiver end
    • H04L2027/0026—Correction of carrier offset

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Abstract

The invention provides a method for estimating joint time-frequency offset of an OQAM/OFDM system, which mainly comprises the following steps: carrying out segmentation processing on a received signal at a receiving end, and detecting a region with conjugate symmetry; calculating statistics and comparing with a threshold value; selecting a proper expression to estimate the time offset; and estimating the frequency offset by using the pilot frequency conjugate symmetry. The time frequency offset estimation method provided by the invention can reduce the complexity of the system, save frequency spectrum resources and realize better time frequency offset estimation performance.

Description

Time-frequency offset joint estimation method in OQAM/OFDM
Technical Field
The invention relates to communication and information processing technologies, in particular to an OFDM/OQAM time-frequency offset joint estimation method.
Background
Compared with the traditional OFDM technology, the OQAM/OFDM technology adopts a prototype filter with good time-frequency focusing performance, and can obtain good performance of resisting interference between symbols and carriers without adding cyclic prefixes. The characteristics enable the OQAM/OFDM technology to have higher spectrum utilization efficiency and become one of the main candidate technologies of future mobile communication.
The structural composition and the working process of the OQAM/OFDM system are shown in figure 1, and mainly comprise the following steps:
the transmitting terminal carries out OQAM modulation on transmission data bits, adds known pilot symbols or sequences at corresponding positions of data blocks for channel estimation, converts frequency domain symbols into time domain signals through an IFFT module, and finally superposes and transmits the time domain signals after being formed through a synthesis filter.
The processing process of the receiving end is opposite to that of the sending end, firstly, the received signal passes through an analysis filter bank, then a frequency domain symbol is obtained through FFT, channel information is extracted by using a pilot frequency symbol or sequence, the influence caused by time frequency offset is eliminated, and finally, original data are obtained through OQAM demodulation.
It can be seen that time-frequency offset estimation is a key step for implementing reliable transmission in an OQAM/OFDM system, but due to the real-number domain orthogonality of the prototype filter, the wireless fading channel causes the OQAM/OFDM symbols to be inevitably interfered by adjacent symbols and subcarriers in the imaginary number domain, and such interference makes the channel estimation method of the conventional OFDM system no longer applicable.
Currently, two methods, namely a pilot-based estimation method and a blind estimation method, are mainly used as time-frequency offset estimation methods for an OQAM/OFDM system.
The former distributes pilot symbols on time frequency grid points according to a certain rule according to the coherence bandwidth and coherence time of a channel, obtains time offset estimation and coarse frequency offset estimation by calculating the cross-correlation function of the pilot symbols at a receiving end, and then performs fine frequency offset estimation by using the pilot symbols to obtain complete time frequency offset estimation. The method can utilize pilot symbols, and the complexity of the system is low. However, when this method is used, the frequency offset estimation needs two steps to be implemented, and the estimation result is affected by the pilot frequency structure. At the same time, the presence of pilots reduces the spectral efficiency of the system. How to improve the spectrum efficiency is a problem that the pilot frequency-based time frequency offset estimation method needs to be studied deeply.
The latter estimates the time frequency offset according to the self characteristics of the transmission symbol, such as cyclic symmetry, conjugate symmetry, etc., so that the system does not need to add other symbols when transmitting data, and thus, the frequency spectrum can be fully utilized to achieve the purpose of improving the frequency spectrum efficiency. However, this method needs to derive and prove the characteristic function of the system, and uses the time offset and the frequency offset as parameters. The derivation of the system characteristic function proves that the derivation is complex, so that the blind time-frequency offset estimation complexity is high.
It can be seen that the previously proposed channel estimation methods all have corresponding disadvantages: the pilot frequency-based mode depends on a pilot frequency structure, the frequency spectrum efficiency is low, and the complexity of the blind estimation-based method is high. Therefore, a channel estimation method that is compatible with both spectrum resource consumption and complexity is required.
Disclosure of Invention
Aiming at the problems in the prior art, the invention provides a time-frequency offset joint estimation method in OQAM/OFDM, which comprises the following steps:
step 1: to NbSegmenting the transmission symbols; a. b and c represent the region a, respectively*、b*And c*Conjugate symmetric regions, c represents regions that are not used, x represents regions that do not have conjugate symmetry;
step 2: defining a first M-dimensional matrix
Figure BSA0000193000210000031
Is arranged at the m-th row and the n-th column
Figure BSA0000193000210000032
M is in the range of {0, 1, …, M-1}, N is in the range of {0, 1, …, N }, and N is the number of matrix columns, wherein R, I is the real part and imaginary part corner mark respectively; defining a second M-dimensional matrix
Figure BSA0000193000210000033
Row m and column n
Figure BSA0000193000210000034
Is expressed as
Figure BSA0000193000210000035
Where j is an imaginary unitM', n are
Figure BSA0000193000210000036
The number of rows and columns of
Figure BSA0000193000210000037
Wherein IDFT [. C]For inverse discrete Fourier transform, w is an M-dimensional vector, and the M term is wm＝jm；
And step 3: defining a third M-dimensional matrix
Figure BSA0000193000210000038
Row m and column nIs expressed as
Figure BSA00001930002100000310
Wherein n' is
Figure BSA00001930002100000311
The column coordinates of (a) are,
Figure BSA00001930002100000312
is the sampling interval, T is the symbol interval, g (-) is the prototype filter function; order to
Figure BSA00001930002100000313
Then
Figure BSA00001930002100000314
Can be expressed as
Figure BSA00001930002100000315
And 4, step 4: defining an M-dimensional matrix gnRow m and column n
Figure BSA00001930002100000316
Since the prototype filter is defined over the interval [0, KT) and K is an overlap factor, the matrix g is only if n ∈ {0, 1, …, K-1}, thennThe significance is given; at this time，The same can be obtained
Figure BSA00001930002100000318
I is an imaginary part corner mark;
and 5: according to the nature of the prototype filter g (m) and
Figure BSA00001930002100000319
is delayed by the sampling of
Figure BSA00001930002100000320
Figure BSA00001930002100000321
Wherein
Figure BSA00001930002100000322
Represents
Figure BSA00001930002100000323
The first segment of the sample is taken,
Figure BSA00001930002100000324
represents
Figure BSA00001930002100000325
The second section of sampling, and so on; gk，sAnd gk，iEach represents gkFirst one of (1)Sampling and second
Figure BSA00001930002100000327
Sampling;
Figure BSA00001930002100000328
and
Figure BSA00001930002100000329
respectively represent
Figure BSA00001930002100000330
First one of (1)Sampling and second
Figure BSA00001930002100000332
Sampling; when k is more than or equal to 5,
Figure BSA00001930002100000333
structure of and
Figure BSA00001930002100000334
the structure is the same;
step 6: receiving signal of system
Figure BSA0000193000210000041
A sequence regarded as a matrix
Figure BSA0000193000210000042
Detecting a region with conjugate symmetry of a received signal, namely whether positive and negative frequency amplitude components are symmetrical or not, and phase components of the positive and negative frequency amplitude components are just opposite;
and 7: computing statistics
Figure BSA0000193000210000043
Wherein θ is time offset; in order to eliminate the influence of noise on the time offset estimation, a threshold value ζ is set;
and 8: estimating the time offset:
Figure BSA0000193000210000044
wherein
Figure BSA0000193000210000045
And step 9: receiving a pilot signal matrix
Figure BSA0000193000210000046
Is a matrix formed by receiving pilot symbols according to a receiving time sequence; suppose thatFor two adjacent received pilot signal matrices, the system frequency offset is
The invention aims at an OQAM/OFDM system, combines a blind estimation method with pilot frequency, estimates time offset by using conjugate symmetry on the basis of realizing time offset blind estimation based on conjugate symmetry, and jointly estimates time offset in the OQAM/OFDM system on the basis, thereby reducing the complexity of the system and improving the spectrum utilization rate of the system. The method provided by the invention can simultaneously consider both the frequency spectrum resource consumption and the system performance.
Drawings
FIG. 1 shows a schematic diagram of the operation of an OQAM/OFDM system;
FIG. 2 shows a schematic diagram of a received signal segmentation method;
FIG. 3 is a graph showing a comparison of time-biased STO performance simulations in an exemplary embodiment of the present invention;
fig. 4 is a diagram illustrating simulation comparison of frequency offset CFO performance in an embodiment of the present invention.
Detailed Description
Specific embodiments of the present invention are given below with reference to the accompanying drawings. The parameters in the examples are merely to illustrate the invention and do not affect the generality of the invention.
To achieve the above object, a segmentation method of transmission symbols is first proposed, as shown in fig. 2. The time offset estimation is realized by proving the conjugate symmetry of each section, and on the basis, the frequency offset estimation is realized by using the pilot frequency information and the proved conjugate symmetry. The specific technical scheme comprises the following steps:
step 1: to NbThe transmission symbols are segmented. a, b and c represent the region a*b*And c*Conjugate pairThe term "region", c denotes the region that is not used, and x denotes the region that does not have conjugate symmetry.
Step 2: defining a first M-dimensional matrixIs arranged at the m-th row and the n-th column
Figure BSA0000193000210000052
M is in the range of {0, 1, …, M-1}, N is in the range of {0, 1, …, N }, and N is the number of matrix columns, wherein R, I is the real part and imaginary part corner mark respectively; defining a second M-dimensional matrix
Figure BSA0000193000210000053
Row m and column n
Figure BSA0000193000210000054
Is expressed as
Figure BSA0000193000210000055
Wherein j is an imaginary unit, m', n are
Figure BSA0000193000210000056
The number of rows and columns of
Figure BSA0000193000210000057
Wherein IDFT [. C]For inverse discrete Fourier transform, w is an M-dimensional vector, and the M term is wm＝jm。
And step 3: defining a third M-dimensional matrix
Figure BSA0000193000210000061
Row m and column n
Figure BSA0000193000210000062
Is expressed as
Figure BSA0000193000210000063
Wherein n' isThe column coordinates of (a) are,
Figure BSA0000193000210000065
is the sampling interval, T is the symbol interval, g (-) is the prototype filter function; order to
Figure BSA0000193000210000066
ThenCan be expressed as
Figure BSA0000193000210000068
And 4, step 4: defining an M-dimensional matrix gnRow m and column nSince the prototype filter is defined over the interval [0, KT) (K is an overlap factor), the matrix g is only if n ∈ {0, 1, …, K-1}, thennThe significance is given; at this time, the process of the present invention,the same can be obtained
Figure BSA00001930002100000611
I is an imaginary part corner mark;
and 5: according to the nature of the prototype filter g (m) and
Figure BSA00001930002100000612
is delayed by the sampling of
Figure BSA00001930002100000613
Figure BSA00001930002100000614
Wherein
Figure BSA00001930002100000615
Represents
Figure BSA00001930002100000616
The first segment of the sample is taken,
Figure BSA00001930002100000617
represents
Figure BSA00001930002100000618
The second section of sampling, and so on; gk，sAnd gk，lEach represents gkFirst one of (1)
Figure BSA00001930002100000619
Sampling and second
Figure BSA00001930002100000620
Sampling;and
Figure BSA00001930002100000622
respectively representFirst one of (1)
Figure BSA00001930002100000624
Sampling and second
Figure BSA00001930002100000625
Sampling; when k is more than or equal to 5,
Figure BSA00001930002100000626
structure of and
Figure BSA00001930002100000627
the structure is the same;
step 6: receiving signal of system
Figure BSA00001930002100000628
A sequence regarded as a matrix
Figure BSA00001930002100000629
Detecting a region with conjugate symmetry of a received signal, namely whether positive and negative frequency amplitude components are symmetrical or not, and phase components of the positive and negative frequency amplitude components are just opposite;
and 7: computing statistics
Figure BSA0000193000210000071
Where θ is the time offset. In order to eliminate the influence of noise on the time offset estimation, a threshold value ζ is set;
and 8: estimating the time offset:
Figure BSA0000193000210000072
wherein
Figure BSA0000193000210000073
And step 9: receiving a pilot signal matrix
Figure BSA0000193000210000074
Is a matrix of received pilot symbols in accordance with the received timing. Suppose that
Figure BSA0000193000210000075
For two adjacent received pilot signal matrices, the system frequency offset is
Figure BSA0000193000210000076
DETAILED DESCRIPTION OF EMBODIMENT (S) OF INVENTION
In one embodiment of the invention, the number of pilots is set to 1024, the channel model is an ITU-T wireless channel and an AWGN channel, the sparsity of the channel is 6, the multipath delay is-30324711 } mus, the multipath gain is-60-7-22-16-20 } dB, the channel length is 129, the number of pilots is selected to be 40, and the prototype filter is selected to be IOTA (α ═ 1, overlap factor 4). Time offset tau0A fluctuation range of τ0E {3M, …, 4M-1}, frequency offset mu0The fluctuation range is [ -0.45, 0.45 [)]。
For different channels and thresholds, the Root Mean Square Error (RMSE) performance of the method of the present invention (denoted by method C in the simulation for convenience) was simulated under three channels and different thresholds, and compared with the method proposed by t.fusco and m.tanda in the document "bland CFO estimation for OFDM/OQAM systems" (denoted by method a in the simulation), and the method proposed by gan Yang et al in the document "Data-aided joint system timing and CFO estimation for OFDM/OQAM systems" (denoted by method B in the simulation).
Fig. 3 is a schematic diagram showing RMSE performance comparison of time offset estimation of an OQAM/OFDM system designed by the present invention at different channels and thresholds. Where the horizontal axis represents signal-to-noise ratio and the vertical axis represents RMSE (in dB). It can be seen from the figure that the RMSE performance using the time offset estimation method of the present invention is superior to that of ITU-B in ITU-a and AWGN channels. Under the same channel condition, the smaller the threshold value is, the better the time offset estimation performance is. Therefore, the method provided by the invention can improve the RMSE performance of the system time offset estimation.
Fig. 4 is a schematic diagram showing comparison between RMSE of frequency offset estimation of OQAM/OFDM system designed by the present invention and the method proposed by t.fusco and m.tanda in "bland CFO estimation for OFDM/OQAM systems" (method a), and the method proposed by GangYang et al in "Data-aided joint system timing and CFO estimation for OFDM/oqa estimation" in (method B). It can be seen that the RMSE performance of the system using the proposed method is superior to the other two methods. Therefore, the method provided by the invention can effectively improve the frequency offset estimation performance of the system.
By way of example, it can be seen that the time-frequency offset estimation method of the invention can significantly improve the time-frequency offset estimation accuracy of an OQAM/OFDM system, and the improvement of the accuracy is realized on the basis of reducing the system complexity, so that the method of the invention can also reduce the system complexity.
The invention aims at an OQAM/OFDM system, combines a blind estimation method with pilot frequency, estimates time offset by using conjugate symmetry on the basis of realizing time offset blind estimation based on conjugate symmetry, and jointly estimates time offset in the OQAM/OFDM system on the basis, thereby reducing the complexity of the system and improving the spectrum utilization rate of the system. The method provided by the invention can simultaneously consider both the frequency spectrum resource consumption and the system performance.
The above examples are merely exemplary embodiments of the present invention, and the application of the present invention is not limited to the above examples, and any modification, replacement, and improvement made within the spirit and principle of the present invention should be included in the scope of the present invention.

Claims (1)

1. A time-frequency offset joint estimation method in OQAM/OFDM comprises the following steps:
step 1: to NbSegmenting the transmission symbols; a. b and c represent the region a, respectively*、b*And c*Conjugate symmetric regions, c represents regions that are not used, x represents regions that do not have conjugate symmetry;
step 2: defining a first M-dimensional matrix
Figure FSA0000193000200000011
Is arranged at the m-th row and the n-th columnM is in the range of {0, 1, …, M-1}, N is in the range of {0, 1, …, N }, and N is the number of matrix columns, wherein R, I is the real part and imaginary part corner mark respectively; defining a second M-dimensional matrix
Figure FSA0000193000200000013
Row m and column n
Figure FSA0000193000200000014
Is expressed as
Figure FSA0000193000200000015
Wherein j is an imaginary unit, m', n are
Figure FSA0000193000200000016
The number of rows and columns of
Figure FSA0000193000200000017
Wherein IDFT [. C]For inverse discrete Fourier transform, w is an M-dimensional vector, and the M term is wm＝jm；
And step 3: defining a third M-dimensional matrix
Figure FSA0000193000200000018
Row m and column nIs expressed as
Figure FSA00001930002000000110
Wherein n' isThe column coordinates of (a) are,
Figure FSA00001930002000000112
is the sampling interval, T is the symbol interval, g (-) is the prototype filter function; order to
Figure FSA00001930002000000113
ThenCan be expressed as
Figure FSA00001930002000000115
And 4, step 4: defining an M-dimensional matrix gnRow m and column n
Figure FSA00001930002000000116
Since the prototype filter is defined over the interval [0, KT) and K is an overlap factor, the matrix g is only if n ∈ {0, 1, …, K-1}, thennThe significance is given; at this time, the process of the present invention,
Figure FSA00001930002000000117
the same can be obtained
Figure FSA00001930002000000118
I is an imaginary part corner mark;
and 5: according to the nature of the prototype filter g (m) and
Figure FSA00001930002000000119
is delayed by the sampling of
Figure FSA00001930002000000120
Figure FSA00001930002000000121
Wherein
Figure FSA00001930002000000122
RepresentsThe first segment of the sample is taken,
Figure FSA0000193000200000022
represents
Figure FSA0000193000200000023
The second section of sampling, and so on; gk，sAnd gk，iEach represents gkFirst one of (1)
Figure FSA0000193000200000024
Sampling and secondSampling;and
Figure FSA0000193000200000027
respectively represent
Figure FSA0000193000200000028
First one of (1)
Figure FSA0000193000200000029
Sampling and second
Figure FSA00001930002000000210
Sampling; when k is more than or equal to 5,
Figure FSA00001930002000000211
structure of and
Figure FSA00001930002000000212
the structure is the same;
step 6: receiving signal of systemA sequence regarded as a matrix
Figure FSA00001930002000000213
Detecting a region with conjugate symmetry of a received signal, namely whether positive and negative frequency amplitude components are symmetrical or not, and phase components of the positive and negative frequency amplitude components are just opposite;
and 7: computing statisticsWherein θ is time offset; in order to eliminate the influence of noise on the time offset estimation, a threshold value ζ is set;
and 8: estimating the time offset:
wherein
Figure FSA00001930002000000216
And step 9: receiving a pilot signal matrix
Figure FSA0000193000200000031
Is a matrix formed by receiving pilot symbols according to a receiving time sequence; suppose that
Figure FSA0000193000200000032
For two adjacent received pilot signal matrices, the system frequency offset is
Figure FSA0000193000200000033
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