CN110474856B - Channel estimation method based on complete interference elimination - Google Patents
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- H04L25/0226—Channel estimation using sounding signals sounding signals per se
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- H04L25/0202—Channel estimation
- H04L25/024—Channel estimation channel estimation algorithms
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- H04L5/0048—Allocation of pilot signals, i.e. of signals known to the receiver
Abstract
The invention discloses a channel estimation method based on complete interference elimination, belonging to the field of filter bank multi-carrier communication. The method comprises the following steps: inserting a sparse block-shaped pilot frequency symbol in a frame header of a subframe to be transmitted, and inserting a row of zero guard intervals in the front and rear time positions of the pilot frequency symbol; calculating the total imaginary part interference suffered by the pilot frequency symbol; inserting designed auxiliary symbols in the front and rear time positions of the sub-carrier where the pilot symbol is located; adopting OQAM/FBMC to send and receive pilot symbols, auxiliary symbols and data symbols in frames of a frame header; and obtaining the channel frequency response of the subcarrier where the pilot symbol is located based on a least square criterion, and obtaining the estimated value of the actual channel through Fourier transformation. The invention effectively counteracts the imaginary part interference generated by the data symbol to the pilot frequency symbol by inserting the additional auxiliary symbol at the zero guard interval of the sparse block pilot frequency, and can effectively improve the channel estimation performance under the condition of not changing the structure of the receiver.
Description
Technical Field
The invention belongs to the field of filter bank multi-carrier communication, and particularly relates to a channel estimation method based on complete interference elimination.
Background
A conventional Orthogonal Frequency Division Multiplexing (OFDM) system adopts a time domain rectangular window, which causes problems of high system Frequency domain sidelobe, sensitivity to Frequency offset, strict requirement on synchronization, and the like. In contrast, Filter Bank Multicarrier with Offset Quadrature Amplitude Modulation (OQAM/FBMC) employs a prototype Filter with very low spectral sidelobes, and the out-of-band leakage of the transmitted signal is very weak. Meanwhile, strict synchronization and orthogonality do not need to be kept in the whole network range between user signals of the OQAM/FBMC system, so that the synchronization overhead and access delay of the system are greatly reduced, the system design is more flexible and efficient, and the method is very suitable for typical application scenes such as machine type communication, coordinated multi-point transmission communication and the like in future wireless communication. At present, OQAM/FBMC has been listed as one of candidate modulation techniques for 5G cellular networks, Professional Mobile Radio (PMR) evolution and satellite communication, and is regarded as important in the application prospect of future wireless communication.
There are still many key technical problems to be studied for the OQAM/FBMC system, and the pilot design is one of the most important items. Since future mobile communication faces more complicated communication environments, multipath effects and doppler effects impose higher requirements on the communication quality of the system, and channel estimation is essential. For accurate channel estimation, it is generally necessary to insert additional pilot symbols within the data frame, which are known at both the transmitting end and the receiving end of the system. However, the OQAM/FBMC is different from the conventional OFDM system, and after the receiving end of the OFDM system passes Fast Fourier Transform (FFT), the data and pilot symbols are completely separated. However, in the OQAM/FBMC system, due to the use of non-orthogonal filters, pilot symbols suffer from inherent Inter-Symbol/Inter-Carrier Interference (ISI/ICI) from both the time and frequency domains. ISI/ICI manifests as imaginary interference to real symbols, regardless of the channel. Therefore, the pilot design method in the conventional OFDM system cannot be directly used for the OQAM/FBMC system.
An article (d.katselis, e.kofidis, a.rotagiannis, and s.theodoris, "Preamble-based channel estimation for CP-OFDM and OFDM/OQAM systems: a comparative channel," IEEE trans.signal process, vol.58, No.5, pp.2911-2916, May 2010.) proposes a sparse block pilot design scheme, which proves that, on the premise that the imaginary part interference of a pilot symbol by a data symbol is assumed to be zero, by inserting an equi-power, equi-spaced sparse block pilot structure in the frame header of the subframe to be transmitted, the optimal channel estimation mean square error MSE performance can be obtained at the receiving end. However, the scheme has the problem of residual data interference, and data symbols generate certain imaginary part interference on the pilot frequency, so that the problem of error floor of the channel estimation MSE performance at high signal-to-noise ratio is caused. Especially for prototype filters with poor time-domain focusing, large residual data interference can cause significant degradation of channel estimation performance.
Disclosure of Invention
Aiming at the defects of the prior art, the invention aims to provide a sparse block pilot design method based on complete interference cancellation, and aims to solve the problem of low channel estimation performance caused by the fact that imaginary part interference generated by data symbols on pilot symbols is not considered in the conventional pilot design method.
To achieve the above object, the present invention provides a channel estimation method based on complete interference cancellation, including:
(1) inserting a sparse block-shaped pilot frequency symbol into a frame header of a subframe to be transmitted for channel estimation, and inserting a row of zero guard intervals into the front and rear time positions of the pilot frequency symbol;
(2) respectively calculating and superposing imaginary part interference of different data symbols on the pilot symbol according to imaginary part interference coefficients caused by different data symbols on the pilot symbol to obtain total imaginary part interference on the pilot symbol;
(3) inserting designed auxiliary symbols respectively in the front and rear time positions of the subcarrier where the pilot symbol is located so as to counteract imaginary part interference suffered by the pilot symbol;
the auxiliary symbols comprise a first auxiliary symbol A1And a second auxiliary symbol A2The first auxiliary symbol A1And a second auxiliary symbol A2Satisfies the following conditions: a. the1＝-A2I/2r, wherein r denotes the auxiliary symbol a2For the imaginary part interference coefficient of the pilot frequency symbol, I is the total imaginary part interference suffered by the pilot frequency symbol;
(4) adopting a filter bank multicarrier OQAM/FBMC based on offset quadrature amplitude modulation to send and receive pilot symbols, auxiliary symbols and data symbols in frames of a frame header;
(5) and obtaining the channel frequency response of the subcarrier where the pilot symbol is located based on a least square criterion, and obtaining the estimated value of the actual channel through Fourier transformation.
Furthermore, the pilot symbols are sparse block pilot sequences with equal power and equal interval, and the subcarrier index set of the sparse block pilot sequences is
For estimating the impulse response CIR of the channel;
wherein, M is the number of the sub-carriers of the OQAM/FBMC system, and L is the length of the channel.
Further, the zero guard interval and the pilot symbols form an M × 3 time-frequency matrix; the pilot symbols are located in the second column of the time-frequency matrix.
Further, the total imaginary part interference suffered by the pilot symbols is I ═ wd; wherein d ═ d1,d2,d3,…dU]TRepresenting the associated U data symbols causing imaginary interference to the pilot symbols; w ═ w1,w2,…,wU]And represents imaginary interference coefficients corresponding to different data symbols.
Further, the transmission signal at the kth time after the OQAM/FBMC modulation in step (4) is:
wherein, am,nIs the real data sent at the nth time on the mth subcarrier, g k]Is a prototype filter function, j is an imaginary unit, and Z represents an integer set;
the demodulation data at the time frequency point of the receiving end (m, n) is as follows:
wherein, r [ k ] is the received signal of the signal s [ k ] after channel transmission.
Further, the step (5) specifically comprises:
(5.1) obtaining a pilot frequency point m epsilon by adopting a least square estimation methodLChannel estimation value of (b):
wherein, ym,1And am,1Respectively representing a demodulation symbol and a pilot symbol at the 1 st moment on the mth subcarrier;
(5.2) combining the obtained L channel estimation values into a column vector
Obtaining the estimated value of the channel impulse response CIR:
wherein, FL×LRepresenting the first L columns of an M x M-point Discrete Fourier Transform (DFT) matrix F and a set of pilot subcarrier indicesLThe size formed by the corresponding L rows is L multiplied by L sub-matrixes;
(5.3) estimating the CIR according to the channel impulse response
And obtaining the CFR estimated value of the channel frequency response on all the subcarriers.
Wherein the content of the first and second substances,
FM×La submatrix of size M × L composed of the first L columns of the M × M-point DFT matrix F is represented.
Further, when M/L is not an integer, the channel length is extended to zero padding operation
Then, corresponding pilot frequency design and channel estimation operation are carried out, and finally the final estimated channel impulse response CIR is removed
The number of the cells; wherein the content of the first and second substances,
means not less than log2The smallest positive integer of L.
Through the technical scheme, compared with the prior art, the invention has the following beneficial effects:
the invention effectively counteracts the imaginary part interference generated by the data symbol to the pilot frequency symbol by inserting the additional auxiliary symbol at the zero guard interval of the sparse block pilot frequency, can solve the problem of high signal-to-noise ratio error floor caused by the data interference in the design of the block pilot frequency of the filter bank multi-carrier system under the condition of not changing the structure of a receiver, and effectively improves the channel estimation performance.
Drawings
FIG. 1 is a frame structure of an OQAM/FBMC system based on the sparse block pilot;
fig. 2 is a comparison of the channel estimation performance of the pilot design with the conventional scheme under different filters.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention.
The invention provides a channel estimation method based on complete interference cancellation, which comprises the following steps:
(1) inserting sparse block pilot symbols for channel estimation into a frame header of a subframe to be sent by a system, and inserting a column of zero guard intervals at the front and rear time positions of the pilot symbols;
specifically, as shown in fig. 1, three columns of block pilot sequences are inserted into the frame header, the second column of symbols of the block pilot exhibits a sparse structure, and includes L pilot symbols with equal power and equal interval, which have the same length as the channel, and are used for channel estimation, and the subcarrier index set of the sparse structure is:
wherein, M represents the number of subcarriers of the system, and the first and third columns of zero guard intervals of the block pilot are used for suppressing the imaginary part interference caused by the data symbol to the pilot symbol.
(2) Respectively calculating and superposing imaginary part interference of different data symbols on the pilot symbol according to imaginary part interference coefficients caused by different data symbols on the pilot symbol to obtain total imaginary part interference on the pilot symbol;
specifically, the total imaginary part interference suffered by the pilot symbols is I ═ wd; wherein d ═ d1,d2,d3,…dU]TRepresenting the associated U data symbols causing imaginary interference to the pilot symbols; w ═ w1,w2,…,wU]Representing imaginary interference coefficients corresponding to different data symbols;
based on the difference of time-frequency focusing of different prototype filters, the number, the position and the interference coefficient of data symbols which generate interference on the pilot frequency are different. For a classic PHYDYAS prototype filter, the number of data symbols generating imaginary interference to pilot symbols on (m, n) time-frequency points is 12, and the time-frequency distribution region is { (m)0,n0)||m0-m|≤1,2≤n0-n ≦ 5}, corresponding interference coefficients w ═ 0.125,0, -0.125,0.0429,0.0668,0.0429,0.0054,0, -0.0054,0.0013,0.0023,0.0013, respectively]1j, where j is an imaginary unit; for a classical IOTA prototype filter, the number of data symbols that would interfere with the pilot symbols at the (m, n) time-frequency points is 14, and the time-frequency distribution region is { (m)0,n0)||m0-m|≤3,2≤n0-n ≦ 3}, and corresponding imaginary interference coefficients w ═ 0.0016,0,0.038,0, -0.038,0, -0.0016,0,0.0016,0.0103,0.0183,0.0103,0.0016,0]And 1j, calculating the total residual data interference I suffered by the pilot frequency according to the data symbol and the interference coefficient at the corresponding position.
(3) Inserting designed auxiliary symbols in the front and rear time positions of the sub-carrier where the pilot symbol is located respectively to offset imaginary part interference suffered by the pilot symbol;
in particular, note the auxiliary symbol a on the (m, n +1) time frequency point2For the interference coefficient r of the pilot frequency on the (m, n) time frequency point, the auxiliary symbol A on the (m, n-1) time frequency point is determined according to the symmetry property of the prototype filter1Corresponding to interference coefficient of-r, designing auxiliary symbol A1And A2Have the same amplitude to reduce the power overhead, and the size of the amplitude respectively represents A1＝-A2When the system adopts 4QAM modulation, for a classic PHYDYAS prototype filter, r is 0.5644j, and the statistical average power of the auxiliary symbols is 0.031; for the classical IOTA prototype filter, r is 0.4411j and the statistical average power of the auxiliary symbols is 0.004.
(4) Adopting a filter bank multicarrier OQAM/FBMC based on offset quadrature amplitude modulation to send and receive pilot symbols, auxiliary symbols and data symbols in frames of a frame header;
specifically, the transmission signal at the kth time after the OQAM/FBMC modulation is:
wherein, am,nIs the real data sent at the nth time on the mth subcarrier, g k]Is a prototype filter function, j is an imaginary unit, and Z represents an integer set;
the demodulation data at the time frequency point of the receiving end (m, n) is as follows:
wherein, r [ k ] is the received signal of the signal s [ k ] after channel transmission.
(5) And obtaining the channel frequency response of the subcarrier where the pilot symbol is located based on a least square criterion, and obtaining the estimated value of the actual channel through Fourier transformation.
Specifically, the step (5) includes:
(5.1) obtaining a pilot frequency point m epsilon by adopting a least square estimation methodLChannel estimation value of (b):
wherein, ym,1And am,1Respectively representing a demodulation symbol and a pilot symbol at the 1 st moment on the mth subcarrier;
(5.2) combining the obtained L channel estimation values into a column vector
Obtaining the estimated value of the channel impulse response CIR:
wherein, FL×LRepresenting the first L columns of an M x M-point Discrete Fourier Transform (DFT) matrix F and a set of pilot subcarrier indicesLThe size formed by the corresponding L rows is L multiplied by L sub-matrixes;
(5.3) estimating the CIR according to the channel impulse response
And obtaining the CFR estimated value of the channel frequency response on all the subcarriers.
Wherein the content of the first and second substances,
FM×La submatrix of size M × L composed of the first L columns of the M × M-point DFT matrix F is represented.
In particular, when M/L is not an integer, the channel length is extended to zero padding operation
Then, corresponding pilot frequency design and channel estimation operation are carried out, and finally the final estimated channel impulse response CIR is removed
The number of the cells; wherein the content of the first and second substances,
means not less than log2The smallest positive integer of L.
In order to verify the effectiveness of the method, the embodiment of the invention carries out simulation tests in a Matlab environment. The specific parameter settings for the simulation are as follows: the number of subcarriers of the OQAM/FBMC system is M-256, each frame comprises 20 OQAM symbols, and two different prototype filters, namely PHYDYAS and IOTA, are respectively adopted; the multipath channel selects the SUI-3 channel proposed by the IEEE802.16 broadband Wireless Access working group, and the channel of each frame is random, but the channel of the same frame remains unchanged. The Mean Square Error (MSE) performance of different channel estimation methods is compared at a receiving end, and the result is shown in FIG. 2, and simulation results show that no matter what prototype filter is adopted, the traditional channel estimation method has the problem of error floor in a high signal-to-noise ratio (SNR) area due to the influence of residual data interference. The channel estimation method based on complete interference elimination provided by the invention eliminates the influence of data interference by designing auxiliary symbols, solves the problem of error floor in a high signal-to-noise ratio (SNR) area, and improves the channel estimation performance.
It will be understood by those skilled in the art that the foregoing is only a preferred embodiment of the present invention, and is not intended to limit the invention, and that any modification, equivalent replacement, or improvement made within the spirit and principle of the present invention should be included in the scope of the present invention.
Claims (7)
1. A channel estimation method based on complete interference cancellation, comprising:
(1) inserting a sparse block-shaped pilot frequency symbol in a frame header of a subframe to be transmitted, and inserting a row of zero guard intervals in the front and rear time positions of the pilot frequency symbol; the zero guard interval is used for suppressing imaginary part interference caused by the data symbols to the pilot symbols;
(2) respectively calculating and superposing imaginary part interference of different data symbols on the pilot symbol according to imaginary part interference coefficients caused by different data symbols on the pilot symbol to obtain residual imaginary part interference on the pilot symbol;
(3) inserting designed auxiliary symbols in the front and rear time positions of the sub-carrier where the pilot symbol is located respectively to offset residual imaginary part interference suffered by the pilot symbol;
the auxiliary symbols comprise a first auxiliary symbol A1And a second auxiliary symbol A2The first auxiliary symbol A1And a second auxiliary symbol A2Satisfies the following conditions: a. the1＝-A2I/2r, wherein r denotes the auxiliary symbol a2For the imaginary part interference coefficient of the pilot frequency symbol, I is the residual imaginary part interference suffered by the pilot frequency symbol; the auxiliary symbols have the same amplitude to reduce power overhead;
(4) adopting a filter bank multicarrier OQAM/FBMC based on offset quadrature amplitude modulation to send and receive pilot symbols, auxiliary symbols and data symbols in frames of a frame header;
(5) and obtaining the channel frequency response of the subcarrier where the pilot symbol is located based on a least square criterion, and obtaining the estimated value of the actual channel through Fourier transformation.
2. The method of claim 1, wherein the pilot symbols are sparse block pilot sequences with equal power and equal spacing, and the subcarrier index sets thereof are sparse block pilot sequences with equal power and equal spacing
For estimating the impulse response CIR of the channel;
wherein, M is the number of the sub-carriers of the OQAM/FBMC system, and L is the length of the channel.
3. The method of claim 2, wherein the zero guard interval and the pilot symbols form an M x 3 time-frequency matrix; the pilot symbols are located in the second column of the time-frequency matrix.
4. A method for channel estimation based on full interference cancellation according to any of claims 1-3, characterized in that the pilot symbols are subject to total imaginary interference I ═ wd; wherein d ═ d1,d2,d3,...dU]TRepresenting the associated U data symbols causing imaginary interference to the pilot symbols; w ═ w1,w2,…,wU]And represents imaginary interference coefficients corresponding to different data symbols.
5. The channel estimation method based on complete interference cancellation according to claim 1, wherein the transmitted signal s [ k ] at the kth time after the OQAM/FBMC modulation in step (4) is:
wherein, am,nIs the real data sent at the nth time on the mth subcarrier, g k]Is a prototype filter function, j is an imaginary unit, and Z represents an integer set;
the demodulation data at the time frequency point of the receiving end (m, n) is as follows:
wherein, r [ k ] is the received signal of the signal s [ k ] after channel transmission.
6. The channel estimation method based on complete interference cancellation according to claim 1, wherein the step (5) specifically includes:
(5.1) obtaining a pilot frequency point m epsilon by adopting a least square estimation methodLChannel estimation value of (b):
wherein, ym,1And am,1Respectively representing a demodulation symbol and a pilot symbol at the 1 st moment on the mth subcarrier;
(5.2) combining the obtained L channel estimation values into a column vector
Obtaining the estimated value of the channel impulse response CIR:
wherein, FL×LFirst L columns and pilot subcarrier index set for representing M x M point discrete Fourier transform matrix FLThe size formed by the corresponding L rows is L multiplied by L sub-matrixes;
(5.3) estimating the CIR according to the channel impulse response
Obtaining CFR estimated values of channel frequency responses on all subcarriers;
wherein the content of the first and second substances,
FM×La submatrix of size M × L composed of the first L columns of the M × M-point DFT matrix F is represented.
7. The method of claim 6, wherein when M/L is not an integer, the channel length is extended by zero padding to obtain zero padding
Then carry out the correspondingAnd removing the last in the finally estimated channel impulse response CIR
The number of the cells; wherein the content of the first and second substances,
means not less than log2The smallest positive integer of L.
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