CN1104002A - Method for controlling resonance power conversion - Google Patents
Method for controlling resonance power conversion Download PDFInfo
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- CN1104002A CN1104002A CN 93121000 CN93121000A CN1104002A CN 1104002 A CN1104002 A CN 1104002A CN 93121000 CN93121000 CN 93121000 CN 93121000 A CN93121000 A CN 93121000A CN 1104002 A CN1104002 A CN 1104002A
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Abstract
The invention, relates to current transformers of semi-conductor, causes resonance transformer to operate in self-adapting control of approximate resonance under changes of component parameters, input voltage and load, and to output constant current and voltage. It is suitable for use in program control of load characteristic simulation, such as in high freq. motors, welders, etc. and also resonance switching power supplies.
Description
A kind of method for controlling resonance power conversion is to belong to the Semiconductor Converting Technology field, can be in high-frequency motor, high-frequency welding machine, supersonic generator, high-frequency induction heating, fluorescent lamp or gaseous discharge lamp ballast or constant current, neon lamp power source and high pressure generator also can be made resonant transformation formula Switching Power Supply according to this method.
Many loading under the high-frequency worked, and can reduce volume, weight, and the raising to economize on electricity, complete machine performance is beneficial especially in addition.Yet prior art produces high-frequency sine wave or nearly sinusoidal wave converter method one class is to make inverter output interruption square wave (can modulate) or produce the multi-ladder ripple by multiple method, be filtered into sine then, like this frequency can do quite stable, and shortcoming to be efficient low or the too high control of cost is complicated, only be fit to decide the load of frequency and voltage, as " DC converter principle and design " (People's Telecon Publishing House's publication) and " transistor circuit " the 2nd (department of electronic engineering, tsinghua university is compiled Science Press and published).
Another kind of is " series inverter ", and essence is a kind of special case of semibridge system square-wave inverter." transistor circuit " the 2nd 971 pages introduced this mode in forced reversing, natural commutation, three kinds of situations of critical commutation, point out to face when being situated between commutation, the most approaching sine wave, also point out only to adapt to small-power, load variations, frequency respective change (also having the voltage respective change certainly), so how, just can reach critical commutation and other commutation control, specific or concrete control circuit do not introduced in its literary composition, other books and periodicals are not found yet, may be that this converter method formula exists shortcoming too many, only are qualitative analyses, to its further investigation, people also relatively ignore.Should state, also have the unsteady flow switch element will bear several times of supply voltage, only this point just is difficult to enter practicality.Certainly also have some similar example application; as CN2070058u; the morphotropism that is this mode is used; the control mode level is higher; be to be applied to high-frequency induction heating; it is that above-mentioned semibridge system changes full bridge application into; be L; the C series resonant circuit is between cross-over connection two half-bridges; certain such basic structure; be for a long time public; crucial is that what kind of control the unsteady flow switch element is imposed; thereby reach due application performance; thereby the different characteristic that has just the caused control method feature different with the control circuit structure; with regard to CN2070058u; its control circuit only is applicable to this application; with controllable silicon be the unsteady flow switch element of object; its shortcoming needs start-up operation in addition; no-load current is big; frequent starting commutation failure may take place and even be difficult to protection (also when keeping, opening) as vibration; controllable silicon is a pulse-triggered in addition; in fact in order to improve antijamming capability and turn-off speed, must add back-pressure, as being more satisfactory driving method with a suitable differential of ac square wave in the off period." DC converter principle and design " pointed out in the full-bridge type inverter that output transformer is coupled with capacitor C and can be obtained sine wave, in fact this moment, primary was equivalent to resonant inductance L, L connects with C and is connected across between two half-bridge, it is the citation form of full-bridge type resonance inverter, its implication is: when C is some definite values, L, C natural frequency are identical with control frequency, and resonance will take place, and will produce sine wave.
CN2107117u, CN2134029 etc. are the patent application typical examples of existing up to a hundred electronic ballast for fluorescent lamp, also represent the basic structure of neon light, electronic ballast of sodium lamp patent, they are except that drive part, be the basic structure form that known series resonance becomes device or semi-bridge type inverter, and their drive circuit feature to be known load current mutual inductance feedback drive that the part of load current is coupled on the unsteady flow switch element.Though this is simple in structure, can not realize the control adjustment of resonance current, performances such as preheating starter, short circuit, open-circuit-protection are difficult to take into account.In order to solve this shortcoming, CN2091057u has done so-called improvement, and essence is the type of drive and the structure of known half-bridge self-excitation square-wave inverter, does not also reach the practical application purpose.
CN1056965 is the citation form of existing three-phase inverter, is applied to threephase motor, and it has just used the good characteristic of field effect transistor, forced commutation easily, frequency can be done highly, but harmonic wave is very big, motor also has harmonic noise, far can not satisfy actual requirement.If make three phase windings be in resonance condition, a good way that yes, lean on and the capacitance compensation power factor (PF) as threephase motor, CN1060372A also is this principle, yet this is a low frequency, desired volume is big, load variations in addition, electric capacity should be followed variation automatically, auto power-factor compensating device (switching capacitance) is exactly this wisdom so, yet its disadvantage is well-known, if by the resonance inversion method, three phase windings are in from strain resonance, and the advantage aspect just has a lot: 1, this body, heavily reduce, power factor (PF) can realize automatic tracking and compensating; Contactless damage, pyrophoric behavio(u)r etc.
Existing in addition high-frequency welding machine all is that the employing square-wave inverter is the unsteady flow power source with being applied to high-power ultrasound generators such as pulverizing, welding, heating, cleaning, atomizing, harmonic wave is greatly distinct issues, be applied to the high-power high voltage generator of plasma high voltage source for another example, also outstanding to harmonic requirement, and existing technology or square-wave inverter.
In addition, existing high power switching power supply exists harmonic wave big, radiated interference, and differ from problem time response, so also need to seek new mode.
Resonance inverter (or claiming the resonance convertor assembly), can be divided in parallel and series resonance dual mode, except that control circuit and resonant circuit, its structure, be the basic structure (dividing half-bridge and full-bridge and three-phase bridge) of existing square wave bridge-type inverter, certainly push off inverter and also can make the parallel resonance formula, if the unsteady flow in them is opened half dollar spare conduction angle control difference, character also can have greatly changed, can be converted into resonance inversion even intermitted resonance inversion from the square wave inversion, so key is conduction angle control.Practical application wishes that conversion is a sine or approaching sinusoidal, the curtage of conversion is controlled, realized the simulation program control that resonance unsteady flow fully or free position keep resonance unsteady flow more completely or nearly resonance unsteady flow or make output current or voltage be adjusted and can add easily to be suitable for load characteristic by the speed governing conduction angle.This purpose of the present invention just, this method for controlling resonance power conversion also is very strong compatibility, be suitable for multiple application, overcome discrete, the variation of resonant element, particularly during load variations, influence to resonance condition, both can be suitable for the unsteady flow switch control of single-phase multiple application, also can be suitable for the benchmark control of a certain phase x phase unsteady flow switch of three-phase, controlling object can be controllable silicon, triode, field effect transistor, static triode and the three-terminal semiconductor element that can turn on and off current characteristic; Have the startup function concurrently, need not establish start-up circuit in addition; Be convenient to add gating control, keying, to realize overcurrent, overvoltage protection and the control of keying intermitted resonance.
Specific implementation method can be: 1, resonance current is taken a sample or sensing gained signal I
kObtain V through no phase shift or in-phase voltage conversion
kIn order to make control accurately, can be earlier V
kBe shaped to homophase square wave V
Hf, then V
HfIntegration or be filtered into nearly sine wave and become the reference signal V that amplitude is not influenced by load or power-supply ripple
k', again with V
k' (or V
k) add the Schmidt trigger voltage comparator and handle and be transformed into and I
kThe square wave V that given phase relation is arranged
, then with V
The multivibrator more much lower than resonance frequency that desynchronizes, the gate pole of multivibrator or reset terminal are V
Kk, its output or through buffering output can directly be coupled or isolation coupling to the ac square wave V of unsteady flow switch element
k(V
Suitably differential is handled to be suitable for the reasonable driving of switch element in coupling process), V
kWith V
Phase place is identical, applies a fixing threshold voltage at the threshold values end of Schmidt trigger, just can make V
k(or V
) fixing phase shift of maintenance, can make the resonance unsteady flow be in nearly resonance condition or keep a fixing phase shift with complete resonance, by changing the identical or opposite of fixedly threshold values and Schmidt trigger output phase, just can obtain this fixing lag or lead.When needs are adjusted load current or voltage, can be load current or voltage sampling (or sampling indirectly, or mutual inductance reflection sampling), relatively amplify rear drive or directly drive and adjust element such as photoelectrical coupler etc., comparison threshold values size is changed, phase shift changes thereby make fixedly, thereby the resonance unsteady flow is changed between away from resonance and complete resonance, makes load current or voltage obtain adjusting.So deformation method can also be I
hDirectly add the electric current Schmidt trigger, by changing the size and Orientation of current threshold, or make its size be subjected to the variation of the sampled signal size controlled and change, can realize as above performance equally.2, can directly carry out even two (or four) voltage multiplying rectifier to resonance current or shunting resonance current for low-power applications or simple and easy control, obtain a disymmetric pair of voltage, make the self-supporting power of subordinate's power supply, obtain a sinusoidal square wave conversion at the rectifying tube two ends that are connected on the self-supporting power negative pole equally, with this square wave V
Equally can a synchronous multivibrator more much lower than resonance frequency (its gating is V very
Kk), also can cushion through gate circuit, also can remove to trigger a R-S trigger through buffering output control signal V
kOn rectifier diode and fixed capacity, the hysteresis phase shift that then can obtain to fix, also available light electric coupling or triode (or three-terminal element of two-way operation) in parallel with diode R
xWith capacitor C
pBe composed in series the variable RC phase shift,, control these variable resistance elements according to the load current or the voltage of sampling, realizing lagging behind automatically phase shift, this moment phase shift signal V
pFrom R
xWith C
pSeries connection point takes out, and the circuit that also can add a special function phase shifter or phase shift function arranged is as using V
Trigger one 2 frequency multiplier, its output and V
Handle with adding XOR gate, the monostable time of frequency division time is controlled by load signal, and XOR gate output just can controlled signal V through buffering like this
kOutput.C in the as above RC phase shifter uses artificial capacitor C
zReplace, remove to control C with load current or voltage
xChange, also can realize the phase shift that lags behind automatically.The realization of early commutation (being the previous phase place of zero passage) is on rectifying tube and resistance can be realized.3, also: taking a sample in load current or voltage signal or being equivalent to the curtage signal of load and the reference voltage relative error is amplified output voltage V from strain control method
, use V
Control voltage-controlled voltage, perhaps directly control voltage-controlled voltage, perhaps directly use V with load signal
As voltage-controlled voltage, control a voltage-controlled astatic multivibrator, the frequency of multivibrator is changed, thereby make the conduction angle of unsteady flow switch element send out variation, output current or voltage also change thereupon, control loop automatic stabilisation when reaching the setting member value, it is stable or constant that load current or voltage are limited.This kind method is particularly suitable for being made into resonant transformation formula Switching Power Supply.Out of control in order to prevent because of the too big influence of power-supply ripple, detecting the resonance current zero passage or removing to control the pressure-controlled magnitude of voltage, make its qualification near the zero passage commutation signal, just can suppress out of control.4, also can be from strain control method: at three stem stem magnetic cores or two magnetic loop magnetic cores or the iron core such as the EI type of a common magnetic circuit are arranged, on diplopore or dicyclo type or the common magnetic circuit core that is combined into by two single hole magnetic cores or iron core or on the middle stem stem around the mutual inductance secondary coil, allow secondary voltage drive the unsteady flow switch element, at other both sides stem stem or claim after the series connection of mutual inductance primary coil, to seal in load current or shunting load current or resonance current respectively again on the two independent magnetic circuit cores in addition, and make these two coils on the middle stem stem or the magnetic flux that produces on the common magnetic circuit core opposite, in addition on the stem stem of one side or on the independent magnetic circuit core around control coil, the load current of sampling or voltage or the current and voltage signals that will control through relatively amplify rear drive control adjust element absorb primary coil that energy (making the energy on the control coil) on the control coil makes the control coil place on the middle stem stem or the magnetic flux that produces on the common magnetic circuit core change, thereby change secondary output current or voltage, so also changed the conduction angle of unsteady flow switch element or claimed conduction time, output current or voltage are adjusted automatically.Make output variable reach stable or qualification.5, also can be from strain control method: the primary coil that two mutual inductance current feedback is driven used instrument transformer seals in load current, the voltage that closes that their secondary reversed polarity serial connection is constituted drives the unsteady flow switch, on an instrument transformer also around control coil, the load current of sampling or voltage signal are relatively amplified rear drive control to be adjusted element and absorbs energy on the control coil, the synthesising output voltage of two instrument transformers is changed, thereby changed conduction angle, adjusted defeated curtage.6, from strain control method can also be: directly on the instrument transformer that current feedback drives around control coil, relatively amplify rear drive with load current of taking a sample or voltage signal and control the energy of adjusting on the element absorption control coil, reach conduction angle control thereby change secondary output current, make output current or voltage obtain adjusting or limiting.7, from strain control method can also be: the drive principle according to CR timing inverter refers to bridge-type inverter, the resistive element R equivalent resistance controllable elements that changes easily, as replacements such as triode field effect transistor, make the load current or the voltage ratio of sampling amplify these elements of rear drive, its equivalent resistance is changed reach the purpose that changes conduction angle.
The present invention also is to propose to be applied to the resonance unsteady flow control method of three-phase, and this need only be with the output signal V of above-mentioned unsteady flow from the circuit that strain control method constituted
kSend into 120 ° and 240 ° of frequency-tracking phase shifters respectively, buffering output V
Ky, V
KzAs other two-phase is Y phase and Z control mutually.In addition, in order to adjust three-phase imbalance, three-phase imbalance can be set adjust automatically, method is: the triangle circulation signal V that detects X, Y, Z three-phase
AWith neutral current signal V
φCompare and enlarge the gained signal, again through processing in case with the Y phase shift control butt joint of phase shifter mutually, the conduction angle of Y phase unsteady flow switch is produced proofreaies and correct skew, be i.e. the may command serious imbalance that may occur.
The method for controlling resonance power conversion that is applied to three-phase also is: the resistive time constant element of three-phase signal generator is replaced with controllable triode of equivalent resistance or field effect transistor, controlling it with load current of sampling or voltage signal changes, constitute voltage-controlled three-phase signal generator, allow the output signal of sort signal generator control three-phase bridge unsteady flow switch element respectively, if parallel resonance is used, then can desynchronize with the parallel resonance current signal of a certain phase and the pairing phase place of three-phase signal generator, specifically single-phase process as described above.
In addition, aforementioned multivibrator has a variety of, if any 7555, NAND gate, NOR gate, ECL NOR gate, D, J-K, JEC-2 trigger and amplifier etc. all can constitute good multivibrator, and these great majority have gating or reset terminal or easily add gating controlled stage V
Kk, by to V
KkControl; can make the vibration stop and start; thereby also can be used as the overcurrent of resonance convertor assembly, the control end of overvoltage protection; also can be it as the keying control end; realize the application of keying formula resonance unsteady flow; with pwm signal control, realize keying formula Switching Power Supply, or teleswitch signal generation frequently or isolating switch signal output control etc.
May most application to adopt the AC Electric Power power supply rectification filter by the resonance unsteady flow that as above method constituted from strain control device, because big capacitor filtering produces the circuit peak current unavoidablely, the operate as normal of ifs circuit and load crest factor require to allow, rectifying and wave-filtering electric capacity is reduced, in order to improve the line power factor, current harmonics and output crest factor, can be around feedback coil on resonant inductance, making it rectification feeds back to the peak region resonant energy on the power supply, also can be attempted by two series capacitances on the power supply, as resonant capacitance or a part of resonant capacitance, simultaneously on power supply and connect a rectification half-bridge, the input (the serial connection points of two rectifying tubes) that makes the rectification half-bridge and two series capacitances be connected in series a little between, be connected with the serial or parallel connection circuit of inductance with an electric capacity or inductance or electric capacity, as couples back, make two series capacitances feed back to power supply in the peak region resonance potential rectification at two ends respectively.So method for controlling resonance power conversion is also at the feedback method to resonant energy: the may command inductance that is made into according to the magnetic amplifier principle is improved couples back element in line power factor, current harmonics and the output crest coefficient method as the present invention, the control coil of may command inductance is by the load current or the voltage control of sampling, the variation of inductance value like this, feed back to the power supply coupling and measure also respective change, output current or voltage just can obtain adjusting or restriction.
Can be made into according to aforesaid method for controlling resonance power conversion and to be applicable to high-frequency motor, high-frequency welding machine, supersonic generator, high-frequency induction heating, fluorescent lamp or gaseous discharge lamp ballast or constant current or current limliting, neon lamp power source and high pressure generator and resonance transform Switching Power Supply.In addition in order to be applicable to the needs of load characteristic, as realizing the simulation external characteristic of electric welding machine, can be the object of the comparison value of the sampled signal of load as simulation program control.
Now further specify as follows to this control method and principle in conjunction with the accompanying drawings:
Fig. 1 is the resonance convertor assembly basic principle figure of single-phase application.
Fig. 2 is from the strain control method basic block diagram.
Fig. 3 is the resonance convertor assembly basic principle figure of small-power or simple applications.
Fig. 4 is the control principle figure that pressured control frequency is adjusted from strain.
Fig. 5 is series resonance applicating example figure, contains 5A, 5B, 5C, 5D, 5E, 5F, 5G.
Fig. 6 is parallel resonance applicating example figure, contains 6A, 6B, 6C, 6D, 6E, 6F, 6G.
Fig. 7 is the resonance convertor assembly basic principle figure of three-phase and four-line output.
Fig. 8 is the resonance convertor assembly basic principle figure of three-phase six lines output.
Among Fig. 1, the 1st, DC power supply according to the application requirements difference, can be general rectifier power source or High Power Factor rectifier power source or constant-current source, output voltage is V
, at 1 two ends and to connect 2 and 2 ' and 3,2 and 2 ' be that two tandem tap elements are respectively A
1, B
1And A
2, B
2Form, wherein A
1With B
1The serial connection point is 0, A
2And B
2The serial connection point be 0 ', 3 to be two capacitor C
AAnd C
BSerial connection, serial connection point are 0 ', and this is a compatible figure so, in order to merge explanation, i.e. and A
1, B
1With C
A, C
BForm semibridge system unsteady flow structure, and A
1, B
1With A
2, B
2Then can form full-bridge type unsteady flow structure again, be not the present technique feature, and present technique is characterised in that unsteady flow switch element A
1, B
1, A
2, B
2Special control, as following, T is a current transformer, the input current end be I, I ' II ' and sample resistance R arranged
0, also have the effect of bypass high frequency clutter, output be Vh(over the ground), also have group output V
h' V
HoAllow II ' seal in the electric current that will take a sample certainly also sensing otherwise, even direct sample.Certainly also has the voltage sensor method, as common.The 401st, from strain control method basic circuit structure (following), its input termination V
h, output is V
k, gating or reset terminal are V
KkII ' seal in the main resonant circuit of series resonance 5 or in the humorous tank capacitance branch road of parallel resonance 6, the V of output
kSignal can directly be coupled, and also can isolation coupling arrive A
1, B
1, A
2, B
2Control end.V
KkDuring high flat the or low level of input, V
kNo-output or maintain the original state, otherwise V
kNormal output.
Fig. 2 is 401 detailed structure.Wherein II is full-wave rectification, is input as the output V of the T of Fig. 1 current sensor
h' and V
Ho, potentiometer 12 is connected to II two outputs, and central contact connects an input of comparison amplifier 14, and 13 is reference voltage source, is connected between another input and ground of 14, and 14 output meets the light-emitting component D of photoelectrical coupler 7 through resistance
1, 7 can be MCD521.G
1Be operational amplifier, use as Schmidt trigger, R at this
1Be input resistance, the V of a termination current sense T
hEnd, another termination G
1Inverting input, G
1In-phase input end connecting resistance Re in the Pn point, the Re other end to ground, P
Point meets three throw switch K
aMoving plate, in addition three stators are respectively B
k, B
m, B
, B
k, B
MDifference connecting resistance R
pAnd photo resistance (or the variable resistor element that controlled by resonance current) R
, R
p, R
xThe other end is with being connected to P
mPoint, simultaneously, B
xConnecting resistance or variable resistor R
nAlso can resemble R
sLike that by sampled signal control, to inverter G
2Output, G
2Input be P
mThe point.In addition at P
Throw when Bk G
1Lagging voltage than for Re/Re+Rp, its value is gone to zero, even can be zero, this state is the no-voltage comparator; When Pn threw in Bn, leading voltage transferred Rn can change leading phase shifting angle than being Re/Re+Rn; When Pn threw in Bm, lagging voltage was than being Re/Re+Rx, and Rx is subjected to resonance current or voltage or load current voltage control.So the size of the comparison threshold values by changing the Schmidt trigger voltage comparator and its identical or opposite with the comparator output phase just can realize V thus
With I
bFixed lead or hysteresis phase shift, or automatically leading or hysteresis phase shift, thus also can adjust resonance current or voltage or load current or voltage.P
mOutput voltage is V
, V
Through the synchronous end of capacitor C m crosstalk resistance Rm to multivibrator 8, V
KkBe 8 gate pole, 8 output is through 9 buffering output Vk control signals.The Vk control signal is an ac square wave, just can be suitable for controllable silicon through suitable differential and trigger needs, can directly drive or isolation coupling curtage driving elements such as field effect transistor, triode, static triodes, directly drive or during isolation coupling, also can do to quicken to handle.
Accompanying drawing 3 are small-powers with or simple and easy control, only different with Fig. 1 is control circuit is 402,402 principle schemes are as described in the motion 2.Also can be suitable for high-power applications, this moment if the transducing signal input that changes II end input into resonance current just can.Also can carry out in 402 for implementing motion 3 described methods, resonance current sampling this moment can be taken out from the voltage-stabiliser tube stabling current of self-supporting power.
Fig. 4 is the control principle figure that voltage-controlled automatic frequency is adjusted.
4A is that source of stable pressure, 4B are that comparison amplifier, 4C are that voltage-controlled multivibrator, 4D are buffer among Fig. 4, and Vk is that output signal, Vh are resonance current voltage transformation signal, also voltage sampling or load current voltage signal sampled signal, and Vkk is a gate pole.
Fig. 5 is the series resonance applicating example, component 5A, 5B, 5C, 5D, 5E, 5F, 5G.
Fig. 5 A be Fig. 1 or Fig. 30 and 0 ' between connect the inductance L crosstalk and hold C, string fluorescent tube Rf; Rf is by R ' C ' series connection starter or other starting circuit.
Fig. 5 B is at 0 and 0 ' indirect high-frequency induction heating coil L
C is held in crosstalk.
Fig. 5 C is in 00 ' indirect motor winding L
C is held in crosstalk.
Fig. 5 D is 00 ' indirect high-frequency welding machine transformer L
gC is held in crosstalk, and Ls is the mutual inductance output winding of Lg.
Fig. 5 E holds C in 00 ' indirect inductance L crosstalk, and ultrasonic transducer X is attempted by the L two ends.
Fig. 5 F is at 00 ' indirect inductance L string X.
Fig. 5 G holds C, L in the elementary circle Lz crosstalk of 00 ' indirect variable depressor Bz
Be the mutual inductance output winding, two ends also meet X.
Fig. 6 is the applicating example figure of parallel resonance, contains component 6A, 6B, 6C, 6D, 6E, 6F, 6G.
Wherein L, L
, L
, L ' is inductance, C is an electric capacity, X is a transducer.
Fig. 6 A is 00 ' indirect L at Fig. 1 or Fig. 3
0Choke serially adds heat coil L
Or motor winding L
r, L
HTwo ends are in parallel with C.
Fig. 6 B is L
OConnect with the primary coil L of electric welding machine or high pressure generator, neon lamp power source, C is in parallel with L, and L ' is the mutual inductance output winding.
Fig. 6 C is L
0Connect with L, transducer X is in parallel with L.
Fig. 6 D is L
0Connect with L, connect with fluorescent tube Rf again, C and at the two ends of L and Rf, C ' is the starting circuit of connecting with R '.
Fig. 6 E is L
0Connect with L, C is in parallel with L, and X is in parallel with C.
Fig. 6 F is L
0Connect with L, C is in parallel with L, and L ' mutual inductance transfers to X.
Fig. 6 G is L
0Connect with L, C is in parallel with L, and L ' is the Switching Power Supply output winding, meets rectification filter circuit CL, and defeated Vz, Vz add that to cause the PWM input signal be the Vkk signal.
Fig. 7 is respectively tandem tap Ax, Ax ' and Ay, Ay ' and Az, Az ' and series capacitance C
A, C
BTogether be connected to 1 liang of power supply, as above the serial connection point is followed successively by Px, Py, Pz, 0, at PxO and PyO and PzO output three-phase, the Vk of basic control circuit 401 is coupled to the control utmost point of Ax ', Ax, and 205,206 are respectively y, the z phase control circuit, their input is with meeting Vk, exports Vky, Vkz control signal through 120 ° and 240 ° of frequency-tracking phase shifts respectively, is coupled to Ay, Ay ' and Az, Az ' respectively.208 is two comparison amplifiers, V
△Be triangle circulation signal input part, V
φBe neutral line electric wire input, input 208 is relatively amplified respectively, is input to 207 and handles output signal V
QSo that connect, adjust 205 phase shift skew with 205 phase shifters."=" expression isolation coupling among the figure, Fig. 8 too.
Fig. 8 is the resonance convertor assembly basic principle figure of three-phase six lines output.Among the figure with regard to unsteady flow switch Bx
1, Bx
2, Bx
3, Bx
4And By
1, By
2, By
3, By
4And Bz
1, Bz
2, Bz
3, Bz
4Forming x, y, z phase bridge-type convertor circuit respectively, is Vccx, Vccy, Vccz with power supply respectively.X, y, z go out to be Ox, Ox ' and Oy, Oy ' and Oz, Oz ', Bx mutually respectively
1, Bx
4And Bx
3, Bx
2, and By
1, By
4And By
3, By
2, and Bz
1, Bz
4And Bz
3, Bz
2Be respectively homophase control, its control end is respectively Bx, Bx ', By, By ', Bz, Bz ', 401 as Fig. 2 principle, output Vk is coupled to Bx ', and to Bx, 205,206 as described in Figure 6 through the Fx coupled in reverse wi for Vk, By ', Bz ', By ', Bz ' are coupled in output respectively, anti-phase through Fy, Fz respectively, be coupled to By, Bz respectively, 207,208 as described in Figure 6.Vccx, Vccy, Vccz are three-phase rectifier power source respectively.
Fig. 7,8 is all applicable to high-frequency motor, and at this moment, winding and its shunt capacitance are at any time, all be in resonance or connect very much resonance condition, thereby the power factor (PF) height, also can be used for electric welding machine, principle is identical, their difference output circuit connection such as Fig. 5 .6 00 ' between circuit.
But power Vcc, Vccx, Vccy, Vccz DC power supply, rectification High frequency filter power supply, High Power Factor rectifier power source, also stabilized voltage power supply, also continuous current source.
Resonance frequency bearing calibration: with standard frequency and actual vibration rate input phase demodulation (frequently) device, or the frequency comparator of rest-set flip-flop formation, output is amplified through integration, the size of the switching capacity of control resonant circuit and the variable inductance of making according to the magnetic amplifier principle, thereby emending frequency.Because when some requires as heating, a best heating Frequency point etc. should be arranged.
Control the designed circuit of each method according to this, can be made into solid modules circuit or thick film IC or application-specific integrated circuit (ASIC).
Claims (10)
1, method for controlling resonance power conversion is to do conduction angle control to wiping the unsteady flow switch element that shakes, and it is characterized in that:
A, resonance current is taken a sample or sensing gained signal I
hObtain V through no phase shift or in-phase voltage conversion
h, again with V
hBe shaped to homophase square wave V
HfIntegration or be filtered into nearly sine wave and become the signal V that amplitude is not influenced by load and power-supply ripple
h', again with V
h' add the Schmidt trigger voltage comparator and handle and be transformed into and I
hThe square wave V that given phase relation is arranged
SfUse V again
AfThe multivibrator more much lower than resonance frequency that desynchronizes, the gate pole of multivibrator or reset terminal are V
Kk, its output or the control signal V that exports through buffering
kThe unsteady flow switch element of resonance convertor assembly is done conduction angle control.
B, to V
h' (or V
h)-V
AfConversion be utilization Schmidt trigger voltage comparator, by applying solid comparison threshold values or changing the relatively size of threshold values, just can realize V with load current or voltage
aWith I
hFixed lead or hysteresis phase shift, or with the automatically leading or hysteresis phase shift of load current or change in voltage, thereby make the resonance unsteady flow be in nearly resonance or and complete resonance keep a fixing phase shift or away from resonance with changing between the resonance fully, make load current or voltage obtain adjustment.
2, method for controlling resonance power conversion is to the control of resonance unsteady flow switch element conduction angle, it is characterized in that:
A, be resonance current or the shunting resonance current directly carry out the even voltage multiplying rectifier, obtain the self-supporting power of a symmetric double voltage as subordinate, the sine-square wave voltage of transformation V of the resonance current that two aspects obtain from the voltage multiplying rectifier diode two ends that are connected on the self-supporting power negative pole on the one hand
Use V
The multivibrator more much lower than resonance frequency that desynchronizes, (gate pole or reset terminal are V
Ratio) multivibrator output or through buffering output V
kSignal removes to control the switch element of resonance convertor assembly.
B, on the multiplication of voltage diode and a fixed capacity, can make V
kWith V
A fixing hysteresis phase shift is arranged.
C, on the multiplication of voltage diode and a R
zC
pPhase shifter, R
zBut be the three-terminal element of variable resistor element such as photoelectrical coupler MCD521 or two-way operation,, its resistance changed automatically, with signal at R by the control of load sampled signal curtage
With fixed capacity C
pTie point get V
Phase shift signal V
p, the multivibrator that desynchronizes makes output V
kWith V
Automatically hysteresis phase shift.
D, press on the diode and a RC at letter
xPhase shifter is with the sampling current or the voltage change C of load
x, can obtain V
kWith V
Automatic hysteresis phase shift.
E, also can be V
Remove to trigger a rest-set flip-flop or directly amplify output V by gate circuit
kSignal.
3, method for controlling resonance power conversion is that resonance unsteady flow switch element is done conduction angle control, it is characterized in that: take a sample in load current or the voltage signal and the reference voltage relative error amplification output voltage V of load current or voltage signal or equivalence
, use V
Control pressure-controlled voltage perhaps directly with load signal control piezoelectricity control voltage, is perhaps directly used V
As voltage-controlled voltage, control a voltage-controlled astatic multivibrator, multi resonant shake the frequency of device is changed, thereby adjust load current or voltage, make resonance current or voltage reach constant or limit.
4, method for controlling resonance power conversion is that resonance unsteady flow switch element is done conduction angle control, it is characterized in that: on the common magnetic circuit core of two magnetic loop magnetic cores of a common magnetic circuit or iron core around the mutual inductance secondary coil, allow secondary voltage drive the unsteady flow switch element, after the series connection of mutual inductance primary coil, sealing in load current or shunting load current or resonance current on other the two independent magnetic circuit cores respectively again, and the magnetic flux that these two coils are produced on the common magnetic circuit core is opposite, on an independent magnetic circuit core around control coil, the load current of sampling or voltage signal are adjusted element through relatively amplifying rear drive control, absorb the energy on the control coil, the magnetic flux that the primary coil at control coil place is produced on common magnetic circuit changes, thereby change secondary output current or voltage, thereby make the conduction angle of unsteady flow switch adjust output current or voltage automatically, make output variable reach stable or qualification.
5, method for controlling resonance power conversion is that resonance unsteady flow switch element is done conduction angle control, it is characterized in that: directly on the instrument transformer that current feedback drives around control coil, relatively amplify rear drive with load current of taking a sample or voltage signal and control the energy of adjusting on the element absorption control coil, reach conduction angle control thereby change secondary output current, make output current or voltage obtain adjusting or limiting.
6, method for controlling resonance power conversion is that resonance unsteady flow switch element is done conduction angle control, it is characterized in that: according to the drive principle of CR timing inverter, with equivalent resistance controllable elements such as replacements such as triode, field effect transistor, the load current of sampling or voltage ratio are amplified these element equivalent resistances of rear drive and are changed and reach the control of conduction angle the timing resistor element.
7, method for controlling resonance power conversion is the feedback method to resonant energy, it is characterized in that: the may command inductance that is made into according to the magnetic amplifier principle is improved couples back element in power factor, current harmonics and the output crest coefficient method as the present invention, the control coil of may command inductance is by the load current or the voltage control of sampling, its inductance value is changed, also respective change is measured in the coupling that feeds back to power supply, thus adjustable speed or restriction output current or voltage.
8, method for controlling resonance power conversion is the resonance unsteady flow control that is applied to three-phase, it is characterized in that: the resistive time constant element of three-phase signal generator is replaced with controllable triode of equivalent resistance or field effect transistor, controlling it with load current of sampling or voltage signal changes, constitute voltage-controlled three-phase signal generator, make the output signal control three-phase bridge unsteady flow switch element of generator, and when parallel resonance is used, desynchronize and the pairing phase place of three-phase signal generator with a certain resonance current signal that is in parallel.
9, the resonance unsteady flow control device that method for controlling resonance power conversion constituted, it is characterized in that: the peak region resonant energy is fed back on the power supply making it rectification around feedback coil on the resonant inductance, perhaps two series capacitances are attempted by on the power supply, as resonant capacitance or a part of resonant capacitance, simultaneously on power supply and connect a rectification half-bridge, be connected with the serial or parallel connection circuit of inductance with an electric capacity or inductance or electric capacity between the input that makes the rectification half-bridge and the serial connection point of two series capacitances, as couples back, make two series capacitances feed back to power supply in the peak region resonance potential rectification at two ends respectively, to improve the power factor of supply and AC circuit, current harmonics and output crest factor.
10, the resonance convertor assembly that is constituted according to claim 1,2,3,4,5,6,7,8,9 described methods is characterized in that: ballast or constant current or current limliting, neon lamp power source and high pressure generator and the resonance transform Switching Power Supply that can use high-frequency welding machine, supersonic generator, high-frequency induction heating, fluorescent lamp and gaseous discharge lamp.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 93121000 CN1104002A (en) | 1993-12-15 | 1993-12-15 | Method for controlling resonance power conversion |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 93121000 CN1104002A (en) | 1993-12-15 | 1993-12-15 | Method for controlling resonance power conversion |
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| Publication Number | Publication Date |
|---|---|
| CN1104002A true CN1104002A (en) | 1995-06-21 |
Family
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN 93121000 Pending CN1104002A (en) | 1993-12-15 | 1993-12-15 | Method for controlling resonance power conversion |
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| CN100464489C (en) * | 2005-09-26 | 2009-02-25 | 艾默生网络能源有限公司 | Control of resonant circuit output characteristics and resonant circuit |
| CN105302033A (en) * | 2015-11-27 | 2016-02-03 | 成都聚汇才科技有限公司 | Electricity meter anti-interference adaptable control system based on anti-interference resonant signal identification circuit |
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| CN105302033A (en) * | 2015-11-27 | 2016-02-03 | 成都聚汇才科技有限公司 | Electricity meter anti-interference adaptable control system based on anti-interference resonant signal identification circuit |
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