CN109842182A - Power supply system - Google Patents
Power supply system Download PDFInfo
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- CN109842182A CN109842182A CN201910135525.9A CN201910135525A CN109842182A CN 109842182 A CN109842182 A CN 109842182A CN 201910135525 A CN201910135525 A CN 201910135525A CN 109842182 A CN109842182 A CN 109842182A
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
This disclosure relates to a kind of power supply system, the system comprises: current source power factor converting device PFC is electrically connected to external power supply, converts electric current and voltage of transformation for receiving the electric energy of external power supply, and according to required power output；Adjustable gain converter, it is electrically connected to current source PFC and load, for receiving the load voltage of load, and utilizes the gain of load voltage adjustment adjustable gain converter, to export supply voltage using voltage of transformation and gain, and utilize transformation electric current and gain output supply current；Feedback controller is electrically connected to the load and the current source PFC, adjusts the transformation electric current for the load current and target current of receiving stream overload, and according to load current and the target current.By system above, the disclosure can be controlled transformation electric current, voltage of transformation can be made to be clamped in the range of setting, power supply system is expeditiously worked in wide output voltage range with firm power.
Description
Technical field
This disclosure relates to power technique fields more particularly to a kind of power supply system.
Background technique
It is well known that battery boosting technology becomes the key for restricting new energy development with the development and application of new energy
Element, electric car (EV) are one of most important new energy applications, and different EV is equipped with the battery of different capacity and voltage.
The battery pack of EV has different voltage levels, for example, small passenger car is usually using A-battery group, and bus is usual
Use high-tension battery group.Cell voltage can be swung between the wide scope of deep discharge conditions to fully charged state (for example,
Voltage range can be from 330V to 750V).In order to reduce the battery charge time of charging equipment, the charging equipment of charging station needs
Worked in full voltage range with constant power-mode, if it is necessary to meet the requirements, charging equipment may become it is very expensive and
It is heavy.
In the related art, most of PFC topologys used are Vienna three-phase voltage increasing converters, DC/DC grade be LLC with
Phase shift converter.And PFC and DC/DC grades is independent control, this control needs large-sized DC capacitor, and cannot be in system
It is advantageous that institute is obtained in rank.In addition, in low-voltage output DC/DC grades must work under low-down duty ratio, or
Increase substantially the switching frequency of LLC converter.Power consumption when these methods export low pressure increases.To solve the problems, such as this, one
A little schemes mechanically switch winding connection using high power relay to adapt to wide output voltage range, it is apparent that it is increased
Cost simultaneously occupies big quantity space.
Therefore, it is badly in need of proposing a kind of new technical solution, can realizes the perseverance of wide-voltage range in the level of topology and system
Determine the power conversion of power efficient.
Summary of the invention
In view of this, the present disclosure proposes a kind of power supply system, the system comprises:
Current source power factor converting device PFC, is electrically connected to external power supply, for receiving the electric energy of the external power supply,
And electric current and voltage of transformation are converted according to required power output；
Adjustable gain converter is electrically connected to the current source PFC and load, for receiving the load electricity of the load
It presses, and adjusts the gain of the adjustable gain converter using the load voltage, to utilize the voltage of transformation and the increasing
Benefit output supply voltage, and supply current is exported using the transformation electric current and the gain；
Feedback controller is electrically connected to the load and the current source PFC, the load current for receiving stream overload
And target current, and the transformation electric current is adjusted according to the load current and the target current.
In a kind of possible embodiment, the adjustable gain converter includes the first full-bridge circuit, the second full-bridge electricity
Road, the first secondary circuit and second subprime circuit, first full-bridge circuit is connected in series in second full-bridge circuit, described
First secondary circuit is coupled to first full-bridge circuit, and the second subprime circuit is coupled to second full-bridge circuit, institute
The gain for stating adjustable gain converter is by changing the phase in-migration tune between first full-bridge circuit and the second full-bridge circuit
Whole.
In a kind of possible embodiment, first full-bridge circuit includes the first transistor, second transistor, third
Transistor, the 4th transistor and the first armature winding, the first end of the first transistor are electrically connected to the current source PFC's
The first end of one output end and the third transistor, the second end of the first transistor are electrically connected to the second transistor
First end and first armature winding first end, the second end of the third transistor is electrically connected to the 4th crystal
The second end of the first end of pipe and first armature winding, it is brilliant that the second end of the second transistor is electrically connected to the described 4th
The second end of body pipe.
In a kind of possible embodiment, second full-bridge circuit includes the 5th transistor, the 6th transistor, the 7th
The first end of transistor, the 8th transistor and the second armature winding, the 5th transistor is electrically connected to the 7th transistor
First end, the second end of the 5th transistor be electrically connected to the 6th transistor first end and it is described second it is primary around
The first end of group, the second end of second armature winding are electrically connected to the second end of the 7th transistor and described 8th brilliant
The first end of body pipe, the second end of the 6th transistor are electrically connected to another output end and described of the current source PFC
The second end of eight transistors.
In a kind of possible embodiment, first secondary circuit includes the first rectification circuit and the second rectified current
Road, the second subprime circuit include third rectification circuit and the 4th rectification circuit, in which:
Positive half-wave of first rectification circuit for first full-bridge circuit rectifies；
Second rectification circuit is used for the negative halfwave rectifier of first full-bridge circuit；
Positive half-wave of the third rectification circuit for second full-bridge circuit rectifies；
4th rectification circuit is used for the negative halfwave rectifier of second full-bridge circuit.
In a kind of possible embodiment, first secondary circuit includes the first secondary windings, first diode, the
Two diodes, the second subprime circuit include second subprime winding, third diode, the 4th diode, first grade
Circuit and the second subprime circuit all include the 5th diode and the 6th diode, and first rectification circuit includes described
One diode and the 5th diode, second rectification circuit include second diode and the 6th diode,
The third rectification circuit includes the third diode and the 5th diode, and the 4th rectification circuit includes described
Four diodes and the 6th diode, in which:
The first end of first secondary windings is electrically connected to the anode and second diode of the first diode
Cathode, the cathode of the first diode is electrically connected to the cathode of the third diode and the cathode of the 5th diode；Institute
The anode for stating third diode is electrically connected to the first end of the second subprime winding and the cathode of the 4th diode；It is described
The second end of second subprime winding is electrically connected to the anode and the six or two of the second end of first secondary windings, the 5th diode
The cathode of pole pipe, the anode of the 4th diode are electrically connected to the anode of second diode and the sun of the 6th diode
Pole.
In a kind of possible embodiment, first rectification circuit and the third rectification circuit are configured as two
Staggered power rectifier, and/or
Second rectification circuit and the 4th rectification circuit are configured as two staggered power rectifiers.
In a kind of possible embodiment, first secondary circuit and second subprime circuit also include the first electricity jointly
Sense and the second inductance, in which:
The first end of first inductance is electrically connected to the cathode of the cathode of the first diode, the third diode
And the cathode of the 5th diode, the first end of second inductance are electrically connected to the anode, described of the 6th diode
The anode of the anode of second diode and the 4th diode；The of the second end of first inductance and second inductance
Two ends are for exporting the supply voltage and supply current.
In a kind of possible embodiment, the adjustable gain converter further includes first capacitor, the second capacitor, described
The first end of first capacitor is electrically connected to the second end of first inductance, and the second end of the first capacitor is electrically connected to described
The second end of the first end of second capacitor, the second end of first secondary windings and the second subprime winding；Described second
The second end of capacitor is electrically connected to the second end of second inductance.
In a kind of possible embodiment, in first full-bridge circuit and/or the duty of second full-bridge circuit
Than be less than or equal to 50% when, by adjusting first full-bridge circuit and second full-bridge circuit phase shift or pass through pulse
Width modulated PWM adjusts the gain.
In a kind of possible embodiment, in first full-bridge circuit and/or the duty of second full-bridge circuit
When than being equal to 50%, the increasing is adjusted by adjusting the phase in-migration between first full-bridge circuit and second full-bridge circuit
Benefit.
It is described by adjusting first full-bridge circuit and second full-bridge circuit in a kind of possible embodiment
Between phase in-migration adjust the gain, comprising:
The phase shift is determined by following formula:
β=180 ° * ((Vo-V1)/(V2-V1)), wherein β indicates the size of the phase shift, and Vo indicates the load electricity
Pressure, V1 indicate the minimum value of the load voltage, and V2 indicates the maximum value of the load voltage.
In a kind of possible embodiment, the adjustable gain converter further include: third capacitor and the 4th capacitor, institute
The first end for stating third capacitor is electrically connected to one end of the current source PFC, and the second end of the third capacitor is electrically connected to institute
State the first end of the 4th capacitor and the tie point of the first full-bridge circuit and the second full-bridge circuit, the second end electricity of the 4th capacitor
It is connected to the other end of the current source PFC.
In a kind of possible embodiment, the feedback controller includes operational amplifier and current loop compensator,
For receiving the load current, the second end of the operational amplifier is used for the first end of the operational amplifier
Receive the target current；
The current loop compensator is electrically connected to the first end and output end of the operational amplifier, for according to
The load current of operational amplifier output and the comparison result of the target current are to described in current source PFC output
Transformation electric current is adjusted to adjust the supply current.
According to another aspect of the present disclosure, a kind of charging equipment is proposed, the charging equipment includes the power supply system
System.
The disclosure is by phase shifting control, and the series connection and parallel connection for realizing the output of two open loop transition devices of adjustable gain converter are even
It connects and the electrodeless adjustment of output voltage.According to the power supply system framework of the disclosure and new adjustable gain converter topologies,
Inverter power density can be increased substantially, magnetic element is made full use of, reduces the current stresses of semiconductor devices, it can be in width
Output voltage range keep good power conversion efficiency.
By system above, the transformation that the disclosure can export current source PFC according to the target current needed for load is electric
Stream is controlled, and transformation of the gain of adjustable gain converter to make current source PFC export can be adjusted according to load voltage
Voltage is clamped in the range of setting, allow power supply system with firm power the high efficiency in wide output voltage range
Ground work.
According to below with reference to the accompanying drawings to detailed description of illustrative embodiments, the other feature and aspect of the disclosure will become
It is clear.
Detailed description of the invention
Comprising in the description and constituting the attached drawing of part of specification and specification together illustrates the disclosure
Exemplary embodiment, feature and aspect, and for explaining the principles of this disclosure.
Fig. 1 shows the schematic diagram of the power supply system according to one embodiment of the disclosure.
Fig. 2 a shows the schematic diagram of current source PFC and adjustable gain converter according to one embodiment of the disclosure.
Fig. 2 b shows the another signal of current source PFC and adjustable gain converter according to one embodiment of the disclosure
Figure.
Fig. 3 is shown according to the input of the three-phase voltage of the external power supply of one embodiment of the disclosure, three-phase current and electric current
The waveform diagram of the transformation electric current of source PFC output.
Fig. 4 shows the phase according to one embodiment of the disclosure-supply voltage-voltage of transformation corresponding relationship signal
Figure.
Fig. 5 shows the schematic diagram of the adjustable gain converter according to one embodiment of the disclosure.
Fig. 6 shows the schematic diagram according to each waveform in one embodiment of the disclosure in adjustable gain converter.
Fig. 7 a shows the schematic diagram according to the first full-bridge circuit and the first secondary circuit in one embodiment of the disclosure, figure
7b shows the control schematic diagram to the first full-bridge circuit according to one embodiment of the disclosure.
Fig. 8 a, which is shown, is less than or equal to 0.5 according to the gain of adjustable gain converter 20 in one embodiment of the disclosure
When, the duty ratio of the first full-bridge circuit Phase A and/or the second full-bridge circuit Phase B are less than or equal to control when 50%
Schematic diagram, when Fig. 8 b is shown according to the gain of adjustable gain converter 20 in one embodiment of the disclosure more than or equal to 0.5,
The Phaseshift controlling schematic diagram of first full-bridge circuit Phase A and the second full-bridge circuit Phase B.
The control signal schematic representation of Fig. 9 each transistor when showing between the gain 0-1 of adjustable gain converter.
Specific embodiment
Various exemplary embodiments, feature and the aspect of the disclosure are described in detail below with reference to attached drawing.It is identical in attached drawing
Appended drawing reference indicate element functionally identical or similar.Although the various aspects of embodiment are shown in the attached drawings, remove
It non-specifically points out, it is not necessary to attached drawing drawn to scale.
Dedicated word " exemplary " means " being used as example, embodiment or illustrative " herein.Here as " exemplary "
Illustrated any embodiment should not necessarily be construed as preferred or advantageous over other embodiments.
In addition, giving numerous details in specific embodiment below to better illustrate the disclosure.
It will be appreciated by those skilled in the art that without certain details, the disclosure equally be can be implemented.In some instances, for
Method, means, element and circuit well known to those skilled in the art are not described in detail, in order to highlight the purport of the disclosure.
Referring to Fig. 1, Fig. 1 shows the schematic diagram of the power supply system according to one embodiment of the disclosure.
As shown in Figure 1, the system comprises:
Current source power factor converting device PFC 10, is electrically connected to external power supply 50, for receiving the external power supply 50
Electric energy, and electric current and voltage of transformation are converted according to required power output；
Adjustable gain converter 20 is electrically connected to the current source PFC 10 and load 40, for receiving the load 40
Load voltage, and the gain of the adjustable gain converter 20 is adjusted using the load voltage, with electric using the transformation
Pressure and the gain export supply voltage and export supply current using the transformation electric current and the gain；
Feedback controller 30 is electrically connected to the 40 and current source PFC 10 of the load, is used for receiving stream overload 40
Load current and target current, and the exchanging electric current is adjusted according to the load current and the target current.
By system above, the transformation that the disclosure can export current source PFC according to the target current needed for load is electric
Stream is controlled, and transformation of the gain of adjustable gain converter to make current source PFC export can be adjusted according to load voltage
Voltage is clamped in the range of setting, allow power supply system with firm power the high efficiency in wide output voltage range
Ground work.
In a kind of possible embodiment, the external power supply 50 can be AC power source, and the AC power source can be with
It is three-phase input.In other implementations, external power supply 50 is also possible to DC power supply or other suitable power supplys, this
It discloses without limitation.
In a kind of possible embodiment, the load 40 can be the battery pack of electric car EV, be also possible to it
The battery pack of his unit.
In a kind of possible embodiment, the gain can be equivalent to the no-load voltage ratio (turn ratio) of transformer.
In a kind of possible embodiment, the feedback controller 30 may include operational amplifier 32 and current loop
Compensator 31,
The first end of the operational amplifier 32 is used for receiving the load current, the second end of the operational amplifier
In reception target current；
The current loop compensator 31 is electrically connected to the first end and output end of the operational amplifier 32, is used for basis
The operational amplifier 32 compensates the comparison result of the load current and the target current through current loop compensator 31
Afterwards, the current source power factor converting device PFC 10 is controlled, to adjust the transformation electric current.
In a kind of possible embodiment, operational amplifier 32 and current loop included by the feedback controller 30
Compensator 31 can be realized with digital circuit or digital operation.
In a kind of possible embodiment, the target current can be the reference current that load 40 is charged
Or current-order.
For example, when load current is less than target current, current loop compensator can increase the value of switching current,
So that the supply electric current of output moves closer to the target current.When load current is greater than target current, current loop
Compensator can also do reduction processing to switching current, so that the supply circuit of output is gradually reduced, close to the mesh
Mark electric current.
Current loop compensator 31 can design according to the actual situation, specific knot of the disclosure to current loop compensator 31
Structure does not walk limitation.
It should be understood that, above description is exemplary, and is not considered as the limitation to the disclosure.
Fig. 2 a is please referred to, Fig. 2 a shows the current source PFC and adjustable gain converter according to one embodiment of the disclosure
Schematic diagram.
As shown in Figure 2 a, when the electric energy of input is three-phase alternating current, the current source PFC 10 may include inductance LA, LB
And one end of LC, transistor Q1-Q6, inductance LA receive A phase alternating current, the other end of inductance LA is electrically connected to the source of transistor Q1
The drain electrode of pole and transistor Q2.One end of inductance LB receives B phase alternating current, and the other end of inductance LB is electrically connected to transistor Q3's
The drain electrode of source electrode and transistor Q4.One end of inductance LC receives C phase alternating current, and the other end of inductance LC is electrically connected to transistor Q5
Source electrode and transistor Q6 drain electrode.The drain electrode of transistor Q1, transistor Q3 and transistor Q5 are electrically connected, transistor Q2, crystal
The grid of the source electrode of pipe Q4 and transistor Q6 ground connection, transistor Q1- transistor Q6 is believed for receiving control signal, and according to control
It number is turned on or off, to carry out electric energy adjustment.
In a kind of possible embodiment, the current source PFC 10 can be used for boosting in the alternating current of input
(boost), for example, alternating current can be increased to by current source PFC 10 from 380V when the alternating current of input is three-phase 380V
Direct current 660V (Vbus voltage) or other voltage values.
It is shown also referring to Fig. 3, Fig. 3 defeated according to the three-phase voltage of the external power supply 50 of one embodiment of the disclosure
Enter, the waveform diagram of the transformation electric current of three-phase current and current source PFC output.
As shown in figure 3, the horizontal axis of Fig. 3 can indicate time interval, three vertical axises respectively indicate three-phase electricity from top to bottom
Press the transformation electric current of input, three-phase current, output.
As shown in figure 3, it is same phase transformation that the voltage Va and electric current ia of phase a, which are same phase change, the voltage Vb of phase b and electric current ib,
Voltage Vc and electric current ic change, phase c are same phase changes.The transformation electric current of current source PFC10 output has minimum ripple,
The ripple for converting electric current is less than the 10% of average current, and ripple frequency is 6 times of the frequency of the alternating current of input.
For example, the ac frequency of external power supply input can be in 50Hz between 60Hz, correspondingly, the frequency of ripple can
With in 300Hz between 360Hz.Since the battery pack of load has the characteristic of bulky capacitor, battery pack can be with several
It charges under the electric current of hundred Hz frequency small magnitude (such as less than 10%) ripples.Also, in some possible embodiments, may be used
To be filtered using lesser capacitor, compared in the related technology utilize bulky capacitor (electrolytic capacitor) be filtered, the disclosure
Space can be greatly saved, to optimize circuit structure and reduce cost, this point be will be described herein-after.
It is to be understood that being exemplary above to the description of current source PFC 10, current source PFC is also possible to other
Circuit structure, such as Vienna three-phase PFC, the disclosure do not limit this.
With continued reference to Fig. 2 a, in a kind of possible embodiment, the adjustable gain converter 20 may include first
Full-bridge circuit Phase A, the second full-bridge circuit Phase B, the first secondary circuit and second subprime circuit, the first full-bridge electricity
Road Phase A is connected in series in the second full-bridge circuit Phase B, and first secondary circuit is coupled to first full-bridge
Circuit, the second subprime circuit are coupled to second full-bridge circuit, and the gain of the adjustable gain converter 20 is to pass through
Change the phase in-migration adjustment between the first full-bridge circuit Phase A and the second full-bridge circuit Phase B.
In a kind of possible embodiment, first secondary circuit is coupled to the first full-bridge circuit Phase A,
At this point, the first secondary circuit and the first full-bridge circuit Phase A can be considered as a commutator transformer.Similarly, described second
Grade circuit is coupled to the second full-bridge circuit Phase B, and second subprime circuit and the second full-bridge circuit Phase B can also at this time
To be considered as a commutator transformer.
In a kind of possible embodiment, " coupling " described above can be magnetic coupling.
In a kind of possible embodiment, the first full-bridge circuit Phase A may include the first transistor Q1a,
Second transistor Q2a, third transistor Q3a, the 4th transistor Q4a and the first armature winding T1a, the first transistor Q1a
First end be electrically connected to an output end of the current source PFC 10 and the first end of the third transistor Q3a, described
The second end of one transistor Q1a be electrically connected to the second transistor Q2a first end and the first armature winding T1a
One end, the second end of the third transistor Q3a are electrically connected to the first end and first primary of the 4th transistor Q4a
The second end of winding T1a, the second end of the second transistor Q2a are electrically connected to the second end of the 4th transistor Q4a.
In a kind of possible embodiment, the first transistor Q1a, second transistor Q2a, third transistor Q3a,
The first end of 4th transistor Q4a can be drain electrode, the first transistor Q1a, second transistor Q2a, third transistor Q3a,
The second end of four transistor Q4a can be source electrode.It is to be understood that in actual use scene, the transistor that is mentioned above
It can be MOSFET, IGBT etc., when transistor is MOSFET, each end of transistor includes grid, source electrode, drain electrode；In crystal
When pipe is IGBT, each end may include collector, emitter, base stage.Therefore, the disclosure to the type of transistor with no restrictions,
Also, the disclosure to the first end of transistor, second end without limitation.
In a kind of possible embodiment, the second full-bridge circuit Phase B includes the 5th transistor Q1b, the 6th
Transistor Q2b, the 7th transistor Q3b, the 8th transistor Q4b and the second armature winding T1b, the of the 5th transistor Q1b
One end is electrically connected to the first end of the 7th transistor Q3b, and the second end of the 5th transistor Q1b is electrically connected to described
The first end of the first end of six transistor Q2b and the second armature winding T1b, the second end of the second armature winding T1b
It is electrically connected to the second end of the 7th transistor Q3b and the first end of the 8th transistor Q4b, the 6th transistor
The second end of Q2b is electrically connected to another output end of the current source PFC and the second end of the 8th transistor Q4b.
In a kind of possible embodiment, the 5th transistor Q1b, the 6th transistor Q2b, the 7th transistor Q3b,
The first end of 8th transistor Q4b can be drain electrode, the 5th transistor Q1b, the 6th transistor Q2b, the 7th transistor Q3b,
The second end of eight transistor Q4b can be source electrode.It is to be understood that in actual use scene, the source electrode of transistor, drain electrode
May be used interchangeably, therefore, the disclosure to the first end of transistor, second end without limitation.
In a kind of possible embodiment, an output end of the current source PFC 10 and transistor Q1, transistor Q3,
The drain electrode of transistor Q5 is connected, another output end and transistor Q2, transistor Q4 and transistor Q6 of the current source PFC 10
Source electrode be connected.
In a kind of possible embodiment, the first transistor Q1a, second transistor Q2a, third transistor Q3a,
4th transistor Q4a, the 5th transistor Q1b, the 6th transistor Q2b, the 7th transistor Q3b, the 8th transistor Q4b grid can
To control signal for receiving, and according to control signal conduction or disconnection.
In a kind of possible embodiment, the gain (i.e. equivalent duty ratio) of adjustable gain converter 20 is less than or equal to
When 50%, the first full-bridge circuit Phase A and the second full-bridge circuit Phase B duty ratio are again smaller than or equal to 50%
(duty ratio that can indicate commutator transformer voltage), at this time can by PWM (pulsewidth modulation) or the phase shifting control of itself come
The gain is adjusted, it is this to control the starting for being mainly used for DC/DC converter.If started with phase shifting control, described first
Full-bridge circuit Phase A and the second full-bridge circuit Phase B is usually to work in same-phase, i.e. their phase shift β=0 °,
With the increase of duty ratio, output voltage rises.When effective duty cycle reaches 50%, the first full-bridge circuit Phase
A and the second full-bridge circuit Phase B each work in full duty ratio, i.e., most efficient DC/DC transformer (commutator transformer)
Open loop mode of operation.
In a kind of possible embodiment, the gain (equivalent duty ratio) of adjustable gain converter 20 is equal to or more than
When 50%, by adjusting the phase in-migration tune between the first full-bridge circuit Phase A and the second full-bridge circuit Phase B
The whole gain.When the phase shift between them is zero degree (β=0 °), the first full-bridge circuit Phase A and described second
The output of full-bridge circuit Phase B is work in parallel connection；It is described when the phase shift between them is 180 degree (β=180 °)
The output of first full-bridge circuit Phase A and the second full-bridge circuit Phase B are work in series connection.Adjustable gain turns
The gain of parallel operation 20 can realize stepless gain adjustment by changing the phase shift between them.It is described in this embodiment
First full-bridge circuit Phase A and the second full-bridge circuit Phase B works in most efficient DC/DC transformer open loop operation mould
Formula.
It, can be by controlling the first transistor Q1a, second transistor Q2a, the in a kind of possible embodiment
Three transistor Q3a, the 4th transistor Q4a, the 5th transistor Q1b, the 6th transistor Q2b, the 7th transistor Q3b, the 8th crystal
Pipe Q4b conducting, turn-off time control between the first full-bridge circuit Phase A and the second full-bridge circuit Phase B
Phase shift.The first full-bridge circuit Phase A and the second full-bridge circuit Phase B can under different phases work
Make.
In a kind of possible embodiment, the first secondary circuit Phase A may include the first secondary windings
T1a, first diode D1a, the second diode D2a, the second subprime circuit Phase B include second subprime winding T1b,
Three diode D1b, the 4th diode D2b, first secondary circuit and the second subprime circuit all include the 5th diode
DF1 and the 6th diode DF2, in which:
The first end of the first secondary windings T1a is electrically connected to the anode and described second of the first diode D1a
The cathode of diode D1b, the cathode of the first diode D1a are electrically connected to the cathode and the 5th of the third diode D2a
The cathode of diode DF1；The anode of the third diode D2a be electrically connected to the second subprime winding T1b first end and
The cathode of the 4th diode D2b；The second end of the second subprime winding T1b is electrically connected to first secondary windings
The cathode of the second end of T1a, the anode of the 5th diode DF1 and the 6th diode DF2, the anode of the 4th diode D2b
It is electrically connected to the anode of the 6th diode DF2 of anode of the second diode D1b.
In a kind of possible embodiment, first diode D1a and the 5th diode DF1 form the first rectification circuit,
Positive half-wave for the first full-bridge circuit rectifies.Second diode D1b and the 6th diode DF2 forms the second rectification circuit, uses
In the negative halfwave rectifier of the first full-bridge circuit.Third diode D2a and the 5th diode DF1 forms third rectification circuit, is used for
The positive half-wave of second full-bridge circuit rectifies.4th diode D2b and the 6th diode DF2 form the 4th rectification circuit, for the
The negative halfwave rectifier of two full-bridge circuits.
It functionally divides, the first secondary circuit includes the first rectification circuit and the second rectification circuit, second subprime circuit
Including third rectification circuit and the 4th rectification circuit.
In a kind of possible embodiment, first rectification circuit and the third rectification circuit are configured as two
Staggered power rectifier, and/or
Second rectification circuit and the 4th rectification circuit are configured as two staggered power rectifiers.
In a kind of possible embodiment, first secondary circuit and the second subprime circuit also include the jointly
One inductance Lo1 and the second inductance Lo2, in which:
The first end of the first inductance Lo1 is electrically connected to the cathode of the first diode D1a, third diode D2a
Cathode and the 5th diode DF1 cathode, the first end of the second inductance Lo2 is electrically connected to the 6th diode
The anode of the anode of DF2, the anode of the second diode D1b and the 4th diode D2b, the first inductance Lo1's
Second end and the second end of the second inductance Lo2 are for exporting the supply voltage and supply current.
In a kind of possible embodiment, the adjustable gain converter 20 further includes first capacitor Co1, the second capacitor
Co2, the first end of the first capacitor Co1 are electrically connected to the second end of the first inductance Lo1, the first capacitor Co1's
Second end is electrically connected to the first end and the first secondary windings T1a and second subprime winding T1b of the second capacitor Co2
Second end, the second end of the second capacitor Co2 are electrically connected to the second end of the second inductance Lo2.
In a kind of possible embodiment, the capacitor of the first capacitor Co1 and the second capacitor Co2 can be small
Capacitor can be used for absorbing high-frequency switching currents ripple, electric relative to line frequency is eliminated using big electrolytic capacitor in the related technology
Flow liner wave, the disclosure can greatly reduce the area of component occupancy, to optimize circuit structure, and significantly reduce cost.
It is described by adjusting first full-bridge circuit and second full-bridge circuit in a kind of possible embodiment
Between phase in-migration adjust the gain, may include:
The phase shift is determined by following formula:
β=180 ° * ((Vo-V1)/(V2-V1)), wherein β indicates the size of the phase shift, and Vo indicates the load electricity
Pressure, V1 indicate the minimum value of the load voltage, and V2 indicates the maximum value of the load voltage.
In a kind of possible embodiment, the phase shift can be the second full-bridge circuit relative to the first full-bridge circuit
Phase difference.
Referring to Figure 4 together, Fig. 4 shows phase-supply voltage-voltage of transformation according to one embodiment of the disclosure
Correspondence diagram.
In Fig. 4 example, the minimum value V1 of load voltage is 330V, and the maximum value V2 of load voltage is 750V, load voltage
Vo can change between 330V-750V.In this case, the determination formula of phase shift can be with are as follows:
β=180 ° * ((Vo-330)/420).
After obtaining load voltage Vo, so that it may determine the first full-bridge circuit Phase A and second according to above formula
Phase shift between full-bridge circuit Phase B.Wherein, the first full-bridge circuit Phase A and the second full-bridge circuit Phase B can be by
It is configured to work under same phase, at this point, the first full-bridge circuit Phase A and the second full-bridge circuit Phase B is 0 ° of phase shift,
In this case, with the first full-bridge circuit Phase A coupling the first secondary circuit and with the second full-bridge circuit Phase B coupling
The second subprime circuit in parallel connect connects, at this time power supply system output HIGH current, low-voltage.First full-bridge circuit Phase A and
Second full-bridge circuit Phase B can be configured as to work under opposite phase, at this point, the first full-bridge circuit Phase A and
Two full-bridge circuit Phase B are 180 ° of phase shifts, in this case, first grade with the first full-bridge circuit Phase A coupling
Circuit and the second subprime circuit coupled with the second full-bridge circuit Phase B are connected in series, the low current of power supply system output at this time,
High voltage.
For example, when load voltage Vo is 330V, the first full-bridge circuit Phase A and the second full-bridge circuit Phase
B is configured as working under identical phase.When load voltage Vo is 750V, the first full-bridge circuit Phase A and second is complete
Bridge circuit Phase B is configured as working under opposite phase, at this point, the phase difference of the two is 180 °.
When load voltage Vo is when 330V is between 750V, above method can also be passed through and obtain the first full-bridge circuit
Phase shift β between Phase A and the second full-bridge circuit Phase B is adjusted with the gain to adjustable gain converter.At this
In the case of kind, the first secondary circuit, second subprime circuit can be considered as part in parallel connection, sections in series connection.In this way
Control, in the range of the voltage of transformation that current source PFC can be exported is limited in needs, to improve the work of power supply system
Efficiency.
After the phase shift between the first full-bridge circuit Phase A and the second full-bridge circuit Phase B has been determined, so that it may
To the equivalent turn ratio N (N=f (Vo) as shown in Figure 1) of adjustable gain converter 20.
It is to be understood that load voltage Vo described in the disclosure can be load 40 it is initial when the charging voltage that needs,
It is also possible to load 40 supply voltage received during the charging process, when charging to the battery pack of load 40, bears
The voltage for carrying 40 battery pack can gradually rise, for example, it may be possible to it is increased to 420V or so from 330V or so within 1-2 hour,
Therefore load voltage has dynamic change procedure.
From fig. 4, it can be seen that can determine the first full-bridge circuit Phase A and the second full-bridge circuit according to load voltage V
Phase shift between Phase B, it is also possible to obtain the size for the voltage of transformation that current source PFC 10 needs to export.
For example, the voltage bus of current source PFC can be defeated when the turn ratio on the secondary side of the original of transformer T1a and T1b is 1:1
Voltage of transformation out can be with are as follows:
Vbus=660+90* (Vo-330)/420.
As can be seen that the voltage on voltage bus Vbus can be in the range of 600V to 750V.
It is to be understood that above description is exemplary, it is not considered that above description is the limitation to the disclosure.
Please continue to refer to Fig. 2 a, in a kind of possible embodiment, the adjustable gain converter 20 can also include:
The first end of third capacitor Ca and the 4th capacitor Cb, the third capacitor Ca are electrically connected to one end of the current source PFC 10,
The second end of the third capacitor Ca is electrically connected to the first end and the first full-bridge circuit Phase B and of the 4th capacitor Cb
The tie point of two full-bridge circuit Phase B, the second end of the 4th capacitor Cb are electrically connected to the another of the current source PFC 10
One end.
In a kind of possible embodiment, the capacitor of the third capacitor Ca and the 4th capacitor Cb can be small capacitances,
The switching frequency current ripple that can be used for absorbing voltage bus Vbus, relative to being eliminated in the related technology using big electrolytic capacitor
Line frequency current ripples, the disclosure can greatly reduce the area of component occupancy, to optimize circuit structure, and significantly drop
Low cost.Also, in this case, current source PFC and adjustable gain converter are not independent control, but are carried out system-level
Control, current source PFC and adjustable gain converter will more efficiently work.
It is to be understood that being exemplary above to the description of adjustable gain converter, above description should not be understood
To be the limitation to the disclosure, art technology thinks to increase on the basis of the disclosure, reduces component or change each
The connection relationship of a component, as long as by multiple transformer device structures, and by the phase controlling of different transformers to reality
The variation of voltage is now supplied, such change should be considered as the deformation based on the disclosure, and deformation should be considered as in this public affairs
In the range of opening protection.
What disclosure output stage provided is voltage-multiplying circuit connection (Fig. 2 a), and commutator transformer shown in Fig. 2 a can be without in
Heart tap can simplify the design of transformer using such design, and can reduce cost.Certainly, implement in others
In mode, also transformer can also realize (Fig. 2 b) with centre tapped times of current circuit connection using having, and can also realize in this way
The function of adjustable gain converter, should also be considered as the deformation based on the disclosure, and deformation should be considered as protecting in the disclosure
In the range of shield.
Referring to Fig. 5, Fig. 5 shows the schematic diagram of the adjustable gain converter according to one embodiment of the disclosure.
Adjustable gain converter 20 can be by adjusting the first full-bridge circuit Phase A and the second full-bridge circuit Phase B
Between phase in-migration realize the adjusting of gain, the first full-bridge circuit may be implemented in adjustable gain converter 20 described in the disclosure
Automated power balance between Phase A and the second full-bridge circuit Phase B, the first full-bridge circuit Phase A and the second full-bridge
Circuit Phase B works in parallel when exporting low supply voltage Vo, when exporting high supply voltage Vo to go here and there
The mode of connection works, in the useful power supply voltage range of output (such as 330V-750V), the first full-bridge circuit Phase
A and the second full-bridge circuit Phase B work in most efficient DC/DC transformer open loop mode of operation, adjustable gain converter
Each component stress variation it is smaller, the phase shift between the first full-bridge circuit Phase A and the second full-bridge circuit Phase B
It can seamlessly change, be exported with adapting to supply voltage Vo between minimum value (such as 330V) and maximum value (such as 750V),
In this way, AC/DC converter can be made to have higher and stable power conversion efficiency in entire range of regulation.
It shows please also refer to Fig. 6, Fig. 6 according to each wave in one embodiment of the disclosure in adjustable gain converter
The schematic diagram of shape.
Each waveform includes the voltage waveform of secondary side gusset VF1 and VF2, the electricity for flowing through inductance Lo1 and inductance Lo2
Flow waveform, the second subprime winding of the waveform of Io1 and electric current Io2, the waveform of the voltage Vsa of the first secondary windings and electric current Isa
Voltage Vsb waveform and electric current Isb waveform.
In a kind of possible embodiment, the first full-bridge circuit Phase A and the second full-bridge circuit Phase B are ok
It works under full duty ratio, and (such as 330V-750V) can realize ZVS in a wide range.Due to the first full-bridge
Circuit Phase A and the second respective voltage and current of full-bridge circuit Phase B are all push-push operations, therefore the first full-bridge circuit
The circulating current of Phase A and the second full-bridge circuit Phase B are almost nil, and the working efficiency of adjustable gain converter can pole
Big raising realizes high efficiency and highdensity work.
As shown in fig. 6, with the change of the phase shift between the first full-bridge circuit Phase A and the second full-bridge circuit Phase B
Change, voltage, the current waveform of each node change therewith in adjustable gain converter.By taking electric current Isa as an example, when the first full-bridge electricity
From parallel operation pattern switching to tandem working mode, (phase shift becomes road Phase A and the second full-bridge circuit Phase B from 0 °
180 °) when, the current value of electric current Isa is reduced to original half.
It should be noted that the specific introduction to adjustable gain converter, please refers to description above, it is no longer superfluous herein
It states.
Fig. 7 a and Fig. 7 b, Fig. 7 a is please referred to show according to the first full-bridge circuit in one embodiment of the disclosure and first time
The schematic diagram of grade circuit, Fig. 7 b show the control schematic diagram to the first full-bridge circuit according to one embodiment of the disclosure.
As shown in Figure 7b, when the duty ratio of the first full-bridge circuit is equal to 50% (full duty ratio), phase shift control can be passed through
System or PWM control are to control the working condition of the first full-bridge circuit.At this point, two kinds of controls are fully equivalent.
In Phaseshift controlling, conducting to each transistor of the first full-bridge circuit and it can disconnect and carry out Phaseshift controlling,
So that the first transistor Q1a, second transistor Q2a, third transistor Q3a, the 4th transistor Q4a are when different
Between be connected.
In PWM control, it can use pwm pulse and make the first transistor Q1a, second transistor Q2a, third brilliant
Body pipe Q3a, the 4th transistor Q4a are connected in different times, to control the working condition of first full-bridge circuit.
In a kind of possible embodiment, Fig. 7 b, which is shown, controls the first secondary windings T1a by Phaseshift controlling and PWM
Voltage Vsa, node VF1, node VF2 voltage.
Similarly, it when the duty ratio of the second full-bridge circuit is equal to 50%, can also be controlled by Phaseshift controlling and PWM control
Make the work of the 5th transistor Q1b, the 6th transistor Q2b, the 7th transistor Q3b, the 8th transistor Q4b in the second full-bridge circuit
State, principle is similar with the first full-bridge circuit, and details are not described herein.
It is to be understood that Fig. 7 b is exemplary, it is complete that those skilled in the art can be arranged first according to the actual situation
The working condition of each transistor of bridge circuit Phase A and/or the second full-bridge circuit Phase B, the disclosure do not limit this
System.
It please refers to Fig. 8 a and Fig. 8 b, Fig. 8 a and shows increasing according to adjustable gain converter 20 in one embodiment of the disclosure
Benefit be less than or equal to 0.5 (i.e. equivalent duty ratio, by the no-load voltage ratio of transformer be 1 for) when, the first full-bridge circuit Phase A and/
Or second control schematic diagram when being less than or equal to 50% of the duty ratio of full-bridge circuit Phase B, Fig. 8 b shows according to this public affairs
When opening the gain of adjustable gain converter 20 in an embodiment more than or equal to 0.5 (by taking the no-load voltage ratio of transformer is 1 as an example), the
The Phaseshift controlling schematic diagram of one full-bridge circuit Phase A and the second full-bridge circuit Phase B.
As shown in Figure 8 a, in the phase duty cycle of the first full-bridge circuit Phase A and/or the second full-bridge circuit Phase B
When less than or equal to 50%, it is complete the first full-bridge circuit Phase A and/or second can be controlled by Phaseshift controlling or PWM
Each transistor working condition of bridge circuit Phase B.
As shown in Figure 8 b, after adjustable gain converter has obtained phase shift β, so that it may adjust the first full-bridge according to phase shift β
Phase shift between circuit Phase A and the second full-bridge circuit Phase B, so that the first full-bridge circuit Phase A and second
Full-bridge circuit Phase B works between in parallel and serial, to be adjusted to supply voltage.At this point, the first full-bridge circuit
Phase A and the second full-bridge circuit Phase B each work in full duty ratio state.
The control of each transistor when being shown between the gain 0-1 of adjustable gain converter also referring to Fig. 9, Fig. 9
Signal schematic representation.
As can be seen that when the duty ratio of the first full-bridge circuit Phase A and/or the second full-bridge circuit Phase B is 50%
When following, each transistor of the first full-bridge circuit Phase A and/or the second full-bridge circuit Phase B can be controlled by PWM
Working condition.When the duty ratio of the first full-bridge circuit Phase A and the second full-bridge circuit Phase B all reach full duty ratio
When 50%, it can continue to adjust by the phase in-migration between control the first full-bridge circuit Phase A and the second full-bridge circuit Phase B
The gain of whole adjustable gain converter, according to mode as shown in Figure 9, to the first full-bridge circuit Phase A and/or the second full-bridge
The working condition of each transistor of circuit Phase B is controlled.
For example, when the duty ratio of the first full-bridge circuit Phase A and the second full-bridge circuit Phase B are full duty ratio
It, can be in the working condition for each transistor for controlling the first full-bridge circuit Phase A according to mode shown in Fig. 9 when 50%
Afterwards, output controls the working condition that signal controls each transistor of the second full-bridge circuit Phase B after postponing phase shift β, leads to
Cross such mode, realize the gain of adjustable gain converter from 0.5 to 1 between control, the first full-bridge circuit can be made
Phase A and the second full-bridge circuit Phase B is gradually converted into series connection from parallel connection, to increase supply voltage.
It should be noted that above each crystal to the first full-bridge circuit Phase A and the second full-bridge circuit Phase B
The control of pipe is exemplary, it is not considered that above description is the limitation to the disclosure, as long as passing through control the first full-bridge electricity
Phase shift between road Phase A and the second full-bridge circuit Phase B is to which realization is to the technology of the adjustment of the supply voltage of output
Scheme should be all considered as within the scope of the present disclosure.
The presently disclosed embodiments is described above, above description is exemplary, and non-exclusive, and
It is not limited to disclosed each embodiment.Without departing from the scope and spirit of illustrated each embodiment, for this skill
Many modifications and changes are obvious for the those of ordinary skill in art field.The selection of term used herein, purport
In the principle, practical application or technological improvement to the technology in market for best explaining each embodiment, or lead this technology
Other those of ordinary skill in domain can understand each embodiment disclosed herein.
Claims (15)
1. a kind of power supply system, which is characterized in that the system comprises:
Current source power factor converting device PFC, is electrically connected to external power supply, for receiving the electric energy of the external power supply, and root
Electric current and voltage of transformation are converted according to required power output；
Adjustable gain converter is electrically connected to the current source PFC and load, for receiving the load voltage of the load, and
The gain of the adjustable gain converter is adjusted, using the load voltage to export using the voltage of transformation and the gain
Supply voltage, and supply current is exported using the transformation electric current and the gain；
Feedback controller is electrically connected to the load and the current source PFC, load current and mesh for receiving stream overload
Electric current is marked, and the transformation electric current is adjusted according to the load current and the target current.
2. system according to claim 1, which is characterized in that the adjustable gain converter include the first full-bridge circuit,
Second full-bridge circuit, the first secondary circuit and second subprime circuit, it is complete that first full-bridge circuit is connected in series in described second
Bridge circuit, first secondary circuit are coupled to first full-bridge circuit, and the second subprime circuit is coupled to described second
Full-bridge circuit, the gain of the adjustable gain converter are by changing between first full-bridge circuit and the second full-bridge circuit
Phase in-migration adjustment.
3. system according to claim 2, which is characterized in that first full-bridge circuit includes the first transistor, second
Transistor, third transistor, the 4th transistor and the first armature winding, the first end of the first transistor are electrically connected to described
An output end of current source PFC and the first end of the third transistor, the second end of the first transistor are electrically connected to institute
It states the first end of second transistor and the first end of first armature winding, the second end of the third transistor is electrically connected to
The first end of 4th transistor and the second end of first armature winding, the second end electrical connection of the second transistor
In the second end of the 4th transistor.
4. system according to claim 2, which is characterized in that second full-bridge circuit includes the 5th transistor, the 6th
Transistor, the 7th transistor, the 8th transistor and the second armature winding, the first end of the 5th transistor are electrically connected to described
The first end of 7th transistor, the second end of the 5th transistor are electrically connected to the first end of the 6th transistor and described
The first end of second armature winding, the second end of second armature winding be electrically connected to the 7th transistor second end and
The second end of the first end of 8th transistor, the 6th transistor is electrically connected to another output of the current source PFC
The second end of end and the 8th transistor.
5. system according to claim 2, which is characterized in that first secondary circuit includes the first rectification circuit and the
Two rectification circuits, the second subprime circuit include third rectification circuit and the 4th rectification circuit, in which:
Positive half-wave of first rectification circuit for first full-bridge circuit rectifies；
Second rectification circuit is used for the negative halfwave rectifier of first full-bridge circuit；
Positive half-wave of the third rectification circuit for second full-bridge circuit rectifies；
4th rectification circuit is used for the negative halfwave rectifier of second full-bridge circuit.
6. system according to claim 5, which is characterized in that first secondary circuit includes the first secondary windings, the
One diode, the second diode, the second subprime circuit include second subprime winding, third diode, the 4th diode, institute
It states the first secondary circuit and the second subprime circuit all includes the 5th diode and the 6th diode, first rectification circuit
Including the first diode and the 5th diode, second rectification circuit includes second diode and described
Six diodes, the third rectification circuit include the third diode and the 5th diode, the 4th rectification circuit
Including the 4th diode and the 6th diode, in which:
The first end of first secondary windings is electrically connected to the anode of the first diode and the yin of second diode
Pole, the cathode of the first diode are electrically connected to the cathode of the third diode and the cathode of the 5th diode；Described
The anode of three diodes is electrically connected to the first end of the second subprime winding and the cathode of the 4th diode；Described second
The second end of secondary windings is electrically connected to the anode and the 6th diode of the second end of first secondary windings, the 5th diode
Cathode, the anode of the 4th diode is electrically connected to the anode of second diode and the anode of the 6th diode.
7. system according to claim 5, which is characterized in that first rectification circuit and the third rectification circuit quilt
Two staggered power rectifiers are configured to, and/or
Second rectification circuit and the 4th rectification circuit are configured as two staggered power rectifiers.
8. system according to claim 6, which is characterized in that first secondary circuit and second subprime circuit are also common
Including the first inductance and the second inductance, in which:
The first end of first inductance is electrically connected to the cathode of the first diode, the cathode of the third diode and institute
The cathode of the 5th diode is stated, the first end of second inductance is electrically connected to the anode of the 6th diode, described second
The anode of the anode of diode and the 4th diode；The second end of the second end of first inductance and second inductance
For exporting the supply voltage and supply current.
9. system according to claim 8, which is characterized in that the adjustable gain converter further includes first capacitor,
Two capacitors, the first end of the first capacitor are electrically connected to the second end of first inductance, the second end of the first capacitor
It is electrically connected to the second of the first end of second capacitor, the second end of first secondary windings and the second subprime winding
End；The second end of second capacitor is electrically connected to the second end of second inductance.
10. system according to claim 2, which is characterized in that in first full-bridge circuit and/or second full-bridge
When the duty ratio of circuit is less than or equal to 50%, by adjusting the phase shift of first full-bridge circuit and second full-bridge circuit
Or the gain is adjusted by pulse width modulation (PWM).
11. system according to claim 2, which is characterized in that in first full-bridge circuit and/or second full-bridge
When the duty ratio of circuit is equal to 50%, by adjusting the phase in-migration between first full-bridge circuit and second full-bridge circuit
Adjust the gain.
12. system according to claim 11, which is characterized in that described by adjusting first full-bridge circuit and described
Phase in-migration between second full-bridge circuit adjusts the gain, comprising:
The phase shift is determined by following formula:
β=180 ° * ((Vo-V1)/(V2-V1)), wherein β indicates the size of the phase shift, and Vo indicates the load voltage, V1
Indicate the minimum value of the load voltage, V2 indicates the maximum value of the load voltage.
13. system according to claim 2, which is characterized in that the adjustable gain converter further include: third capacitor and
4th capacitor, the first end of the third capacitor are electrically connected to one end of the current source PFC, the second end of the third capacitor
It is electrically connected to the first end of the 4th capacitor, the second end of the 4th capacitor is electrically connected to the another of the current source PFC
End.
14. system according to claim 1, which is characterized in that the feedback controller includes operational amplifier and electric current
Loop compensator,
The first end of the operational amplifier is for receiving the load current, and the second end of the operational amplifier is for receiving
The target current；
The current loop compensator is electrically connected to the first end and output end of the operational amplifier, for according to the operation
The transformation that the load current of amplifier output and the comparison result of the target current export the current source PFC
Electric current is adjusted to adjust the supply current.
15. a kind of charging equipment, which is characterized in that the charging equipment includes such as the described in any item power supplies of claim 1-14
System.
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|---|---|---|---|
| US201962789750P | 2019-01-08 | 2019-01-08 | |
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| CN112073029A (en) * | 2020-08-12 | 2020-12-11 | 武汉博畅通信设备有限责任公司 | Frequency hopping filter |
| WO2023179242A1 (en) * | 2022-03-25 | 2023-09-28 | 追觅创新科技(苏州)有限公司 | Constant-power control apparatus and method for electronic device, and device and storage medium |
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| CN109842182B (en) | 2020-12-04 |
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