CN109818518B - Modularized series inverter - Google Patents
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- CN109818518B CN109818518B CN201910128711.XA CN201910128711A CN109818518B CN 109818518 B CN109818518 B CN 109818518B CN 201910128711 A CN201910128711 A CN 201910128711A CN 109818518 B CN109818518 B CN 109818518B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/483—Converters with outputs that each can have more than two voltages levels
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
- H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
Abstract
The invention discloses a modularized series inverter, the topology of which is an N +1 level single-phase cascade H-bridge structure or an N +1 level three-phase MMC structure, comprising a normal sub-module and a redundant sub-module which are connected in series, wherein the normal sub-module and the redundant sub-module have the same structure and are respectively composed of a full-bridge or half-bridge structure composed of IGBTs with anti-parallel diodes and a direct current capacitor C; when in modulation, firstly, a modulation wave signal of each sub-module is determined by combining a control strategy of the modular series inverter; then determining the amplitude of the triangular carrier wave of each submodule according to the number of redundant submodules contained in the modular series inverter topology; and finally, determining a control pulse signal of the submodule according to the modulation wave signal of the submodule and the corresponding triangular carrier signal, and further controlling the switching state of the submodule. When the sub-module of the inverter breaks down, the switching process of the traditional normal sub-module and the traditional redundant sub-module is not needed, and the disturbance to the system is reduced.
Description
Technical Field
The invention belongs to the field of power electronics, and particularly relates to a redundant fault-tolerant PWM (pulse-width modulation) method and a modular series inverter based on the same.
Background
In recent decades, with the rapid development of power electronic technology, Voltage Source Converters (VSCs) based on fully-controlled power switching devices such as IGBTs are widely applied in power systems, wherein multilevel converters have the characteristics of low output voltage harmonic content, small switching loss, high applicable voltage level and the like, and have obvious advantages in the fields of high-power occasions such as high-voltage direct current (HVDC), medium-high voltage power quality control and the like.
The modularized series inverter adopts a high-degree modularized structure due to the topology, is easy to expand a system and realize redundancy control, has the advantages of low switching frequency, good output voltage waveform and the like, and has become the support force applied to the current multilevel converter. However, each phase of the modular series inverter is formed by cascading a plurality of submodules with the same structure, the output function depends on the submodules to a great extent, and once a fault occurs in a submodule, the normal work of the modular series inverter is influenced, so that the reliability of the system operation is reduced. Therefore, a certain number of redundant sub-modules must be arranged, and when a sub-module fails, the sub-module can be replaced in time, so that the normal operation of the modular series inverter can be ensured. In practical application, in order to realize efficient protection of the modular series inverter, all sub-modules (including redundant sub-modules) are usually put into operation without setting a special redundant sub-module, and when a sub-module fails, the sub-module is bypassed and put into the redundant sub-module for replacement, so that the rapid recovery of the whole system is ensured.
For a modular series inverter, the choice of modulation strategy directly affects its output characteristics. Currently, common modulation methods include nearest level approximation modulation (NLM), carrier-stacked PWM (CD-PWM), and carrier-phase shifted PWM (CPS-PWM). The carrier phase-shift PWM has good dynamic response performance, excellent output harmonic wave characteristic and easy combination with additional control, and is widely applied to engineering. However, the conventional carrier phase shift PWM technique determines the on/off of the switching devices in the sub-modules by comparing the modulated wave with the carrier, so that the number of carriers corresponds to the number of sub-modules put into each phase one by one. When the traditional carrier phase-shifting PWM is applied to a modular series inverter containing redundant sub-modules, the redundant sub-modules exist in each phase of the modular series inverter and participate in switching in the whole operation process, so that the number of the sub-modules cannot correspond to the number of the carriers one by one. In order to ensure the normal output of the modular series inverter, carriers need to be circularly distributed, thereby causing some problems such as unnecessary switching action generated by the switching devices in the sub-modules to increase the switching loss thereof, increase the control difficulty of the switching devices in the sub-modules, and the like.
Disclosure of Invention
The invention aims to provide a redundant fault-tolerant PWM modulation method and a modular series inverter based on the method, which do not need to circularly distribute carriers.
The technical solution for realizing the purpose of the invention is as follows: a redundant fault tolerant PWM modulation method for a modular series inverter with redundant sub-modules, comprising the steps of:
step 1: determining a modulation wave signal of each sub-module by combining a control strategy of the modular series inverter;
step 2: according to the number of redundant sub-modules contained in the modular series inverter topology, determining the amplitude of the triangular carrier wave of each sub-module, specifically:
minimum value A of triangular carrier amplitudeminRemains unchanged, maximum value AmaxThe number of the redundant sub-modules is determined, namely:
wherein N is the number of normal sub-modules, and M is the number of redundant sub-modules;
and step 3: and determining a control pulse signal of the submodule according to the modulation wave signal of the submodule and the corresponding triangular carrier signal, and further controlling the switching state of the submodule.
The control strategy in the step 1 is a capacitance-voltage balance control strategy, a direct-current capacitance voltage value of each submodule is collected, and is compared with a voltage instruction value and then multiplied by a sign function of current flowing into each submodule to obtain a modified modulation wave signal.
And then normalizing the modified modulation wave signal to be used as a modulation wave signal input into a PWM (pulse-width modulation) algorithm.
The specific method for determining the control pulse signal of the sub-module in the step 3 is as follows: when the modulation wave signal of the sub-module is greater than the corresponding carrier signal, controlling the pulse signal to output a high level; and when the modulation wave signal of the sub-module is smaller than the corresponding carrier signal, controlling the pulse signal to output a low level.
The modular series inverter based on the modulation method is characterized in that the topology of the modular series inverter is an N +1 level single-phase cascade H-bridge structure or an N +1 level three-phase MMC structure, for the N +1 level single-phase cascade H-bridge structure, the topology is formed by connecting N normal sub-modules and M redundant sub-modules in series, for the N +1 level three-phase MMC structure, each phase is formed by an upper bridge arm and a lower bridge arm which are completely identical, each bridge arm is formed by connecting N normal sub-modules, M redundant sub-modules and an inductor in series, the normal sub-modules and the redundant sub-modules are identical in structure and are formed by a full-bridge or half-bridge structure and a direct-current capacitor C, wherein the full-.
The output port of each submodule is connected with a bypass switch S in parallel, the S is in an off state when the submodule normally operates, and the S is closed to enable the submodule to quit operation when the submodule fails.
Compared with the prior art, the invention has the following remarkable advantages: 1) the number of the triangular carriers in the modulation method is equal to that of the sub-modules, and when the redundant sub-modules exist, the carriers do not need to be circularly distributed, so that the control difficulty of the sub-module switching devices is simplified, unnecessary switching states are reduced, and the switching frequency of the sub-modules is reduced; 2) according to the modular series inverter, when the sub-module fails, the fault module can be cut off by directly closing the bypass switch, the traditional switching process of the normal sub-module and the redundant sub-module is not needed, and disturbance to a system is reduced.
Drawings
Fig. 1 is a topology diagram of a modular series inverter of the present invention.
FIG. 2 is a schematic block diagram of a modulation method of the present invention.
Fig. 3 is a waveform diagram of a triangular carrier wave and a modulated wave in the modulation method of the present invention.
Fig. 4 is a diagram of the operation of a submodule in the modulation method of the present invention.
Detailed Description
The invention is further illustrated by the following embodiments in combination with the accompanying drawings.
Fig. 1 is a topology diagram of a modular series inverter, where the topology of the modular series inverter is an N +1 level single-phase cascade H-bridge structure or an N +1 level three-phase MMC structure, as shown in fig. 1(a) and 1(b), respectively. For an N +1 level single-phase cascade H-bridge structure, the topology is formed by connecting N normal sub-modules and M redundant sub-modules in series; for an N +1 level three-phase MMC structure, each phase is composed of an upper bridge arm and a lower bridge arm which are completely the same, and each bridge arm is formed by connecting N normal sub-modules, M redundant sub-modules and inductors in series. The normal sub-module and the redundant sub-module have the same structure, and for the N +1 level single-phase cascade H-bridge structure, the normal sub-module consists of a full-bridge structure consisting of IGBTs with anti-parallel diodes and a direct-current capacitor C; for an N +1 level three-phase MMC structure, the structure consists of a half-bridge structure consisting of IGBTs with anti-parallel diodes and a direct current capacitor C. For the full-bridge configuration in fig. 1(b), it can be treated as two half-bridge configurations in modulation. And the output port of each submodule is connected with a bypass switch S in parallel, the S is in an off state when the submodule normally operates, and the S is closed to enable the submodule to quit the operation when the submodule fails.
As shown in fig. 2, the redundant fault-tolerant PWM modulation method of the modular series inverter includes the following steps:
step 1: determining a modulation wave signal of each sub-module by combining a control strategy of the modular series inverter;
the control strategy in the step 1 is a capacitance voltage balance control strategy, and the voltage of the direct current capacitor in each sub-module is controlled to track the reference value, so that the energy distribution of each sub-module is adjusted, and the voltage fluctuation of the direct current capacitor is reduced. And the capacitor voltage balance control strategy acquires the direct-current capacitor voltage value of each submodule, the direct-current capacitor voltage value is compared with the voltage instruction value and then multiplied by the sign function of the current flowing into each submodule to obtain a correction modulation wave signal, and the correction modulation wave signal is subjected to normalization operation and is used as a modulation wave signal of a subsequent input carrier phase-shifting PWM modulation method.
Step 2: according to the number of redundant sub-modules contained in the modular series inverter topology, the amplitude of the triangular carrier wave of each sub-module is determined, and the specific method comprises the following steps: minimum value A of triangular carrier amplitudeminRemains unchanged, maximum value AmaxThe number of the redundant sub-modules is determined, namely:
wherein, N is the number of normal sub-modules, and M is the number of redundant sub-modules.
Compared with the traditional carrier phase-shifting PWM modulation method, the method is improved in that the minimum value of the amplitude of the triangular carrier wave is kept to be-1, and the maximum value of the amplitude of the triangular carrier wave is determined by the number of the redundant sub-modules. Meanwhile, the number of the triangular carrier signals corresponds to all the sub-modules including the redundant sub-modules one by one.
In fig. 3, N is 10, M is 2, the phases of the triangular carriers are sequentially shifted by pi/(N + M) pi/12, and the minimum value a of the triangular carrier amplitude isminIs kept constant at-1, maximum
As can be seen from fig. 3, although the number of the triangular carriers is N + M, the maximum value a of the triangular carrier amplitude is within M/(N + M) of each carrier periodmaxAnd the carrier signal is always greater than 1, the carrier signal is always greater than the modulation wave signal, and the submodule controls the pulse signal to maintain low level. The sub-modules are switched between the normal working state and the redundancy state by adjusting the equivalent conduction time of the sub-modules, and the output level number of the modularized series inverter can be ensured to be (N + 1). When a certain submodule in the bridge arm breaks down, the bypass switch S in the submodule can be directly closed to enable the submodule to quit operation, conventional replacement switching operation is not needed, and the system cannot be obviously disturbed because the modulation method controls the triangular carrier wave corresponding to the submodule to be dynamically adjusted.
When the traditional carrier phase-shifting PWM method is applied to the MMC topology of (N + M) sub-modules, in order to ensure that the output level number of the modular series inverter is (N +1), the number of the triangular carriers needs to be fixed to be N. In the modulation method, the number of triangular carriers is no longer fixed to N, but is consistent with the total number of sub-modules, i.e., N + M, as shown in fig. 4.Therefore, unnecessary switching states can be reduced while the control difficulty of the switching device is effectively reduced, and the switching frequency f of the power device in each submodule is reducedcNamely, the following steps are provided:
wherein f isc0The switching frequency of a power device in a submodule is the switching frequency of a traditional carrier phase-shifting PWM modulation method.
And step 3: determining a control pulse signal of the submodule according to the modulation wave signal and a triangular carrier signal of the corresponding submodule so as to control the switching state of the submodule, wherein the specific method comprises the following steps: when the modulation wave signal of the jth sub-module is greater than the corresponding carrier signal, controlling the pulse signal to output a high level; and when the modulation wave signal of the jth sub-module is smaller than the corresponding carrier signal, controlling the pulse signal to output a low level.
Claims (2)
1. A modularized series inverter is characterized in that the topology of the modularized series inverter is an N +1 level single-phase cascade H-bridge structure or an N +1 level three-phase MMC structure, for the N +1 level single-phase cascade H-bridge structure, the topology is formed by connecting N normal sub-modules and M redundant sub-modules in series, for the N +1 level three-phase MMC structure, each phase is formed by an upper bridge arm and a lower bridge arm which are completely the same, each bridge arm is formed by connecting N normal sub-modules, M redundant sub-modules and an inductor in series, the normal sub-modules and the redundant sub-modules have the same structure and are formed by a full-bridge or half-bridge structure formed by IGBTs with anti-parallel diodes and a direct current capacitor C;
output ports of sub-modules in the modular series inverter are connected with a bypass switch S in parallel, the sub-modules are in an off state when in normal operation, and the sub-modules are closed to quit the operation when in failure;
the modularized series inverter adopts the following PWM modulation method, and the specific steps are as follows:
step 1: determining a modulation wave signal of each submodule by combining a control strategy of the modular series inverter, specifically:
the control strategy is a capacitance voltage balance control strategy, a direct current capacitance voltage value of each submodule is collected, and is compared with a voltage instruction value and then multiplied by a sign function of current flowing into each submodule to obtain a modified modulation wave signal;
step 2: according to the number of redundant sub-modules contained in the modular series inverter topology, determining the amplitude of the triangular carrier wave of each sub-module, specifically:
minimum value A of triangular carrier amplitudeminRemains unchanged, maximum value AmaxThe number of the redundant sub-modules is determined, namely:
wherein N is the number of normal sub-modules, and M is the number of redundant sub-modules;
and step 3: determining a control pulse signal of the submodule according to the modulation wave signal of the submodule and the corresponding triangular carrier signal, and further controlling the switching state of the submodule, specifically:
the specific method for determining the control pulse signal of the submodule comprises the following steps: when the modulation wave signal of the sub-module is greater than the corresponding carrier signal, controlling the pulse signal to output a high level; and when the modulation wave signal of the sub-module is smaller than the corresponding carrier signal, controlling the pulse signal to output a low level.
2. The modular series inverter of claim 1, wherein the modified modulation wave signal is normalized as a modulation wave signal input to a PWM modulation algorithm when the modular series inverter performs PWM modulation.
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| CN111342637A (en) * | 2018-12-19 | 2020-06-26 | 南京南瑞继保电气有限公司 | Rapid voltage-sharing method of cascade multilevel converter |
| CN110311543B (en) * | 2019-07-26 | 2020-02-07 | 中国矿业大学(北京) | Topology reconstruction and power factor angle calculation method for cascade H-bridge converter during fault |
| CN113783449A (en) * | 2021-09-03 | 2021-12-10 | 南京理工大学 | Common-ground type double-output switch capacitance type multi-level inverter |
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| CN102684531B (en) * | 2012-05-09 | 2014-07-30 | 浙江大学 | Zero-dead-zone cascade H-bridge type multi-level inverter and control method |
| JP6017272B2 (en) * | 2012-11-12 | 2016-10-26 | 株式会社日立製作所 | Power conversion device and power conversion method |
| CN103248252B (en) * | 2013-03-07 | 2015-02-11 | 中国矿业大学 | Modulation strategy for modular multilevel transducer |
| CN103248112B (en) * | 2013-04-12 | 2015-03-18 | 株洲变流技术国家工程研究中心有限公司 | Control and switch method for redundant submodules of modular multilevel converter |
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