CN109713896B - High-gain boost converter with inverse square characteristic and control method thereof - Google Patents

High-gain boost converter with inverse square characteristic and control method thereof Download PDF

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CN109713896B
CN109713896B CN201910010387.1A CN201910010387A CN109713896B CN 109713896 B CN109713896 B CN 109713896B CN 201910010387 A CN201910010387 A CN 201910010387A CN 109713896 B CN109713896 B CN 109713896B
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CN109713896A (en
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李飞
季素云
耿宁
杨静
刘林
岳增伟
崔川
梁珊珊
孙竟成
姚雨
张阳
徐天赐
于洋
宋嵘
高鹏
薛启成
朱锋
王洪信
刘兴华
乔恒
孙立新
韩旭
王世儒
孙鹏
王磊磊
边宏超
孙燕
燕鹏
李先进
阎炳水
李天�
邵泽霖
葛鹏
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State Grid Corp of China SGCC
Zibo Power Supply Co of State Grid Shandong Electric Power Co Ltd
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Zibo Power Supply Co of State Grid Shandong Electric Power Co Ltd
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Abstract

The invention discloses a high-gain boost converter with inverse square characteristic, which comprisesCoupling inductance network and input filter inductance LinA clamping booster circuit, a power switch tube S and an input filter inductor LinInput side is connected with an input power supply VinThe output side is connected with the clamping voltage booster circuit, and the input side of the coupling inductance network is connected with the voltage boosting capacitor C of the clamping voltage booster circuit1The output end is connected with the drain electrode of the power switch tube S and the clamping booster circuit, and the grid electrode of the power switch tube S is connected with the control signal voltage VgsSource of power switch tube S and input power supply VinThe output end of the clamping voltage-boosting circuit is the output end of the boost converter, and the load is connected with the output end of the boost converter. By utilizing the small change of the duty ratio of the converter, the gain can be greatly increased or reduced, and the smaller the turn ratio of the coupling inductor is, the higher the voltage gain is.

Description

High-gain boost converter with inverse square characteristic and control method thereof
Technical Field
The invention relates to a high-gain boost converter with inverse square characteristic and a control method thereof, belonging to the technical field of power electronic converters.
Background
In recent years, a direct-current microgrid system satisfying local electric energy supply receives more and more attention, and particularly, a system in the renewable energy field, such as photovoltaic power generation and wind power generation, becomes a hot point of research as a direct-current power supply. These power supply systems have a common disadvantage that the output voltage is low, and it is difficult to output power-frequency alternating current after inversion, so that a boost direct current converter is needed to realize voltage boost. Common boosting technologies include a coupling inductor, a switch capacitor and the like, a converter for realizing voltage boosting by adopting the coupling inductor generally increases output voltage along with the increase of the turn ratio of the coupling inductor, and meanwhile, the change of duty ratio cannot realize the great increase of gain. However, too high a turn ratio causes problems: leakage inductance, parasitic capacitance, etc. increase, easily causing voltage and current spikes, which severely degrade system performance.
Disclosure of Invention
The invention aims to provide a high-gain boost converter with inverse square characteristics and a control method thereof, wherein the gain is greatly increased or reduced due to the slight change of the duty ratio, and the voltage gain is higher as the turn ratio of the coupling inductor is smaller.
In order to solve the technical problem, the technical scheme adopted by the invention is as follows: a high-gain boost converter with inverse square characteristic comprises a coupling inductance network, an input filter inductance LinA clamping booster circuit, a power switch tube S and an input filter inductor LinInput side is connected with an input power supply VinThe output side is connected with the clamping voltage booster circuit, and the input side of the coupling inductance network is connected with the voltage boosting capacitor C of the clamping voltage booster circuit1The output end is connected with the drain electrode of the power switch tube S and the clamping booster circuit, and the grid electrode of the power switch tube S is connected with the control signal voltage VgsSource of power switch tube S and input power supply VinThe output end of the clamping voltage-boosting circuit is the output end of the boost converter, and the load is connected with the output end of the boost converter.
Further, the coupling inductance network comprises a coupling inductance first winding N2Second winding N of coupled inductor1The clamping boost circuit comprises a first boost diode D1A second boost diode D2A third boost diode D4A first clamping diode DcAnd an output diode DoA first boost capacitor C1A second boost capacitor C2A first clamping capacitor CcAn output capacitor Co(ii) a Input filter inductance LinA second boost diode D2A first clamping diode DcAnd a first clamp capacitor CcAre connected in series to form a branch 1, a first boosting capacitor C1First winding N of coupling inductor2A second boost capacitor C2And an output diode DoAre connected in series to form a branch 2, the input end of the branch 1 is connected with the input power supply V after being connected with the branch 2 in parallelinIs connected with the positive pole of the output end through an output capacitor CoAnd an input power supply VinIs connected to the negative electrode(ii) a Input filter inductance LinAnd a second boost diode D2The junction between the anodes is called junction 1, and the second boost diode D2Cathode and first clamping diode DcThe junction between the anodes is called junction 2, the first clamping diode DcNegative pole and first clamping capacitor CcThe node between them is called node 3, the first boost capacitor C1And a first winding N of a coupling inductor2The junction point between is called junction point 4, and the first winding N of the coupling inductor2And a second boost capacitor C2The node between is called node 5, the second boost capacitor C2And an output diode DoThe junction between the positive electrodes is called as junction 6, the first boost diode is connected between junction 1 and junction 4, the positive electrode of the first boost diode is connected with junction 1, the negative electrode of the first boost diode is connected with junction 4, and the second winding N of the coupling inductor1A third boost diode D connected between node 2 and node 5, and the drain of power switch S connected to node 24Connected between node 3 and node 6, with the anode connected to node 3 and the cathode connected to node 6.
Further, a load R is connected in parallel with the output capacitor CoTwo ends.
Further, the power switch tube S is an MOS tube.
The invention also discloses a control method of the high-gain boost converter, which specifically comprises the following steps: s01), controlling the boost converter to be in a switching mode 1, and corresponding to the time [ t ]0,t1]The realization method comprises the following steps: t is t0Power switch tube S, D switched on at any moment1、Dc、DoReverse bias, D2、D4Forward bias, coupled inductor first winding leakage current and coupled inductor second winding current
Figure BDA0001936143010000021
iN1Rising, second boost diode current
Figure BDA0001936143010000022
Rising, third boost diode current
Figure BDA00019361430100000212
Rising, power switching tube current iSRising, output capacitance CoSupplying power to a load; s02), controlling the boost converter to be in the switching mode 2, and corresponding to the time [ t ]1,t2]The realization method comprises the following steps: t is t1At the moment, the power switch tube S is turned off, the switch mode 1 is ended, the switch mode 2 is started, and D2、D4Reverse bias, D1、Dx、DoForward bias, coupled inductor first winding leakage current and coupled inductor second winding current
Figure BDA0001936143010000023
iN1Descending; first clamp diode current
Figure BDA0001936143010000024
Drop, output diode current
Figure BDA0001936143010000025
Rising, first boost diode current
Figure BDA0001936143010000026
Down, input power supply VinInput filter inductor LinFirst winding N of coupling inductor2Second winding N of coupled inductor1And a second boost capacitor C2Common transfer of energy to an output capacitor CoAnd a load R; s03), controlling the boost converter to be in a switching mode 3, and corresponding to the time [ t ]2,t3]The realization method comprises the following steps: t is t2At time, the first clamp diode current
Figure BDA0001936143010000027
The voltage drops to zero, the switching mode 2 ends, the switching mode 3 begins, the power switch tube S is kept off, and D2、Dc、D4Reverse bias, D1、DoForward biased, coupled inductor first winding leakage current
Figure BDA0001936143010000028
Output diode current
Figure BDA0001936143010000029
And a first boost diode current
Figure BDA00019361430100000210
At the same time of falling, the input power VinInput filter inductor LinFirst winding N of coupling inductor2Second winding N of coupled inductor1And a second boost capacitor C2Common transfer of energy to an output capacitor CoAnd a load R; s04), the power switch S is turned on, a new switching cycle begins, and the boost converter continues to perform the operation from switching mode 1 to switching mode 3.
Further, the gain M of the high-gain boost converter is:
Figure BDA00019361430100000211
wherein D is the conduction duty ratio of the power switch tube, and N is N2/N1Is the turn ratio of the first winding of the coupling inductor to the second winding of the coupling inductor.
The invention has the beneficial effects that: the boost converter has high gain, the tiny conversion of the duty ratio can cause the great increase or reduction of the gain, the boost converter has the inverse square characteristic, the smaller the turn ratio of the coupling inductor is, the higher the voltage gain is, the influence of the leakage inductance and the parasitic capacitance of the coupling inductor on the performance of the converter is effectively reduced, and the voltage stress of the power switch tube is low.
Drawings
FIG. 1 is a circuit schematic of a high gain boost converter with an inversely proportional squared characteristic;
FIG. 2 is a modal diagram of a high gain boost converter with an inversely proportional squared characteristic;
fig. 3(a) is an equivalent circuit diagram of a high gain boost converter switching mode 1 with an inversely proportional squared characteristic;
fig. 3(b) is an equivalent circuit diagram of a high gain boost converter switching mode 2 with an inversely proportional squared characteristic;
fig. 3(c) is an equivalent circuit diagram of a high gain boost converter switching mode 3 with an inversely proportional squared characteristic;
fig. 4 is a graph of the effect of coupled inductor turn ratio and duty cycle ratio on the proposed boost converter gain.
FIG. 5 shows the input voltage VinThe voltage gain M is 13, the coupling inductance turn ratio is 1.8, and the output power is 500W, namely a Pspice simulation waveform of 38V.
The reference numbers in the figures illustrate: vinIs a DC voltage source, S is a power switch tube, and is coupled with a first winding N of an inductor2Second winding N of coupled inductor1(ii) a First boost diode D1A second boost diode D2A third boost diode D4A first clamping diode DcAnd an output diode DoA first boost capacitor C1A second boost capacitor C2A first clamping capacitor CcAn output capacitor CoR is the load, LMIs a magnetizing inductance, LkIs a coupled inductor leakage inductance.
Detailed Description
The invention is further described with reference to the following figures and specific embodiments.
Example 1
The embodiment discloses a high-gain boost converter with inverse square characteristics, as shown in fig. 1, comprising a coupled inductor network, an input filter inductor LinA clamping booster circuit and a power switch tube S, wherein the coupling inductance network comprises a first winding N of a coupling inductance2Second winding N of coupled inductor1The clamping boost circuit comprises a first boost diode D1A second boost diode D2A third boost diode D4A first clamping diode DcAnd an output diode DoA first boost capacitor C1A second boost capacitor C2A first clamping capacitor CcAn output capacitor Co。
Input filter inductance LinA second boost diode D2A first clamping diode DcAnd a first clamp capacitor CcAre connected in series to form a branch 1, a first boosting capacitor C1Coupled to each otherInductance first winding N2A second boost capacitor C2And an output diode DoAre connected in series to form a branch 2, the input end of the branch 1 is connected with the input power supply V after being connected with the branch 2 in parallelinIs connected with the positive pole of the output end through an output capacitor CoAnd an input power supply VinAre connected with each other.
Input filter inductance LinAnd a second boost diode D2The junction between the anodes is called junction 1, and the second boost diode D2Cathode and first clamping diode DcThe junction between the anodes is called junction 2, the first clamping diode DcNegative pole and first clamping capacitor CcThe node between them is called node 3, the first boost capacitor C1And a first winding N of a coupling inductor2The junction point between is called junction point 4, and the first winding N of the coupling inductor2And a second boost capacitor C2The node between is called node 5, the second boost capacitor C2And an output diode DoThe junction between the positive electrodes is called as junction 6, the first boost diode is connected between junction 1 and junction 4, the positive electrode of the first boost diode is connected with junction 1, the negative electrode of the first boost diode is connected with junction 4, and the second winding N of the coupling inductor1A third boost diode D connected between node 2 and node 54Connected between node 3 and node 6, with the anode connected to node 3 and the cathode connected to node 6.
The drain electrode of the power switch tube S is connected to the node 2, and the source electrode of the power switch tube S is connected to the input power supply VinIs connected to the converter control signal voltage VgsBy controlling the signal voltage V by means of a convertergsThe on-off of the power switch tube is controlled, so that the boost works in different switch modes, and the voltage is promoted.
In this embodiment, the output capacitor CoHaving a filtering effect and an output capacitor CoI.e. the output of the converter, and the load R is connected in parallel at the output of the converter.
In this embodiment, the power switch transistor S is an MOS transistor.
Example 2
This example discloses a method of controlling the high gain boost converter described in example 1,the control method is to make the boost converter reach the mode diagram shown in fig. 2, and fig. 2 shows the control signal voltage V of the high-gain boost convertergsLeakage current of the first winding of the coupling inductor
Figure BDA0001936143010000031
Coupled inductor second winding current iN1First boost diode current
Figure BDA0001936143010000032
Second boost diode current
Figure BDA0001936143010000033
Third boost diode current
Figure BDA0001936143010000034
First clamp diode current
Figure BDA0001936143010000041
Output diode current
Figure BDA0001936143010000042
Current i of power switch tubesThe control method divides the working process of the boost converter into 3 switching modes, namely a switching mode 1 to a switching mode 3, and the method is specifically described as follows:
switching mode 1, corresponding to [ t ] in FIG. 20,t1]The equivalent circuit is shown in FIG. 3(a), t0Power switch tube S, D switched on at any moment1、Dc、DoReverse bias, D2、D4Forward bias, coupled inductor first winding leakage current and coupled inductor second winding current
Figure BDA0001936143010000043
iN1Rising; second boost diode current
Figure BDA0001936143010000044
Rising, third boost diode current
Figure BDA0001936143010000045
Rising, power switching tube current iSRising, output capacitance CoTo power the load.
Switching mode 2, corresponding to [ t ] in FIG. 21,t2]The equivalent circuit is shown in FIG. 3(b), t1At the moment, the power switch tube S is turned off, the switch mode 1 is ended, the switch mode 2 is started, and D2、D4Reverse bias, D1、Dx、DoForward bias, coupled inductor first winding leakage current and coupled inductor second winding current
Figure BDA0001936143010000046
iN1Descending; first clamp diode current
Figure BDA0001936143010000047
Drop, output diode current
Figure BDA0001936143010000048
Rising, first boost diode current
Figure BDA0001936143010000049
And (4) descending. Input power supply VinInput inductor, coupling inductor first winding N2Second winding N of coupled inductor1And a second boost capacitor C2Common transfer of energy to an output capacitor CoAnd a load R, t2At time, the first clamp diode current
Figure BDA00019361430100000414
Drops to zero and the switching mode 2 ends.
Switching mode 3, corresponding to [ t ] in FIG. 22,t3]The equivalent circuit is shown in FIG. 3(c), t2At time, the first clamp diode current
Figure BDA00019361430100000410
The voltage drops to zero, the switching mode 2 ends, the switching mode 3 begins, and the power switch tube S keeps offBreak, D2、Dc、D4Reverse bias, D1、DoForward biased, coupled inductor first winding leakage current
Figure BDA00019361430100000411
Output diode current
Figure BDA00019361430100000412
And a first boost diode current
Figure BDA00019361430100000413
And (4) descending. At the same time, the input power VinInput inductor, coupling inductor first winding N2Second winding N of coupled inductor1And a second boost capacitor C2Common transfer of energy to an output capacitor CoAnd a load R.
When the power switch S is turned on, a new switching cycle begins, and the boost converter continues to perform the operation from the switching mode 1 to the switching mode 3.
From mode 1, the voltage expression of the inductance Lin and the coil N1 is:
VLin＝Vin，NVN1＝Vin+VC1+VN1,VN1+VCc+Vo＝VC2，
from modes 2 and 3, the voltage expression of the inductance Lin is:
VLin＝VC1，
from modalities 2 and 3, the voltage expression for coil N1 is:
Vin+VC1+VN1＝VCc+NVN1+Vo，
VN1＝VCc+VC2，
NVN1+VO＝Vin+VC1+VC2，
in combination with modes 1, 2 and 3, the volt-second balance principle is applied to the inductance Lin and the coil N1,
Figure BDA0001936143010000051
the following voltage expressions were derived:
Figure BDA0001936143010000052
finally, the gain expression derived from the above analysis is:
Figure BDA0001936143010000053
wherein D is the conduction duty ratio of the power switch tube, and N is N2/N1Is the turn ratio of the first winding of the coupling inductor to the second winding of the coupling inductor.
In a conventional coupled inductor type high gain dc converter, the voltage gain is related to the duty cycle and the turn ratio of the coupled inductor by: the voltage gain is obviously improved along with the increase of the turn ratio of the coupling inductor and is approximately in a proportional relation, however, the turn ratio of the coupling inductor cannot be infinitely improved, and when the turn ratio of the coupling inductor is larger, the leakage inductance and parasitic capacitance of the coupling inductor can seriously affect the performance of the converter; alternatively, the voltage gain increases with increasing duty cycle, in an approximately proportional relationship.
In the converter of the embodiment, the smaller the turn ratio of the coupling inductor is, the higher the gain of the converter is, and the approximately inverse proportional relationship is formed, so that the influence of the leakage inductance and the parasitic capacitance of the coupling inductor on the performance of the converter is effectively reduced; as the duty cycle increases, the voltage gain increases significantly, in approximate square proportion. The inverse characteristic and the square characteristic are combined in one transducer. The advantages of the proposed converter in turn ratio and duty cycle are further demonstrated as shown in fig. 4.
The beneficial effects of the structure of the invention are illustrated by the following specific Pspice simulation example:
as shown in fig. 5, the input voltage Vin38V, the voltage gain M is 13, the coupling inductance turn ratio is 1.8, the output power is 500W, the current waveforms of the devices are shown in the figure, and the theory is effectively verifiedThe accuracy of (2). As can be seen from the figure, the first clamp diode is naturally turned off, which can effectively improve the efficiency.
The foregoing description is only for the basic principle and the preferred embodiments of the present invention, and modifications and substitutions by those skilled in the art are included in the scope of the present invention.

Claims (5)

1. A high gain boost converter having an inverse square characteristic, characterized by: comprises a coupling inductance network and an input filter inductance LinA clamping booster circuit, a power switch tube S and an input filter inductor LinInput side is connected with an input power supply VinThe output side is connected with the clamping voltage booster circuit, and the input side of the coupling inductance network is connected with the voltage boosting capacitor C of the clamping voltage booster circuit1The output end is connected with the drain electrode of the power switch tube S and the clamping booster circuit, and the grid electrode of the power switch tube S is connected with the control signal voltage VgsSource of power switch tube S and input power supply VinThe output end of the clamping booster circuit is the output end of the boost converter, and the load is connected with the output end of the boost converter;
the coupling inductance network comprises a coupling inductance first winding N2Second winding N of coupled inductor1The clamping boost circuit comprises a first boost diode D1A second boost diode D2A third boost diode D4A first clamping diode DcAnd an output diode DoA first boost capacitor C1A second boost capacitor C2A first clamping capacitor CcAn output capacitor Co(ii) a Input filter inductance LinA second boost diode D2A first clamping diode DcAnd a first clamp capacitor CcAre connected in series to form a branch 1, a first boosting capacitor C1First winding N of coupling inductor2A second boost capacitor C2And an output diode DoAre connected in series to form a branch 2, the input end of the branch 1 is connected with the input power supply V after being connected with the branch 2 in parallelinIs connected with the positive pole of the output end through an output capacitor CoAnd an input power supply VinThe negative electrodes are connected;input filter inductance LinAnd a second boost diode D2The junction between the anodes is called junction 1, and the second boost diode D2Cathode and first clamping diode DcThe junction between the anodes is called junction 2, the first clamping diode DcNegative pole and first clamping capacitor CcThe node between them is called node 3, the first boost capacitor C1And a first winding N of a coupling inductor2The junction point between is called junction point 4, and the first winding N of the coupling inductor2And a second boost capacitor C2The node between is called node 5, the second boost capacitor C2And an output diode DoThe junction between the anodes is called junction 6, the first boost diode D1Connected between node 1 and node 4, with its positive electrode connected to node 1 and its negative electrode connected to node 4, and coupled inductor second winding N1A third boost diode D connected between node 2 and node 5, and the drain of power switch S connected to node 24Connected between node 3 and node 6, with the anode connected to node 3 and the cathode connected to node 6.
2. The high gain boost converter with inverse square characteristic of claim 1, wherein: the load R is connected in parallel with the output capacitor CoTwo ends.
3. The high gain boost converter with inverse square characteristic of claim 1, wherein: the power switch tube S is an MOS tube.
4. A method of controlling a high gain boost converter as claimed in claim 1, characterized by: the method comprises the following steps: s01), controlling the boost converter to be in a switching mode 1, and corresponding to the time [ t ]0,t1]The realization method comprises the following steps: t is t0Power switch tube S, D switched on at any moment1、Dc、DoReverse bias, D2、D4Forward bias, coupled inductor first winding leakage current and coupled inductor second winding current
Figure FDA0002596355100000011
iN1Rising, second boost diode current
Figure FDA0002596355100000012
Rising, third boost diode current
Figure FDA0002596355100000013
Rising, power switching tube current iSRising, output capacitance CoSupplying power to a load; s02), controlling the boost converter to be in the switching mode 2, and corresponding to the time [ t ]1,t2]The realization method comprises the following steps: t is t1At the moment, the power switch tube S is turned off, the switch mode 1 is ended, the switch mode 2 is started, and D2、D4Reverse bias, D1、Dc、DoForward bias, coupled inductor first winding leakage current and coupled inductor second winding current
Figure FDA0002596355100000014
iN1Descending; first clamp diode current
Figure FDA0002596355100000015
Drop, output diode current
Figure FDA0002596355100000016
Rising, first boost diode current
Figure FDA0002596355100000017
Down, input power supply VinInput filter inductor LinFirst winding N of coupling inductor2Second winding N of coupled inductor1And a second boost capacitor C2Common transfer of energy to an output capacitor CoAnd a load R; s03), controlling the boost converter to be in a switching mode 3, and corresponding to the time [ t ]2,t3]The realization method comprises the following steps: t is t2At time, the first clamp diode current
Figure FDA0002596355100000021
The voltage drops to zero, the switching mode 2 ends, the switching mode 3 begins, the power switch tube S is kept off, and D2、Dc、D4Reverse bias, D1、DoForward biased, coupled inductor first winding leakage current
Figure FDA0002596355100000022
Output diode current
Figure FDA0002596355100000023
And a first boost diode current
Figure FDA0002596355100000024
At the same time of falling, the input power VinInput filter inductor LinFirst winding N of coupling inductor2Second winding N of coupled inductor1And a second boost capacitor C2Common transfer of energy to an output capacitor CoAnd a load R; s04), the power switch S is turned on, a new switching cycle begins, and the boost converter continues to perform the operation from switching mode 1 to switching mode 3.
5. The method of claim 4, wherein the step of controlling the high gain boost converter comprises the steps of: the gain M of the high-gain boost converter is:
Figure FDA0002596355100000025
wherein D is the conduction duty ratio of the power switch tube, and N is N2/N1Is the turn ratio of the first winding of the coupling inductor to the second winding of the coupling inductor.
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