CN109347343A - A kind of multiport energy accumulation current converter that more distributed energy storages can be achieved and method - Google Patents
A kind of multiport energy accumulation current converter that more distributed energy storages can be achieved and method Download PDFInfo
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- CN109347343A CN109347343A CN201811287554.9A CN201811287554A CN109347343A CN 109347343 A CN109347343 A CN 109347343A CN 201811287554 A CN201811287554 A CN 201811287554A CN 109347343 A CN109347343 A CN 109347343A
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- 238000004146 energy storage Methods 0.000 title claims abstract description 37
- 238000000034 method Methods 0.000 title claims description 27
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- 230000002457 bidirectional effect Effects 0.000 claims abstract description 40
- 239000003990 capacitor Substances 0.000 claims abstract description 29
- 230000007935 neutral effect Effects 0.000 claims abstract description 23
- 238000002955 isolation Methods 0.000 claims abstract description 8
- 230000001939 inductive effect Effects 0.000 claims description 7
- 230000003247 decreasing effect Effects 0.000 claims description 5
- 230000001276 controlling effect Effects 0.000 description 10
- 230000005284 excitation Effects 0.000 description 8
- 238000010586 diagram Methods 0.000 description 6
- 230000010363 phase shift Effects 0.000 description 4
- 238000011217 control strategy Methods 0.000 description 3
- 230000009977 dual effect Effects 0.000 description 3
- 230000009286 beneficial effect Effects 0.000 description 1
- 230000033228 biological regulation Effects 0.000 description 1
- 238000006243 chemical reaction Methods 0.000 description 1
- 230000002596 correlated effect Effects 0.000 description 1
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention discloses a kind of multiport energy accumulation current converters that more distributed energy storages can be achieved, single-phase full bridge rectifier connects net side power supply, the single-phase full bridge rectifier is by two pairs of bridge arms, voltage on line side source, net side inductance and net side resistance composition, the DC bus side of single-phase full bridge rectifier is serially connected with the DC voltage divider being made of half-bridge structure and neutral inductance, to realize that DC link output end or more condenser voltage is unbalanced；The output end of DC voltage divider connects first capacitor C1With the second capacitor C2Partial pressure is to realize two direct current output ports；Two direct current output ports concatenate a double active full-bridge bidirectional DC-DC converter respectively, realize voltage isolation, the end parallel connection of two double active full-bridge bidirectional DC-DC converters is to realize three ports；Each double active full-bridge bidirectional DC-DC converters are made of a high-frequency isolation transformer and two H bridges for being located at transformer primary pair side respectively.To and fro flow of power can be achieved in the present invention, and improves the power quality of grid-connected current.
Description
Technical Field
The invention relates to the field of energy storage converters, in particular to a multi-port energy storage converter capable of realizing multi-distributed energy storage and a method.
Background
Currently, energy storage converters have been widely used due to the ever-increasing demand for energy storage in modern power distribution systems. For this type of power conversion system, it can be easily integrated into the grid by controlled power regulation to reduce the effects of load or power supply fluctuations.
Among different types of energy storage devices, batteries are widely used due to their advantages of good safety, high reliability, large capacity, long service life, and the like. For the DC output of the battery, an AC/DC converter is necessary as an efficient interface between the mains supply and the battery. In addition, since the output voltage of a single battery set is much lower than the direct-current voltage required for grid integration, a DC/DC boost device is essential for a distributed battery system. Furthermore, a single distributed energy storage system typically requires an energy storage device to connect multiple batteries with different characteristics. In this case, a plurality of DC/DC converters are generally employed to integrate a plurality of batteries into a system.
Disclosure of Invention
The invention aims to overcome the defects in the prior art, and provides a multi-port energy storage converter and a method for realizing multi-distributed energy storage, which aim to realize multi-port charging of multi-distributed energy storage, independently control charging of a plurality of batteries, reduce cost and improve flexibility. The double-active full-bridge bidirectional DC-DC converter (DAB) adopts a device for phase-shift control and excitation removal of direct current magnetic bias, realizes bidirectional power flow, and improves the electric energy quality of grid-connected current.
The purpose of the invention is realized by the following technical scheme:
a multi-port energy storage converter capable of realizing multi-distributed energy storage is characterized in that a single-phase full-bridge rectifier is connected with a grid-side power supply and consists of two pairs of bridge arms, a grid-side voltage source, a grid-side inductor and a grid-side resistor, and a direct-current bus side of the single-phase full-bridge rectifier is connected with a direct-current voltage divider consisting of a half-bridge structure and a neutral inductor in series so as to realize unbalanced voltage of an upper capacitor and a lower capacitor at the output end of a direct-current link; the output end of the DC voltage divider is connected with a first capacitor C1And a second capacitor C2Voltage division is carried out to realize two direct current output ports; the two direct current output ports are respectively connected in series with a double-active full-bridge bidirectional DC-DC converter to realize voltage isolation, and the tail ends of the two double-active full-bridge bidirectional DC-DC converters are connected in parallel to realize three ports; each double-active full-bridge bidirectional DC-DC converter is respectively composed of a high-frequency isolation transformer and two H-bridges positioned on the primary side and the secondary side of the transformer.
A control method capable of realizing multi-distributed energy storage comprises the following steps:
(1) controlling the single-phase full-bridge rectifier to obtain stable output voltage at the direct current side;
(2) controlling the direct-current voltage divider to realize voltage division of a direct-current bus;
(3) controlling a double-active full-bridge bidirectional DC-DC converter, wherein the double-active full-bridge bidirectional DC-DC converter realizes power bidirectional flow by adopting phase-shifting control;
(4) the double-active full-bridge bidirectional DC-DC converter adopts a feedback compensation method to inhibit the DC magnetic bias phenomenon.
Further, the control method in the step (2) comprises the following steps:
through I1And I2Respectively representing the current passing through a first capacitor and a second capacitor on a direct current bus, and defining a neutral point inductive current INIs (I)2-I1+I0) Defining the voltage difference DeltaV as (V)1-V2) The formula in the complex frequency domain is expressed as:
IN＝-SC×ΔV+I0
(1-1)
where s is a variable in the complex frequency domain, INIs a neutral point inductor current, I0The direct current side is the neutral current of two clamping capacitors respectively connected with the battery in parallel, delta V is the voltage difference between a first capacitor and a second capacitor, and C is a capacitor;
when the capacitor voltage is asymmetric, the total voltage VdcAnd a voltage V of the difference voltage DeltaV output by the first capacitor and the second capacitor respectively1And V2Respectively obtaining the sum and the difference; the neutral point inductor current I can be obtained from the formula (1-1)NChanging the polarity according to the polarity of the voltage difference value delta V; thus, if Δ V increases, the inductor INThe neutral load current is compensated and the voltage difference av is kept at the set value and by decreasing V2Or increase V1And is decreased;
the control formula of the direct current voltage divider is as follows:
wherein,s is a variable of the complex frequency domain, KP-vl2Is the proportionality coefficient, K, of the voltage loop of the DC voltage dividerI-vl2Is the integral coefficient of the voltage loop of the DC voltage divider, sigma-delta V, sigma*Is a given value of the voltage difference sigma,is a neutral inductor current INThe command signal of (1);
where s is a variable in the complex frequency domain, KP-cl2Is the proportionality coefficient of the current loop, KI-cl2Is the integral coefficient, V, of the current loop of a DC voltage dividermIs a switching function of the PWM output.
Further, in the step (4):
the method comprises the following steps of extracting a direct current component by adopting a feedback compensation method, reducing the direct current component by utilizing a proportional-integral regulator, and introducing a feedback signal of a PWM driving pulse to realize feedback compensation, wherein a control formula in a complex frequency domain is as follows:
where s is a variable in the complex frequency domain, ImIs the direct component of the inductive current in a dual active bridge DC-DC converter, IbIs a feedback compensation component, KP-biasIs the proportionality coefficient, KI-biasIs the integral coefficient.
Compared with the prior art, the technical scheme of the invention has the following beneficial effects:
1. the invention can be connected with the power grid through a single-phase full-bridge rectifier, and the voltage at the output end of a direct current link is divided into an upper part and a lower part by using a direct current voltage divider. The DC link port is then connected to another isolated DC link through two dual active full bridge bidirectional DC-DC converters. And meanwhile, the direct current voltage divider is used for realizing voltage division and phase-shifting control of the double-active full-bridge bidirectional DC-DC converter, and the voltage of each direct current link can be independently adjusted to meet the battery control requirement without any obvious interference. By using this architecture, multiple independently controlled batteries can reduce cost and increase flexibility.
2. Compared with the traditional multi-port energy storage converter, the converter has the characteristics of low cost, high flexibility and the like; the invention considers the influence of the direct current excitation of the transformer in the double-active full-bridge bidirectional DC-DC converter (DAB) on the current quality, and excites the direct current magnetic bias by a feedback compensation method, so that the current quality is better.
Drawings
Fig. 1 is a topology structure diagram of the energy storage converter of the present invention.
Fig. 2-1 to fig. 2-4 are schematic diagrams of the control method of the energy storage converter.
Fig. 3 is a diagram of the voltage and current waveforms on the grid side of the energy storage converter.
FIG. 4 is a diagram of the output voltage waveform of each port of the energy storage converter and the inductor current waveform on the neutral line of the voltage divider circuit according to the present invention.
FIG. 5 is a simulated waveform diagram of the primary and secondary currents of the dual-active full-bridge bi-directional DC-DC converter before the DC bias is removed.
Fig. 6 is a simulated waveform diagram of primary side and secondary side currents of the dual-active full-bridge bidirectional DC-DC converter after excitation of direct current magnetic bias.
Detailed Description
The topology, the specific control method and the method for exciting the DC bias of the transformer in the dual-active full-bridge DC-DC converter of the multi-distributed energy-storage multi-port energy-storage converter of the present invention are described below with reference to the accompanying drawings, so as to enable those skilled in the art to better understand the present invention.
As shown in figure 1, the multi-port energy storage converter is composed of four parts, the first part is a single-phase full-bridge rectifier and consists of two pairs of bridge arms, a network side voltage source, a network side inductor and a network side resistor, the system is integrated into a power grid, and the output end of a direct current link of the rectifier is connected with two clamping capacitors C1And C2The voltage is divided to realize two direct current output ports. Due to the requirements on different types of loads and energy storage systems, the second part introduces a direct-current voltage divider structure to realize unbalanced voltage of an upper capacitor and a lower capacitor at the output end of a direct-current link, and the direct-current voltage divider is composed of a half-bridge structure and a neutral inductor and is connected to the direct-current bus side of a single-phase full-bridge rectification circuit in series. The third and fourth parts of fig. 1 are two dual-active full-bridge bidirectional DC-DC converters (DAB) respectively connected in series at the upper and lower two ports of the DC bus side of the DC voltage divider, to implement voltage isolation, and the ends of the two dual-active full-bridge bidirectional DC-DC converters (DAB) are connected in parallel to implement three ports. Each double-active full-bridge bidirectional DC-DC converter (DAB) is respectively composed of a high-frequency isolation transformer and two H-bridges positioned on the primary side and the secondary side of the transformer.
As shown in fig. 2-1 to 2-4, the basic steps of the control strategy and the method for exciting the dc bias based on the multi-port energy storage converter for realizing distributed energy storage are as follows:
step 1: controlling the single-phase full-bridge rectifier to obtain a stable output voltage V at the output end of the DC linkdcThe complex frequency domain control formula of the single-phase full-bridge rectifier is as follows:
where s is a variable in the complex frequency domain, I*Is a guide signal of the network side inductor current I, KP-vl1Is the proportional coefficient of voltage, KI-vl1Is the integral coefficient of the voltage, VrefIs a reference value of the output side direct current voltage, and theta is an output phase angle of the network side phase-locked loop.
VPWM＝[(I*-I)×GPR(s)+Vs]/Vdc(2)
Wherein, VPWMIs the switching function of the pulse width modulated PWM output shown in FIG. 2-1, GPR(s) is the switching function of the proportional resonant controller, VsIs the input voltage of the grid side voltage source.
Where s is a variable in the complex frequency domain, KP-cl1Is the proportionality coefficient, KR-cl1Is the resonance control coefficient, ωcIs the cut-off frequency, omega, of the resonant control0Is the fundamental frequency in radians and k is the control coefficient for the fundamental frequency.
Step 2: and controlling the direct-current voltage divider, wherein in order to realize the division of the output voltage of the direct-current link, the control strategy of the direct-current voltage divider is as follows.
Let I1And I2Respectively representing the current through the two clamp capacitors on the dc bus. In addition, the neutral inductance current INIs defined as (I)2-I1+I0) The voltage difference Δ V is defined as (V)1-V2)，I0The two capacitors on the direct current side are respectively connected with the neutral line current of the battery in parallel.
Vdc＝V1+V2(4)
ΔV＝V1-V2(5)
IN＝I2-I1+I0(6)
Multiplication of formula (6) on both sidesC is capacitance, to
IN＝-sC×ΔV+I0(9)
The principle of the dc voltage divider is to control the measurement current to reach the reference current every switching cycle. When the capacitor voltage is asymmetric, the total voltage VdcThe sum-difference voltage DeltaV is derived from the output voltage V of the capacitor1And V2The sum and difference of (a) are obtained separately. From equation (9), the neutral point inductor current INThe polarity is changed according to the polarity of the voltage difference Δ V. Thus, if Δ V increases, the inductor INThe neutral load current is compensated and the voltage difference av is kept at the set value and by decreasing V2Or increase V1And decreases.
The control formula of the direct current voltage divider is as follows:
where s is a variable in the complex frequency domain, KP-vl2Is the proportionality coefficient, K, of the voltage loop of the DC voltage dividerI-vl2Is the integral coefficient of the voltage loop of the dc voltage divider. σ ═ Δ V, σ*Is a given value of the voltage difference sigma.Is a neutral inductor current INThe command signal of (2).
Where s is a variable in the complex frequency domain, KP-cl2Is the proportionality coefficient of the current loop, KI-cl2Is the integral coefficient of the current loop of the dc voltage divider. VmIs the switching function of the pulse width modulated PWM output shown in fig. 2-2.
And step 3: and controlling a double-active full-bridge bidirectional DC-DC converter (DAB), wherein the double-active full-bridge bidirectional DC-DC converter realizes power bidirectional flow by adopting phase-shift control.
The structure of the double-active full-bridge bidirectional DC-DC converter is symmetrical, and the phase-shifting control is mainly used for controlling the driving pulses of the two full-bridge converters to transmit energy by using the leakage inductance of the high-frequency transformer. In the first and second stages, a phase-shifted signal is generated by adjusting the phase angle of the other side to change the voltage of the leakage inductance, thereby controlling the magnitude and direction of power flow. The operation is bidirectional, that is, each H-bridge can be considered as a primary or secondary, depending on the direction of power flow. The phase shift equation (delta) is
Where s is a variable in the complex frequency domain, T is a one-cycle delay, δ is a phase shift angle, KP1Is the proportionality coefficient, KI1Is the integral coefficient, Vdc-refIs a reference value V of the DC voltage at the output end of the dual-active full-bridge bidirectional DC-DC converterdc-DABThe actual output direct-current voltage of the output end of the double-active full-bridge bidirectional DC-DC converter is obtained.
And 4, step 4: the double-active full-bridge bidirectional DC-DC converter adopts a feedback compensation method to inhibit direct current magnetic bias.
Usually, the excitation current of the transformer is small and negligible. If the current input to the transformer contains a dc component, it may cause a dc bias in the transformer. At this time, the excitation current may vary significantly, and its peak value may reach several times or several tens of times of the normal value. In addition, the direct current magnetic biasing can cause the transformer to have high temperature, the vibration noise is large, and even an insulating layer of the transformer can be burnt.
And a feedback compensation method is adopted, the direct current component is directly extracted, the direct current component is reduced by utilizing a PI regulator, and a feedback signal of a PWM driving pulse is introduced, so that feedback compensation is realized. The control formula is as follows:
where s is a variable in the complex frequency domain, ImIs the direct current component of the inductive current in a dual-active full-bridge bidirectional DC-DC converter, IbIs a feedback compensation component, KP-biasIs the proportional coefficient of the controller, KI-biasIs the integral coefficient of the controller.
The double-active full-bridge bidirectional DC-DC converter (DAB) control structure with the excitation direct-current magnetic bias controller can ensure the proper distribution of the voltage among three direct-current buses and the balance of the voltage of each port.
And 5: and (3) building a simulation model shown in figure 1 by Matlab/Simulink, and verifying the converter control method provided by the invention.
FIG. 3 shows the net side voltage and current, FIG. 4 shows the total DC link output voltage of the single-phase full-bridge rectifier and the V output of the DC voltage divider1And V2. As can be seen from fig. 3, the grid-side current and the grid-side voltage form a sinusoidal phase, and as can be seen from fig. 4, by controlling the reference voltage value of the output voltage of the dc link, the total output voltage of the dc link is controlled to be 560V, and by controlling the voltage difference value of the dc link, the voltage imbalance of the dc link is realized, so as to adapt to different voltage levels of the battery.
In fig. 4, the voltage difference reference values of the dc bus are set to 0V, 10V and 20V for time intervals 0.3, 0.4, 0.6 and 0.6, 0.8. In t ∈ [0.3, 0.4], FIG. 4 shows the balanced voltage output without the DC voltage divider in the DC bus; when t belongs to [0.4, 0.6], the voltage difference value of the upper bus and the lower bus is adjusted to be 10V; when t belongs to [0.6, 0.8], the voltage difference of the upper bus and the lower bus is adjusted to be 20V, the output high voltage reaches 290V, and the output low voltage reaches 270V. As can be seen from fig. 4, the control method of the present invention can ensure that the reference value of the tracking voltage difference (Δ V) realizes the asymmetric dc bus voltage. Also, the magnitude of the neutral current is positively correlated to the voltage difference. In addition, the voltage difference between the two ports can be set according to actual requirements.
Fig. 5 shows the voltage at the output side of the dual-active full-bridge bidirectional DC-DC converter (DAB) and the primary and secondary inductive currents without direct-current excitation, and fig. 6 shows the voltage at the output side of the dual-active full-bridge bidirectional DC-DC converter (DAB) and the primary and secondary inductive currents after direct-current excitation. Fig. 5 and 6 show that a dual active full-bridge bidirectional DC-DC converter (DAB) with two parallel output ports achieves output port voltage stabilization at 320V. In addition, fig. 5 shows that the primary side current and the secondary side current of the transformer generate a severe dc magnetic bias phenomenon of the transformer due to the dc component in the primary and secondary side inductive currents of the transformer. Therefore, a dc component is proposed, and a feedback compensation method is used to eliminate dc biases on the primary side and the secondary side, as shown in fig. 6.
In conclusion, the energy storage converter can overcome the design challenge faced by an energy storage system in the application of different input and output voltage grades, a control strategy of direct current bus voltage division under unbalanced voltage is designed, bipolar direct current bus voltage can be independently adjusted to a required value, in addition, direct current bias is excited and removed by using a feedback compensation method, and the stability of the system is improved.
The present invention is not limited to the above-described embodiments. The foregoing description of the specific embodiments is intended to describe and illustrate the technical solutions of the present invention, and the above specific embodiments are merely illustrative and not restrictive. Those skilled in the art can make many changes and modifications to the invention without departing from the spirit and scope of the invention as defined in the appended claims.
Claims (4)
1. A multi-port energy storage converter capable of realizing multi-distributed energy storage is characterized in that a single-phase full-bridge rectifier is connected with a grid-side power supply, the single-phase full-bridge rectifier consists of two pairs of bridge arms, a grid-side voltage source, a grid-side inductor and a grid-side resistor, and a direct-current bus side of the single-phase full-bridge rectifier is connected with a direct-current voltage divider consisting of a half-bridge structure and a neutral inductor in series so as to realize unbalanced voltage of an upper capacitor and a lower capacitor at the output end of a direct; the output end of the DC voltage divider is connected with a first capacitor (C)1) And a second capacitance (C)2) Voltage division to realize two DC output endsA mouth; the two direct current output ports are respectively connected in series with a double-active full-bridge bidirectional DC-DC converter to realize voltage isolation, and the tail ends of the two double-active full-bridge bidirectional DC-DC converters are connected in parallel to realize three ports; each double-active full-bridge bidirectional DC-DC converter is respectively composed of a high-frequency isolation transformer and two H-bridges positioned on the primary side and the secondary side of the transformer.
2. A control method capable of realizing multi-distributed energy storage is based on the multi-port energy storage converter of claim 1, and is characterized by comprising the following steps:
(1) controlling the single-phase full-bridge rectifier to obtain stable output voltage at the direct current side;
(2) controlling the direct-current voltage divider to realize voltage division of a direct-current bus;
(3) controlling a double-active full-bridge bidirectional DC-DC converter, wherein the double-active full-bridge bidirectional DC-DC converter realizes power bidirectional flow by adopting phase-shifting control;
(4) the double-active full-bridge bidirectional DC-DC converter adopts a feedback compensation method to inhibit the DC magnetic bias phenomenon.
3. The control method capable of realizing multi-distributed energy storage according to claim 2, wherein the control method in step (2) comprises the following steps:
through I1And I2Respectively representing a first capacitance (C) on the DC bus1) And a second capacitance (C)2) The current passed through defines the neutral point inductance current INIs (I)2-I1+I0) Defining the voltage difference DeltaV as (V)1-V2) The formula in the complex frequency domain is expressed as:
IN＝-sC×ΔV+I0(1-1)
where s is a variable in the complex frequency domain, INIs a neutral point inductor current, I0The neutral current of two clamping capacitors connected in parallel with the battery at the DC side, and Δ V is the first capacitor (C)1) And a second capacitance (C)2) The voltage difference between them, C is the capacitance;
when the capacitor voltage is not rightTime-scale, total voltage VdcThe sum-difference voltage DeltaV is formed by a first capacitor (C)1) And a second capacitance (C)2) Respectively output voltage V1And V2Respectively obtaining the sum and the difference; the neutral point inductor current I can be obtained from the formula (1-1)NChanging the polarity according to the polarity of the voltage difference value delta V; thus, if Δ V increases, the inductor INThe neutral load current is compensated and the voltage difference av is kept at the set value and by decreasing V2Or increase V1And is decreased;
the control formula of the direct current voltage divider is as follows:
where s is a variable in the complex frequency domain, KP-vl2Is the proportionality coefficient, K, of the voltage loop of the DC voltage dividerI-vl2Is the integral coefficient of the voltage loop of the DC voltage divider, sigma-delta V, sigma*Is a given value of the voltage difference sigma,is a neutral inductor current INThe command signal of (1);
where s is a variable in the complex frequency domain, KP-cl2Is the proportionality coefficient of the current loop, KI-cl2Is the integral coefficient, V, of the current loop of a DC voltage dividermIs a switching function of the PWM output.
4. The control method capable of realizing multi-distributed energy storage according to claim 2, wherein in the step (4): the method comprises the following steps of extracting a direct current component by adopting a feedback compensation method, reducing the direct current component by utilizing a proportional-integral regulator, and introducing a feedback signal of a PWM driving pulse to realize feedback compensation, wherein a control formula in a complex frequency domain is as follows:
where s is a variable in the complex frequency domain, ImIs the direct current component of the inductive current in a dual-active full-bridge bidirectional DC-DC converter, IbIs a feedback compensation component, KP-biasIs the proportionality coefficient, KI-biasIs the integral coefficient.
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| CN110149053A (en) * | 2019-05-22 | 2019-08-20 | 湖南大学 | The suppressing method of three port isolation DC/DC formula converter transient DCs biasing |
| CN110212776A (en) * | 2019-06-14 | 2019-09-06 | 哈尔滨工业大学 | A kind of three port DC-DC converter of hybrid energy-storing and its power distribution control method |
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| CN111756250A (en) * | 2020-05-31 | 2020-10-09 | 中车永济电机有限公司 | Control method for restraining transformer magnetic biasing in high-frequency full-bridge DC/DC converter |
| CN112710922A (en) * | 2020-12-15 | 2021-04-27 | 西南交通大学 | Open-circuit fault diagnosis method for double-active-bridge DC-DC converter |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN110149053A (en) * | 2019-05-22 | 2019-08-20 | 湖南大学 | The suppressing method of three port isolation DC/DC formula converter transient DCs biasing |
| CN110212776A (en) * | 2019-06-14 | 2019-09-06 | 哈尔滨工业大学 | A kind of three port DC-DC converter of hybrid energy-storing and its power distribution control method |
| CN110481361A (en) * | 2019-08-08 | 2019-11-22 | 西安工业大学 | The vehicle-mounted two-way charger centerline construction of electric car and its control method |
| CN111756250A (en) * | 2020-05-31 | 2020-10-09 | 中车永济电机有限公司 | Control method for restraining transformer magnetic biasing in high-frequency full-bridge DC/DC converter |
| CN111756250B (en) * | 2020-05-31 | 2022-08-05 | 中车永济电机有限公司 | Control method for restraining transformer magnetic biasing in high-frequency full-bridge DC/DC converter |
| CN112710922A (en) * | 2020-12-15 | 2021-04-27 | 西南交通大学 | Open-circuit fault diagnosis method for double-active-bridge DC-DC converter |
| US11817701B2 (en) | 2021-01-29 | 2023-11-14 | Eaton Intelligent Power Limited | Multi-port split-phase power system |
| CN112993971A (en) * | 2021-03-12 | 2021-06-18 | 清华大学 | Bipolar bidirectional DC-DC converter with function of inhibiting direct-current voltage unbalance |
| CN112993970A (en) * | 2021-03-12 | 2021-06-18 | 清华大学 | Bipolar bidirectional boost-buck DC-DC converter with function of inhibiting direct-current voltage unbalance |
| CN112993971B (en) * | 2021-03-12 | 2022-07-01 | 清华大学 | Bipolar bidirectional DC-DC converter with function of inhibiting direct-current voltage unbalance |
| CN112993970B (en) * | 2021-03-12 | 2022-09-09 | 清华大学 | Bipolar bidirectional boost-buck DC-DC converter with function of inhibiting direct-current voltage unbalance |
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