CN109167524B - Three-phase alternating-current/direct-current buck-boost conversion circuit and control method thereof - Google Patents
Three-phase alternating-current/direct-current buck-boost conversion circuit and control method thereof Download PDFInfo
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- CN109167524B CN109167524B CN201811311963.8A CN201811311963A CN109167524B CN 109167524 B CN109167524 B CN 109167524B CN 201811311963 A CN201811311963 A CN 201811311963A CN 109167524 B CN109167524 B CN 109167524B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
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Abstract
The invention discloses a three-phase alternating current-direct current buck-boost conversion circuit and a control method thereof, wherein the conversion circuit comprises an input switch tube group, a rectification switch unit and an energy storage freewheeling unit, the input switch tube group comprises a first switch tube, a second switch tube, a third switch tube, a fourth switch tube, a sixth switch tube and an energy storage freewheeling unit, and the energy storage freewheeling unit comprises a seventh diode, an eighth diode, a seventh switch tube, a first freewheeling inductor, a second freewheeling inductor and a capacitor. The conversion circuit has a simple structure and a simple control method, so that the advantages are obvious in the wide application of the medium and small power output voltage range and in the occasions where high efficiency and high power density are required.
Description
Technical Field
The invention relates to the field of power electronics, in particular to a three-phase alternating-current/direct-current buck-boost conversion circuit and a control method thereof.
Background
Because the requirements of national regulations or the environment of an electric system on electric equipment are higher and higher, the electric equipment adopting three-phase power supply is gradually changed from a single-phase power supply mode to exceed a certain power single-phase power supply mode, and power factor correction is required to ensure the electric energy quality of a power grid and reduce the impact on the power grid, for example, an early electric automobile charger is only 3.3KW, and then is gradually increased to 6.6KW,10KW or even higher, and the like, if the Power Factor Correction (PFC) function is not available, the electric energy quality of the power grid is greatly damaged, and even the power grid is seriously paralyzed.
In addition, the output voltage range of the device may be wider, or the device demand voltage may be around the three-phase uncontrolled rectification range. Therefore, if the PFC (power factor correction) function is required, it is generally a three-level boost type, as shown in fig. 1, which is a more common three-level structure, and then the DC/DC converter circuit is added to the back end to process the three-phase ac input ac/DC converter circuit into a desired output voltage. Therefore, there is another buck PFC circuit, such as the Swiss rectifier shown in fig. 2, and there is a method of 6-switch buck PFC, which can output a voltage of 1.5 times the peak voltage of the phase voltage, if the output requirement voltage exceeds the voltage range, the back end must be processed into the desired output voltage by a boost scheme, and the DC/DC conversion circuit of one stage is matched, as shown in fig. 3, which omits the trouble of high bus voltage, but the cost of the two-stage scheme is still higher, and meanwhile, the efficiency is reduced due to the two-stage conversion, so we have to propose a better scheme to solve the related problems.
The foregoing background is only for the purpose of providing an understanding of the inventive concepts and technical aspects of the present application and is not necessarily prior art to the present application and is not intended to be used as an aid in the evaluation of the novelty and creativity of the present application in the event that no clear evidence indicates that such is already disclosed at the date of filing of the present application.
Disclosure of Invention
The invention aims to provide a novel three-phase direct current buck-boost converter circuit and a control method thereof, which are used for solving the technical problems of limited efficiency and volume or relatively high cost requirement in the prior art.
In a first aspect, the invention provides a three-phase ac/dc buck-boost conversion circuit, which comprises an input switch tube group, a rectification switch unit and an energy storage freewheeling unit, wherein the input switch tube group comprises first to third switch tubes, the rectification switch unit comprises first to sixth diodes and fourth to sixth switch tubes, and the energy storage freewheeling unit comprises a seventh diode, an eighth diode, a seventh switch tube, first to second freewheeling inductors and a capacitor;
The drains of the first switching tube and the third switching tube are respectively connected with the three-phase alternating current input end, and the sources of the first switching tube and the third switching tube are respectively connected with the three input ends of the rectifying switch unit; the cathode of the first diode is connected with the cathode of the second diode and the cathode of the third diode, and is also connected with the cathode of the seventh diode and one end of the first free-wheeling inductor, the anode of the fourth diode is connected with the anode of the fifth diode and the anode of the sixth diode, and is also connected with the anode of the seventh diode and one end of the second free-wheeling inductor, the drain electrode of the fourth switch is connected with the cathode of the fourth diode, the drain electrode of the fifth switch is connected with the cathode of the fifth diode, the drain electrode of the sixth switch is connected with the cathode of the sixth diode, the source electrode of the fourth switch is connected with the anode of the first diode and the source electrode of the first switch, the drain electrode of the fifth switch is connected with the anode of the second diode and the source electrode of the second switch, and the drain electrode of the sixth switch is connected with the anode of the third diode and the source electrode of the third switch;
the other end of the first freewheel inductor is connected with the drain electrode of the seventh switching tube, the other end of the second freewheel inductor is connected with the source electrode of the seventh switching tube, a capacitor is connected between the positive bus end and the negative bus end, and an eighth diode is connected in series between the common end of the first freewheel inductor and the seventh switching tube and one end of the capacitor and/or between the common end of the second freewheel inductor and the seventh switching tube and the other end of the capacitor to serve as a freewheel diode.
Further, the first freewheel inductor and the second freewheel inductor are two windings of the energy-storage transformer with an air gap in the magnetic loop; one of the first freewheel inductor and the second freewheel inductor is reserved.
Further, the first to seventh switching transistors are driven by the same driving signal or are each driven by an independent driving signal; the first to seventh switching tubes are semiconductor devices which are controlled to be turned on and off by high-frequency driving signals and are provided with anti-parallel diodes, and the anti-parallel diodes are integrated diodes, parasitic diodes or externally-added diodes.
The three-phase three-wire power supply is connected to the input switch tube group after being filtered by the input filter.
In a second aspect, the present invention further provides a three-phase ac/dc buck-boost converter circuit, which includes at least two of the three-phase ac/dc buck-boost converter circuits, where each three-phase ac/dc buck-boost converter circuit is connected in parallel or in staggered parallel according to 1/N cycle, and N is the number of three-phase ac/dc buck-boost converter circuits.
In a third aspect, the present invention further provides a control method for the three-phase ac/dc buck-boost conversion circuit of the first aspect, including the following steps:
According to the phase locking judgment of the input three-phase three-wire power supply voltage signals, analyzing the phase and the interval section of each phase of power supply at the current moment;
Applying driving signals to all switching tubes on three-phase lines under the current interval section to conduct PWM driving control, so that two phases with higher absolute amplitude values between three-phase three-wire power supplies form a current conducting loop;
judging whether to turn on a switching tube in the energy storage follow current unit according to the amplitude difference value of two phases forming the current conduction loop, if so, turning off PWM driving of an eighth switching tube after the driving time is calculated according to control and calculation to be met;
The one-phase circuit with lower amplitude absolute value in two phases forming a current conducting circuit is turned off, so that a diode on the one-phase circuit with the smallest amplitude absolute value of the voltage of the three phases is forward biased, and forms a current circuit with the phase with the highest amplitude;
and turning off driving signals of all the switching tubes, and carrying out follow current through a seventh diode, a first follow current inductor, an eighth diode and a second follow current inductor of the energy storage follow current unit.
Further, in a certain interval, if the maximum amplitude difference value between two phases exceeds the value of the output voltage by less than a threshold value or equal to zero, the two phases are conducted in a single period, a seventh switching tube is turned on, and PWM driving of an eighth switching tube is turned off according to control calculation driving time delay; and switching off a communication path with a lower absolute value of amplitude values in the two conducted phases.
Further, analyzing the phase and interval section of each phase of power supply at the current moment; the amplitude absolute value of the voltage of each phase power supply is analyzed, a 'long' PWM driving signal with the same size is applied to a corresponding switching tube in an alternating current loop with the highest amplitude absolute value and the lowest amplitude absolute value, meanwhile, a 'short' PWM driving signal is applied to a corresponding switching tube in an alternating current loop with the next amplitude absolute value, two phases with higher amplitude absolute values form a current loop, meanwhile, the inductance forms partial pressure energy storage, after the 'short' PWM driving signal is closed, the switching tubes of the two phases applying the 'long' PWM driving signal provide a follow current path for the inductance to conduct continuously, and the specific duty ratio of the 'long' PWM driving signal is determined by a real-time control operation result.
Further, the time of conducting the current is positively correlated with the amplitude of the phase voltage, i.e. the higher the amplitude absolute value, the longer the current conducting time, the current conducting time of the phase with the largest amplitude absolute value being equal to the sum of the current conducting times of the two phases with relatively lower amplitude absolute values.
Further, the switching tube connected with the three-phase alternating current is not applied with a driving signal at the same time, firstly, two phases with higher amplitude and opposite polarity are applied with signals to conduct the signals, then, the passage in the same direction as the phase with the lowest amplitude absolute value is closed, and the switching tube on the alternating current loop which is not opened before is opened to enable the follow current to pass through the phase with the lowest amplitude absolute value.
Further, whether circulation exists among the three-phase direct current converters connected in parallel is judged according to the current values of the first free-wheeling inductor and the second free-wheeling inductor, and the long PWM driving signal, the short PWM driving signal or the ratio of turns of the first free-wheeling inductor to turns of the second free-wheeling inductor is adjusted according to the current values so as to realize loop impedance adjustment.
In a fourth aspect, the present invention further provides a control method for the three-phase ac/dc buck-boost converter circuit of the second aspect, where the control method controls at least two parallel-connected three-phase ac/dc buck-boost converter circuits respectively, and the working phases of the N parallel-connected three-phase ac/dc buck-boost converter circuits differ by 1/N high frequency cycles.
Compared with the prior art, the invention has the beneficial effects that:
The invention overcomes the defect of high voltage at the rear end of the traditional boost PFC circuit in structure, so that the limitation of a power device of a direct current converter at the rear end is reduced, the choice is larger, meanwhile, the boost-buck type alternating current-direct current conversion circuit provided by the invention also changes the realization mode of the traditional boost or buck type, and the output voltage has smaller limitation compared with the alternating current input, can be boosted, can be reduced, and can even be voltage in a phase difference amplitude; meanwhile, the whole AC-DC conversion circuit is simple, the control logic is simple, the efficiency is high, the AC-DC conversion circuit is suitable for occasions with high efficiency and high power density, and the advantages of replacing the traditional passive PFC are very obvious;
Functionally, the topology structure combined control method can effectively ensure that the current conduction of each phase circuit has better power factor, meanwhile, because the free-wheeling diode D7 and the symmetrical inductor (the first free-wheeling inductor L1 and the second free-wheeling inductor L2) are arranged, the output side and the alternating current side are isolated through the two inductors when the D7 is in free-wheeling, namely, a loop and the input alternating current are not in current conduction connection during the D7 free-wheeling, the virtual relative potential of the output side is more stable, and the EMI performance of the non-isolated converter is improved.
In terms of control, due to structural simplification, the reduction of power components and the unification of switching driving potential, the control difficulty is further reduced, and from the aspect of switching operation of PFC (power factor correction) functions, a control method is simplified by applying regular or logical combined PWM driving signals to switching tubes of each phase or switching on a boost tube according to judgment of output voltage. And simultaneously, the positive and negative current loop impedance between the parallel circuits is changed by adjusting the on time of each phase of loop, so that cross loop current is avoided.
Therefore, the invention has obvious advantages in high power density occasions, such as three-phase PFC below 10 KW.
Drawings
Fig. 1 is a schematic diagram of a conventional boost PFC circuit.
Fig. 2 is a schematic diagram of a conventional buck PFC circuit.
Fig. 3 is a schematic diagram of a dc output block of the prior art.
Fig. 4 is a schematic diagram of a three-phase ac/dc buck-boost converter circuit according to embodiment 1 of the present invention.
Fig. 5 is a schematic diagram of three-phase voltage waveforms and junction definition according to embodiment 1 of the present invention.
Fig. 6 is a schematic diagram of an AC-BC interval AB phase conduction loop of embodiment 1 of the present invention.
Fig. 7 is a schematic diagram of a two-phase conduction loop in the AC-BC interval AB of embodiment 1 of the present invention.
Fig. 8 is a schematic diagram of the AC-O interval BC phase-sequence loop of embodiment 1 of the present invention.
Fig. 9 is a schematic diagram of an AC-BC interval inductor current freewheel loop according to embodiment 1 of the present invention.
Fig. 10 is a schematic diagram of an O-BC interval AC phase-sequence loop of embodiment 1 of the present invention.
Fig. 11 is a schematic diagram of an O-BC interval AC phase-sequence loop of embodiment 1 of the present invention.
Fig. 12 is an equivalent transformation schematic of embodiment 1 of the present invention.
Fig. 13 is a schematic diagram of a potential equivalent transformation waveform of embodiment 1 of the present invention.
Fig. 14 is a schematic diagram showing the relationship between driving waveforms of each switch group in the three-phase ac cycle according to embodiment 1 of the present invention.
Fig. 15 is a schematic structural view of modified example 2 of example 1 of the present invention.
Fig. 16 is a schematic current diagram of embodiment 2 of the present invention.
Fig. 17 is an equivalent transformation diagram 1 of embodiment 1 of the present invention.
Fig. 18 is an equivalent transformation diagram 2 of embodiment 1 of the present invention.
Fig. 19 is an equivalent transformation diagram 3 of embodiment 1 of the present invention.
Fig. 20 is an equivalent transformation diagram 4 of embodiment 1 of the present invention.
Detailed Description
The invention will be described in further detail with reference to the following detailed description and with reference to the accompanying drawings. It should be emphasized that the following description is merely exemplary in nature and is in no way intended to limit the scope of the invention or its applications.
Non-limiting and non-exclusive embodiments will be described with reference to the following drawings, in which like reference numerals refer to like elements unless otherwise specified.
Example 1:
Fig. 4 shows a three-phase ac/dc buck-boost conversion circuit according to the present invention, which includes an input switch tube group, a rectifying switch unit and an energy storage freewheeling unit, wherein the input switch tube group includes three switch tubes Q1 to Q3, and the three switch tubes Q1 to Q3 are respectively disposed on three phase lines (or connected through an input filter) of an accessed three-phase three-wire power supply; the three switching tubes Q1-Q3 are respectively connected with the rectification switching unit; the drains of the switching tubes Q1-Q3 are respectively connected with a three-phase alternating current input end (or an input filter end), and the sources of the switching tubes Q1-Q3 are respectively connected with three input ends of the rectifying switch unit. The rectification switch unit is a unit which is formed by adding a switch tube at the lower end of a three-phase uncontrolled diode rectifier bridge, and is specifically connected with the cathode of a diode D1, the cathode of a diode D2 and the cathode of a diode D3, and simultaneously connected with the cathode of a freewheeling diode D7 and one end of a freewheeling inductor L1. The anode of the diode D4 is connected to the anode of the diode D5 and the anode of the diode D6, and is also connected to the anode of the flywheel diode D7 and one end of the flywheel inductor L2. The drain electrode of the switch tube Q4 is connected with the cathode of the diode D4, the drain electrode of the switch tube Q5 is connected with the cathode of the diode D5, and the drain electrode of the switch tube Q6 is connected with the cathode of the diode D6; the source electrode of the switching tube Q4 is connected with the anode of the diode D1 and the source electrode of the switching tube Q1, the drain electrode of the switching tube Q5 is connected with the anode of the diode D2 and the source electrode of the switching tube Q2, and the drain electrode of the switching tube Q6 is connected with the anode of the diode D3 and the source electrode of the switching tube Q3; the energy storage freewheel unit includes diode D7, freewheel inductance L1, L2, switch tube Q8, diode D9 and filter capacitor C1, the positive pole of diode D9 and the drain electrode of switch tube Q8 are connected to the other one end of freewheel inductance L1, the negative pole of diode D9 connects filter capacitor C1's one end (or has the positive pole of polarity electric capacity), the other one end of freewheel inductance L2 connects the source of switch tube Q8 and filter capacitor C1's other one end (or has the negative pole of polarity electric capacity), be equipped with filter capacitor C1 between the positive polarity busbar and the negative polarity busbar of rectifier switch unit promptly. Working circuit with voltage boosting and reducing combined function for realizing wide-range output voltage and power factor correction function at the same time, especially working circuit with output voltage interval of three-phase voltage V To/>When the power is multiplied, an additional converter is not needed.
The energy storage flywheel unit is connected with a flywheel diode of the output voltage bus, and can be connected in series at the positive bus end, the negative bus end or both the positive bus and the negative bus end; the follow current inductor can also be a transformer which is provided with an air gap in a magnetic loop and can store energy, and the two windings are used for equivalently replacing two separated inductors; the freewheel inductor may alternatively have only one inductor in the loop.
The switching tube can control a semiconductor device such as an MOS tube or an IGBT tube to be turned on and off by a high-frequency driving signal. The switching tube anti-parallel diode can be an integrated or parasitic diode or an external independent diode. Each phase of input switch and each phase of rectifier bridge switch are driven by the same driving signal; or each driven by an independent drive signal.
In addition, as an embodiment of the present invention, at least two of the three-phase ac/dc buck-boost conversion circuits are included, and the three-phase ac/dc buck-boost conversion circuits are connected in parallel or in staggered parallel according to 1/N cycle, where N is the number of circuits.
As shown in fig. 4, from an input three-phase ac power supply including a phase, B phase, and C phase, three-phase ac voltage signals may refer to fig. 5, which are 120 degrees out of phase with each other, and since there may be a transient in the ac voltage actually input, the voltage waveform shown in this embodiment is a standard waveform as a reference, which is convenient to be described later. The converter that this embodiment shows still includes the input filter, the input filter sets up the switch unit front end, three-phase three-wire power behind the input filter wave filtering access switch unit, play the filter effect to the input power, also can be about to the internal clutter reflection to the input filtering of end simultaneously.
As shown in fig. 4, the phase a includes switching transistors Q1 and Q4, the phase B includes switching transistors Q2 and Q5, and the phase C includes switching transistors Q3 and Q6, and the semiconductor power switch may be a MOS transistor or an IGBT transistor. A. Independent driving power supplies are used between the switching tubes of B, C phases; the two semiconductor power switches on the same phase can share a driving power supply and the same driving signal, and can be driven independently.
Example 2:
As shown in fig. 4, a load (or a circuit equivalent to a load) may be connected between the positive output terminal and the negative output terminal, and the output voltage should be lower than the input voltage according to the basic principle of circuit voltage reduction to form voltage reduction. Therefore, in the circuit, when any two of the three phases are conducted, the instantaneous lowest point of a certain interval class should be 30 °, 90 °, 150 °, 210 °, 270 °, 330 ° of the phase, or similar periodic phase difference relation point, and the lowest value at this time is 1+1/2 times the highest amplitude of the phase voltage, and the instantaneous lowest point of a certain interval class should be 0 °, 60 °, 120 °, 180 °, 240 °, 300 ° of the phase, or similar periodic phase difference relation point, and the lowest value at this time is The highest amplitude of the multiplied phase voltage; in particular, reference may be made to fig. 5, for example, where the amplitude of the output voltage on the load side is in the range of up to three-phase voltage V/>I.e. below the illustrated V1 difference, and is therefore in buck mode, e.g. the amplitude range of the output voltage at the load side is at a minimum the/>, of the three-phase voltage VI.e., higher than the illustrated V3 difference, and thus is in boost mode; the amplitude range of the output voltage at the load side is between the aforementioned V1 and V3, i.e. the V2 difference as shown, and is thus in buck-boost mode; v is the effective value of the phase voltage. The filter capacitor C1 mainly plays a role in filtering and energy storage, and can enable direct current output to be stable, so that the working performance of the electronic circuit is more stable.
As shown in fig. 5, input a represents input a Phase (Phase a), input B represents input B Phase (Phase B), and input C represents input C Phase (Phase C); for convenience of description, three-phase voltages are set to be 120 DEG different and sinusoidal, and each 360 DEG is circulated; in view of visual convenience of the expression, 30 ° to 390 ° (30 ° point of the next cycle) is one complete cycle, so as shown in fig. 5, each intersection is defined as AC (30 °), BC (90 °), BA (150 °), CA (210 °), CB (270 °), AB (330 °), AC (30 °/390 °), respectively; zero crossings are marked as "0" points. For convenience of description, we only discuss the buck-boost mode, i.e. set the output voltage as V2 amplitude, when the phase difference amplitude of this interval section reaches the vicinity of the V2 difference point from the AC point, it is lower than the V2 condition, so the working mode will be boost, and when the phase difference amplitude reaches the vicinity of the V2 difference point to the 0 point, it will be higher than V2, so the working mode will be converted into buck; around the difference equal to or slightly greater than V2, then the buck and boost hybrid mode is established. The future discussion is simple and in the following description of the operating circuit we will directly describe whether the boost Q8 is engaged in operation, and the explanation of the reasons will not be repeated in detail.
Therefore, let it be assumed that from AC point to BC point, AC-BC interval, the absolute value of the voltage amplitude of phase a and phase B is higher than that of phase C, when PWM driving on signals are applied to the switching transistors Q1 to Q6 in the three-way circuit connected to three-phase AC, Q1Q4, Q2Q5, Q3Q6 are all turned on, so D1 and D5 in the circuit of phase a and phase B are turned on by forward bias voltage, and diodes D3 and D6 in the circuit connected to phase C are turned off by reverse bias voltage of phase a and phase B, respectively, and Q8 is turned on assuming that boost mode has been determined according to the input and output voltage relationship, as shown in fig. 6, the current flows through the input switches Q1 and D1, L1, Q8, L2, D5, Q5, and Q2 to form a circuit, the inductors L1 and L2 are in energy storage state, and D9 is turned off by reverse bias; according to the control calculation, as shown in fig. 7, if Q8 is supposed to be turned off, at this time, the current cannot be immediately reversed due to the existence of the inductors L1 and L2 in the loop, the electromotive force of the inductors can be reversed and follow current, and the current forms a loop through the input switches Q1 and D1, L1, D9, L2, D5, Q5 and Q2 to supply power to C1 and the equivalent load; immediately after the driving of Q1, Q4 or Q4 is turned off (referring to the driving of Q2Q5 or Q5 in the AC-0 interval, if in the 0-BC interval); as shown in fig. 8, at this time, the current remains freewheeling due to the presence of the inductors L1 and L2 in the loop, but the induced electromotive force difference of the inductor becomes larger, that is, the gradient of the current drop becomes larger due to the lower differential pressure of the BC two phases; meanwhile, the switching tubes Q3 and Q6 of the C phase are always conducted due to the turn-on driving signals, D3 (D6 in the 0-BC interval) is conducted by the forward bias voltage, so that the C phase begins to form a follow current path with the follow current inductors L1 and L2, and the C1 and equivalent loads are supplied by the current through the input switches Q3 and D3, L1, D9, L2 and D5 and Q6. Assuming that the buck mode is determined according to the relation between the input voltage and the output voltage, the Q8 is not required to be turned on in each switching period, and only Q1-Q6 switching tubes related to the alternating current loop are required to be controlled according to the mode. Assuming that the voltage boosting and reducing compound mode is judged according to the relation between the input voltage and the output voltage, the Q1-Q6 switching tubes related to the alternating current loop are controlled to be firstly turned on in the mode, then the Q8 is turned on for a certain time according to control calculation delay to supplement the boosting energy storage, and then the switching tubes are turned off.
As can be seen from the above, the key factor of the control method for realizing high PF value and low THDI by realizing conduction current of each phase in each switching period is that two phases with higher amplitude and opposite polarity are conducted and stored in the inductance of the loop, then the path in the same direction as the lowest amplitude absolute value is closed (the switching tube in the loop is closed) to enable the follow current to pass through the phase with the lowest amplitude absolute value, so that in each switching period, the current loop of the higher phase with the same amplitude of the two phases is closed (as shown in fig. 8, the driving of the a phase is firstly closed in the interval of 30-60 ° or AC-O, as shown in fig. 8, the driving of the a phase is firstly closed in the interval of 60-90 ° or O-BC, as shown in fig. 10, the driving of the B phase is firstly closed, and the current passes through Q1 and D1, L1, D9, L2, D6, Q6 and Q3 to form the loop); the PWM drive mode that is turned off first is denoted as "short", and the PWM drive mode that is turned off later is denoted as "long". I.e. in the actual control of this embodiment, the duty cycle of each cycle normally has only two values.
When all PWM on voltages applied to the switching tube are off, all current loops input after the switching tube is turned off are cut off, and D7 is turned on by forward bias because the current of the inductor cannot be transient and must remain freewheeling. In the related state, as shown in fig. 9, the current passes through L2, D7 and L1 and D9 from the negative terminal of C1 (or the equivalent load negative terminal of the circuit output) back to the positive terminal of C1 (or the equivalent load positive terminal of the circuit output), so as to form a closed-loop current freewheel loop. At this time, the relative potential of the output terminal is not affected by the input voltage.
According to the above working principle of the embodiment, the PWM driving mode in which the driving signal of the switching tube on each phase loop connected to the three-phase ac phase is turned off first is denoted as "short", and the PWM driving mode in which the switching tube is turned off later is denoted as "long". The control method is characterized in that two phases with higher amplitude and opposite polarity are conducted in each switching period, energy is stored in the inductance of the loop, then a channel which is communicated with the phase with the lowest amplitude absolute value (a switching tube in the loop is closed) is closed, so that the follow current of the phase passes through the phase with the lowest amplitude absolute value, and therefore, in each switching period, three phases have current circulation, if the duty ratio of a PWM driving signal is modulated according to real-time control, the current waveform is consistent with the voltage waveform, and therefore, a higher PF value can be obtained, namely, the PFC correction function is realized.
In addition, if the control complexity is not considered, and only the same effect is needed, another control mode may be adopted, in which the switching tube connected with the three-phase alternating current is not applied with the driving signal, the two phases with higher amplitude and opposite polarity are firstly applied with the signal to conduct the two phases, then the path with the same direction as the lowest amplitude absolute value is closed, and the switch on the previously unopened alternating current loop is opened to enable the follow current to pass through the phase with the lowest amplitude absolute value, so that in each switching period, the current loop with the same amplitude as the two phases and the higher phase is firstly closed, the PWM driving mode firstly closed is marked as 'short 1', the PWM driving mode secondly opened is marked as 'short 2', and the PWM driving mode firstly opened and finally closed is marked as 'long'. This approach does not depart from our previous "long" and "short" control strategy and will not be described in detail later.
The circuit of the three-phase AC/DC buck-boost converter can be equivalently converted in the working modes:
When the switching tube of a certain two phases is conducted, as shown in fig. 17, according to symmetry and switching functionality, the alternating current source can be equivalent to a direct current source after being rectified by a diode under the transient condition, or the alternating current source and the diode can be regarded as a direct current source in an instantaneous circuit after being simplified as shown in fig. 18; meanwhile, the combined switch tube in the alternating current loop can be simplified and equivalent to a switch, so that the switch tube is shown in fig. 19. Simplifying the device with repeated functions is equivalent to that shown in fig. 20. After the above-mentioned equivalent, the front part is a typical voltage-reducing circuit, and the rear part is a typical voltage-increasing circuit, so the circuit can be actually regarded as a voltage-increasing circuit, and thus the circuit has a typical voltage-reducing function vo=vin×d1 or vo=vin/(1-D2) or even vo=vind 1/(1-D2). D1 is the equivalent duty ratio of each switching tube on the input alternating current loop, and D2 is the duty ratio of the eighth switching tube; therefore, the output voltage range is not limited to a single-side section like the traditional boost PFC or buck PFC, so that the output voltage is widened and can be raised and lowered relative to the input voltage.
For other interval sections, by analogy, the BC-0 interval is characterized in that the driving signals of A, B two phases are in a long PWM driving state, the driving signals of C phases are short PWM driving signals, namely, a C-phase loop is firstly turned off; in the interval 0-BA, the drive signals of C, B phases are in a long PWM drive state, and the drive signals of A phases are in a short PWM drive signal, namely the A phase loop is firstly turned off.
In the BA-CA interval, the BA-0 interval and A, C two phases of driving signals are in a long PWM driving state, and the B phase of driving signals are short PWM driving signals, namely, a B phase loop is firstly turned off; in the 0-CA interval, the drive signals of A, B two phases are in a long PWM drive state, and the drive signals of C phases are short PWM drive signals, namely, the C-phase loop is firstly turned off.
The CA-CB interval, CA-0 interval, B, C two-phase driving signals are in a long PWM driving state, A-phase driving signals are short PWM driving signals, namely, a B-phase loop is firstly turned off; in the 0-CB interval, the drive signals of A, C phases are in a long PWM drive state, and the drive signals of B phases are short PWM drive signals, namely, the B phase loop is firstly turned off.
CB-AB interval, CB-0 interval, B, A two phases of driving signals are in a long PWM driving state, C phase driving signals are short PWM driving signals, namely, a C phase loop is firstly turned off; in the 0-AB interval, the drive signals of B, C two phases are in a long PWM drive state, the drive signals of A phases are short PWM drive signals, namely, the A phase loop is firstly turned off.
The AB-AC interval is AB-0, the driving signal of C, A two phases is in a long PWM driving state, the driving signal of B phase is in a short PWM driving signal, namely, the B phase loop is firstly turned off; in the 0-AC interval, B, A two-phase driving signals are in a long PWM driving state, and C-phase driving signals are in a short PWM driving signal, namely, a C-phase loop is firstly turned off.
Since three-phase voltage is not necessarily ideal completely in reality, and there are changes in phase, amplitude and direction, the driving waveform of each section can only be judged according to actual phase locking, so that the driving waveform of each section should be judged according to the characteristics of the instantaneous waveform of each alternating voltage of each section, but not by an ideal angle, and the driving waveform of each switching tube driving signal can be divided into twelve sections according to the characteristics of the three-phase power signal, and the twelve sections can be divided into twelve sections according to the above principle, and the waveform logic tables of the driving signals of each switching tube are shown in the following table one and fig. 14; the two switching tubes on the same phase loop can apply the same signal together or apply the signals respectively, and the switching tubes have anti-parallel diodes, so that the switching driving signal is added to one switching tube, and if the switching tubes have no anti-parallel diodes, the two switching tubes must apply the switching signals simultaneously.
Meter I, switch tube driving state logic table
"A" means that the same driving signal as the other switching tube in the present loop can be applied according to the aforementioned control method, or the driving signal does not need to be applied, specifically referring to the aforementioned rule; normally, "a" or "an" can apply the same drive signal as another switching tube in the circuit.
According to the availability of each interval section of the driving waveform logic table, the following control method can be executed:
Detecting input alternating voltage, judging whether each phase index of the input voltage meets working conditions, and continuing waiting if the indexes of each phase index of the input voltage do not meet the conditions; if the condition is met, starting to work, and analyzing the phase and the section (totally divided into 12 sections) of each phase of power supply at the current moment according to the phase locking judgment of the input three-phase three-wire power supply voltage signals; analyzing the amplitude absolute value of the voltage of each phase of power supply, applying the same-size long PWM driving signal to the corresponding switching tube in the alternating current loop with the highest amplitude absolute value and the lowest amplitude absolute value, and simultaneously applying the short PWM driving signal to the corresponding switching tube in the alternating current loop with the secondary amplitude absolute value. The two phases with higher amplitude absolute values form a current loop, meanwhile, the inductance forms partial pressure energy storage, and after the short PWM driving signal is closed, the switching tube of the two phases which originally apply the long PWM driving signal can provide a follow current path for the inductance to continue to conduct. The specific size of the long and short PWM driving signals is determined by the real-time control operation result.
The method has the advantages that the continuous current of the follow current inductor is not required to be satisfied, and each phase of current can form a passage through the combination of the switches in the switching period under different load conditions. In general, the time of conducting current is in a relative relation to the amplitude of the phase voltages, i.e. the higher the amplitude absolute value, the longer the current conducting time, the current conducting time of the phase with the largest amplitude absolute value is equal to the sum of the current conducting times of the two phases with the relatively lower amplitude absolute value and is smaller than the total time of the switching period.
Through the control method, the three phases are effectively guaranteed to have current flowing in each switching period, meanwhile, the duty ratio of the PWM driving signal is modulated according to real-time control, so that the current waveform and the voltage waveform are consistent in follow-up, a higher PF value can be obtained, and the PFC correction function is realized.
As shown in fig. 4, after the control method described above is applied, the energy storage unit has symmetry, and if C1 is equivalent to a series connection of two capacitors, the equivalent circuit diagram is shown in fig. 12, and as can be seen from fig. 12, it is equivalent to that two capacitors C/2 are provided on the output side, the load is connected in parallel with the two capacitors C/2, and the midpoint of the two capacitors C/2 is defined as the equivalent midpoint. When the input side is conducted with a current loop, the equivalent midpoint is a circuit shown by a sine wave intermediate value; when the input long signal is completely closed, the rectifying unit separates the alternating current input potential from the rectifying bridge, namely the rectifying bridge forms a suspended potential, and the seventh diode D7 is used for clamping the potential in a follow current mode, and the output side still keeps symmetrical, so that the original center potential can be regarded as the potential without any change, and the possibility of being forcedly clamped to a voltage phase with an intermediate amplitude value (or a voltage phase with a1 state) does not occur. Therefore, when the equivalent midpoint of the capacitance is ground or N, the equivalent circuit diagram of the circuit output is shown in fig. 13.
In addition, as can be seen from the control method and the analysis of the working equivalent graph, when the PFC function and the output voltage are implemented, especially when the output voltage interval is V2 (3/2) to V2 (3) times the three-phase voltage V, two converters are not needed as in fig. 3, so that circuit elements can be obviously saved, the circuit is simplified, and the switching loss is saved. The performance advantage and the economic advantage are obvious, and the power density is improved.
Therefore, the invention solves the problems of the related cases, has obvious advantages in high power density occasions and can meet the requirements of high-precision products.
Example 3:
As shown in fig. 15, this embodiment proposes a modified embodiment of the three-phase ac/dc buck-boost converter circuit according to embodiment 1, which includes at least two three-phase ac/dc buck-boost converter circuits described in any one of the above, connected in parallel, and the switching tube between the three-phase ac/dc buck-boost converter circuits is driven to operate in an interleaved mode. So that the ac input current can be continuous.
Through the long and short driving signal control method, at least two (N) parallel connected three-phase alternating current-direct current buck-boost converters can be controlled respectively, and the working phases of the N parallel connected three-phase alternating current-direct current buck-boost converters are different by 1/N high-frequency periods; in addition, positive and negative side inductance current balance control is added in the control algorithm to avoid the current loop crossing in each converter caused by parallel connection.
However, when a plurality of circuits are in parallel connection, because the circuits are non-isolated circuits, after the current values of the two inductors of the L1 and the L2 are directly monitored or related information is obtained through other indirect means, whether loop crossing current (or misplacement circulation current and the like) exists between the circuits can be judged, and as shown in fig. 16, the positive side current of the first circuit is large (or L1 current is large), namely, the current corresponding to a certain phase of input of the circuit is large; the negative side current of the second circuit is large (or L2 current is large), namely the current of a certain phase is large corresponding to the input of the circuit; the sum of the total current input to each phase of the multi-circuit is balanced, so that a cross loop between the circuits is formed; at this time, the ratio of T1 to T2 can be adjusted after the calculation according to the current values, so as to realize loop impedance adjustment, thereby avoiding the current cross loops between different circuits and realizing the current consistency control of the positive and negative sides of the respective circuits.
Thus, a further control method is as follows:
After the circuit is electrified, sampling and phase locking are carried out according to the phase, amplitude and the like of input alternating current after the detection meets the working condition, driving signals are applied to switching tubes on each phase loop according to the 'long' and 'short' driving signal control method of the table I, and the working phases of N parallel-connected three-phase alternating current-direct current buck-boost converters differ by 1/N high frequency periods; meanwhile, after the current values of the two inductors of the same circuit unit are directly monitored or related information is obtained through other indirect means, whether loop crossing currents (or dislocation circulation and the like) exist between the two inductors and other circuits is judged, and the ratio of the T1 to the T2 is adjusted after the operation according to the current values of the inductors so as to realize loop impedance adjustment, thereby avoiding the current crossing loops among different circuits and realizing current consistency control of positive and negative sides of the circuits.
Those skilled in the art will recognize that numerous variations to the above description are possible, and that the examples are intended only to be illustrative of one or more particular implementations.
While there have been described and illustrated what are considered to be example embodiments of the present invention, it will be understood by those skilled in the art that various changes and substitutions can be made therein without departing from the spirit of the invention. In addition, many modifications may be made to adapt a particular situation to the teachings of the invention without departing from the central concept thereof as described herein. Therefore, it is intended that the invention not be limited to the particular embodiment disclosed, but that the invention will include all embodiments falling within the scope of the invention and equivalents thereof.
Claims (7)
1. The control method of the three-phase alternating current-direct current buck-boost conversion circuit is characterized in that the three-phase alternating current-direct current buck-boost conversion circuit comprises an input switch tube group, a rectification switch unit and an energy storage freewheeling unit, wherein the input switch tube group comprises first to third switch tubes, the rectification switch unit comprises first to sixth diodes and fourth to sixth switch tubes, and the energy storage freewheeling unit comprises a seventh diode, an eighth diode, a seventh switch tube, first to second freewheeling inductors and capacitors;
The drains of the first switching tube and the third switching tube are respectively connected with the three-phase alternating current input end, and the sources of the first switching tube and the third switching tube are respectively connected with the three input ends of the rectifying switch unit; the cathode of the first diode is connected with the cathode of the second diode and the cathode of the third diode, and is also connected with the cathode of the seventh diode and one end of the first free-wheeling inductor, the anode of the fourth diode is connected with the anode of the fifth diode and the anode of the sixth diode, and is also connected with the anode of the seventh diode and one end of the second free-wheeling inductor, the drain electrode of the fourth switch is connected with the cathode of the fourth diode, the drain electrode of the fifth switch is connected with the cathode of the fifth diode, the drain electrode of the sixth switch is connected with the cathode of the sixth diode, the source electrode of the fourth switch is connected with the anode of the first diode and the source electrode of the first switch, the drain electrode of the fifth switch is connected with the anode of the second diode and the source electrode of the second switch, and the drain electrode of the sixth switch is connected with the anode of the third diode and the source electrode of the third switch; the first to seventh switching transistors are driven by the same driving signal or are each driven by independent driving signals;
The other end of the first free-wheeling inductor is connected with the drain electrode of the seventh switching tube, the other end of the second free-wheeling inductor is connected with the source electrode of the seventh switching tube, a capacitor is connected between the positive bus end and the negative bus end, and an eighth diode is connected in series between the common end of the first free-wheeling inductor and the seventh switching tube and one end of the capacitor and/or between the common end of the second free-wheeling inductor and the seventh switching tube and the other end of the capacitor to serve as a free-wheeling diode;
The first freewheel inductor and the second freewheel inductor are two windings of the energy-storage transformer with an air gap in the magnetic loop;
The control method of the three-phase alternating current-direct current buck-boost conversion circuit comprises the following steps:
According to the phase locking judgment of the input three-phase three-wire power supply voltage signals, analyzing the phase and the interval section of each phase of power supply at the current moment;
Applying driving signals to all switching tubes on three-phase lines under the current interval section to conduct PWM driving control, so that two phases with higher absolute amplitude values between three-phase three-wire power supplies form a current conducting loop;
Judging whether to turn on a switching tube in the energy storage follow current unit according to the amplitude difference value of two phases forming the current conduction loop, if so, turning off PWM driving of a seventh switching tube after the driving time is calculated according to control and calculation to be met;
The one-phase circuit with lower amplitude absolute value in two phases forming a current conducting circuit is turned off, so that a diode on the one-phase circuit with the smallest amplitude absolute value of the voltage of the three phases is forward biased, and forms a current circuit with the phase with the highest amplitude;
and turning off driving signals of all the switching tubes, and carrying out follow current through a seventh diode, a first follow current inductor, an eighth diode and a second follow current inductor of the energy storage follow current unit.
2. The method according to claim 1, wherein the first to seventh switching transistors are semiconductor devices controlled by high-frequency driving signals to turn on and off, and each have a parallel diode, and the parallel diode is an integrated diode, a parasitic diode, or an external diode.
3. The control method of the three-phase ac/dc buck-boost conversion circuit according to claim 1, wherein: the three-phase three-wire power supply is connected to the input switch tube group after being filtered by the input filter.
4. The control method of the three-phase ac/dc buck-boost conversion circuit according to claim 1, wherein the phase and the interval section of each phase of the power supply at the current time are analyzed; the amplitude absolute value of the voltage of each phase power supply is analyzed, a 'long' PWM driving signal with the same size is applied to a corresponding switching tube in an alternating current loop with the highest amplitude absolute value and the lowest amplitude absolute value, meanwhile, a 'short' PWM driving signal is applied to a corresponding switching tube in an alternating current loop with the next amplitude absolute value, two phases with higher amplitude absolute values form a current loop, meanwhile, the inductance forms partial pressure energy storage, after the 'short' PWM driving signal is closed, the switching tubes of the two phases applying the 'long' PWM driving signal provide a follow current path for the inductance to conduct continuously, and the specific duty ratio of the 'long' PWM driving signal is determined by a real-time control operation result.
5. The control method of a three-phase ac/dc buck-boost conversion circuit according to claim 1, wherein if a maximum amplitude difference between two phases exceeds a value of an output voltage less than a threshold value or equal to zero in a certain interval, the two phases are turned on in a single period, a seventh switching tube is turned on, and PWM driving of the seventh switching tube is turned off according to a control calculation driving time delay; and switching off a communication path with a lower absolute value of amplitude values in the two conducted phases.
6. The method for controlling a three-phase ac/dc buck-boost converter according to claim 4, wherein the method comprises at least two of the three-phase ac/dc buck-boost converter circuits, wherein the three-phase ac/dc buck-boost converter circuits are connected in parallel in a staggered manner according to 1/N cycle, and N is the number of the three-phase ac/dc buck-boost converter circuits.
7. The method of claim 6, wherein whether a loop current exists between the three-phase ac/dc buck-boost conversion circuits is determined according to current values of the first and second freewheeling inductors, and the "long" PWM drive signal, the "short" PWM drive signal, or the ratio of the number of turns of the first and second freewheeling inductors is adjusted according to the current values to achieve loop impedance adjustment.
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| CN209134309U (en) * | 2018-11-06 | 2019-07-19 | 南京熊猫电子股份有限公司 | A kind of three-phase alternating current-direct current buck translation circuit |
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