CN109038725B - High-voltage charging circuit capable of controlling pulse to be adjusted in self-adaptive mode - Google Patents
High-voltage charging circuit capable of controlling pulse to be adjusted in self-adaptive mode Download PDFInfo
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- CN109038725B CN109038725B CN201810864509.9A CN201810864509A CN109038725B CN 109038725 B CN109038725 B CN 109038725B CN 201810864509 A CN201810864509 A CN 201810864509A CN 109038725 B CN109038725 B CN 109038725B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
- H02J7/007—Regulation of charging or discharging current or voltage
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
- H02J7/0029—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries with safety or protection devices or circuits
- H02J7/0036—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries with safety or protection devices or circuits using connection detecting circuits
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Abstract
A high-voltage charging circuit for controlling pulse adaptive adjustment comprises a microcontroller, a control pulse adaptive adjustment circuit, a flyback high-voltage charging circuit and an energy storage capacitor, wherein the energy storage capacitor is used for storing high-voltage energy, and the microcontroller can output a charging control signal and multiple paths of reference voltage to the control pulse adaptive adjustment circuit and detect the feedback voltage of the energy storage capacitor in real time; the control pulse self-adaptive adjusting circuit can compare the multi-channel feedback voltage of the flyback high-voltage charging circuit and the energy storage capacitor with the corresponding reference voltage output by the microcontroller, and outputs a pulse control signal after being analyzed by the logic control circuit to control the on-off of the flyback high-voltage charging circuit; the flyback high-voltage charging circuit is used for charging the energy storage capacitor. The invention can realize the high-efficiency and quick charging of the energy storage capacitor by optimizing the charging process, and is suitable for implantable defibrillators or external defibrillators and other occasions needing high-voltage charging.
Description
Technical Field
The invention belongs to the field of medical instruments, and particularly relates to a high-voltage charging circuit capable of controlling pulse self-adaptive adjustment.
Background
Sudden cardiac death seriously threatens the life safety of human beings, and has become a global public health problem due to high incidence and high death rate. Ventricular fibrillation is the leading cause of sudden cardiac death, and defibrillation by electric shock within a short time after ventricular fibrillation occurs is the only effective method for terminating ventricular fibrillation. The currently clinically developed cardiac defibrillation technologies include an implantable defibrillator and an external defibrillator, which all adopt high-voltage and high-current pulses to perform defibrillation. The high voltage charging circuit is one of the core modules of the defibrillator hardware circuit, and the module needs to raise the low voltage of the power supply battery to a high voltage and store the energy in the energy storage capacitor.
The high voltage charging circuit needs to meet the requirements of short charging time (defibrillation is performed as early as possible to improve the defibrillation success rate) and high charging efficiency (battery life is prolonged). The high-voltage charging circuit in the defibrillator is usually realized by adopting a flyback switching power supply, and the flyback switching power supply has the advantages of simple structure, small size, high efficiency and the like and has two completely different working modes: continuous mode and discontinuous mode. Theoretically, when the high-voltage charging circuit works in a critical state of two modes, the defibrillator is short in charging time and high in efficiency, and the optimal charging effect can be obtained. After the transformer and the load are determined, the working mode of the flyback switching power supply is determined by the frequency and the duty ratio of a pulse signal for controlling the on-off of a switching tube; the control pulse is usually adjusted by using a mature Pulse Width Modulation (PWM) technique or a Pulse Frequency Modulation (PFM) technique, but both techniques cannot make the flyback switching power supply always work in a critical state, so that the optimal charging effect cannot be obtained when the flyback switching power supply is applied to a defibrillator.
Disclosure of Invention
The invention aims to solve the problems in the prior art, and provides a high-voltage charging circuit capable of controlling pulse adaptive adjustment, which can optimize a charging process and realize efficient and quick charging of an energy storage capacitor.
In order to achieve the purpose, the invention adopts the technical scheme that: the device comprises a microcontroller, a control pulse self-adaptive adjusting circuit, a flyback high-voltage charging circuit and an energy storage capacitor, wherein the energy storage capacitor is used for storing high-voltage energy, and the microcontroller can output a charging control signal and a plurality of paths of reference voltages to the control pulse self-adaptive adjusting circuit and detect the feedback voltage of the energy storage capacitor in real time; the control pulse self-adaptive adjusting circuit can compare the multi-channel feedback voltage of the flyback high-voltage charging circuit and the energy storage capacitor with the corresponding reference voltage output by the microcontroller, and outputs a pulse control signal after being analyzed by the logic control circuit to control the on-off of the flyback high-voltage charging circuit; the flyback high-voltage charging circuit is used for charging the energy storage capacitor.
The microcontroller outputs a charging control signal Charge through an I/O port, outputs reference voltages Vref1-Vref4 through digital-to-analog conversion or control of a reference voltage source, and detects the feedback voltage V4 of the energy storage capacitor through analog-to-digital conversion.
The flyback high-voltage charging circuit comprises a direct-current power supply DC, a transformer T1, a switching tube Q1, a diode D1, a transformer primary current detection resistor R1, a transformer secondary current detection resistor R2, an energy storage capacitor high-end sampling resistor R3 and an energy storage capacitor low-end sampling resistor R4; the primary end of the transformer T1 is connected with the anode of a direct current power supply DC in the same name, and the other end of the primary end of the transformer T1 is connected with the drain electrode of a switching tube Q1; the same name of the secondary side of the transformer T1 is connected with one end of a secondary current detection resistor R2 of the transformer, and the other end is connected with the anode of a diode D1; the source electrode of the switching tube Q1 is connected with one end of the primary current detection resistor R1 of the transformer, and the grid electrode is connected with a pulse control signal Ctrl output by the control pulse adaptive adjusting circuit; the cathode of the diode D1 is connected with the anode of the energy storage capacitor; one end of the high-end sampling resistor R3 of the energy storage capacitor is connected with the anode of the energy storage capacitor, and the other end of the high-end sampling resistor R3 of the energy storage capacitor is connected with one end of the low-end sampling resistor R4 of the energy storage capacitor; the negative electrode of the direct current power supply DC, the negative electrode of the energy storage capacitor, the transformer primary current detection resistor R1, the transformer secondary current detection resistor R2 and the other end of the energy storage capacitor low-end sampling resistor R4 are connected together and grounded GND; the feedback voltage V1 is connected with the drain of the switch tube Q1; the feedback voltage V2 is connected with the source electrode of the switching tube Q1; the feedback voltage V3 is connected with the same-name end of the secondary side of the transformer T1; the connection end of the energy storage capacitor high-end sampling resistor R3 and the energy storage capacitor low-end sampling resistor R4 is connected with the feedback voltage V4.
The control pulse self-adaptive adjusting circuit comprises four comparators, a falling edge monostable trigger, two rising edge monostable triggers, a pulse selection circuit, an inverter, two OR gates and an RS trigger; the positive input ends of the four comparators are respectively connected with feedback voltages V1-V4, and the negative input ends of the four comparators are respectively connected with reference voltages Vref1-Vref 4; the output ends of the comparator A1 and the comparator A3 are respectively connected with the input ends of a falling edge monostable trigger M1 and a rising edge monostable trigger M2; the output ends of the falling edge monostable trigger M1 and the rising edge monostable trigger M2 are connected with the input end of the pulse selection circuit M3, the pulse selection circuit M3 switches on one of the falling edge monostable trigger M1 and the rising edge monostable trigger M2 through a switch, the selection of the path is controlled by the microcontroller, and the charging control signal Charge is simultaneously connected with the input ends of the rising edge monostable trigger M4 and the inverter M5; the output ends of the pulse selection circuit M3 and the rising edge monostable trigger M4 are connected with the input end of the OR gate M6; the output ends of the comparator A2, the comparator A4 and the inverter M5 are simultaneously connected with the input end of the OR gate M7; the output end of the OR gate M6 and the output end of the OR gate M7 are respectively connected with the S input end and the R input end of the RS trigger M8; the pulse control signal Ctrl output by the RS flip-flop M8 is used to control the on/off of the switching tube Q1 in the flyback high-voltage charging circuit.
When a pulse selection circuit M3 in the control pulse adaptive adjusting circuit switches on a falling edge monostable trigger M1, a transformer T1 in the flyback high-voltage charging circuit works in a discontinuous mode close to a critical state; when the pulse selection circuit M3 turns on the rising edge monostable flip-flop M2, the transformer T1 operates in the continuous mode, and at this time, the transformer T1 operates in different states of the continuous mode by adjusting the value of the reference voltage Vref 3; adjusting the value of the reference voltage Vref2 changes the maximum current flowing in the primary coil of the transformer T1; adjusting the value of the reference voltage Vref4 changes the target charging voltage of the energy storage capacitor.
The output voltage of the direct current power supply DC is 2.0V-15.0V.
Compared with the prior art, the invention has the following beneficial effects: aiming at the condition that the flyback high-voltage charging circuit can not obtain the optimal charging effect by the conventional pulse width modulation technology or pulse frequency modulation technology, the pulse self-adaptive control circuit is controlled to output a pulse control signal after being analyzed by the logic control circuit by comparing the multi-channel feedback voltage of the flyback high-voltage charging circuit and the energy storage capacitor with the corresponding reference voltage output by the microcontroller, and the self-adaptive control of the control pulse can enable the high-voltage charging circuit to work in an optimal mode close to a critical state.
Drawings
FIG. 1 is a block diagram of the overall architecture of the present invention;
fig. 2 is a schematic diagram of a flyback high-voltage charging circuit;
FIG. 3 is a schematic diagram of a control pulse adaptive tuning circuit;
FIG. 4 is a waveform diagram of the current in the primary and secondary windings of the transformer T1 when M1 is selected to be turned on by M3;
FIG. 5 is a waveform diagram of the current in the primary and secondary windings of the transformer T1 when M2 is selected to be turned on by M3;
FIG. 6M 3 is a waveform diagram of primary and secondary coil currents of transformer T1 when M1 and M2 are turned on sequentially.
Detailed Description
The present invention will be described in further detail with reference to the accompanying drawings.
In an embodiment, the power supply voltage Vdc is set to be 5.0V, and the target charging voltage Vc1 of the energy storage capacitor is set to be 800V.
Referring to fig. 1, the hardware circuit of the invention is composed of a microcontroller 1, a control pulse adaptive adjusting circuit 2, a flyback high-voltage charging circuit 3 and an energy storage capacitor 4. The microcontroller outputs a Charge control signal Charge, and starts/stops charging when the Charge becomes high/low. The microcontroller 1 outputs reference voltages Vref1-Vref4 through digital-to-analog conversion or control of a reference voltage source, the value of Vref1 is 5.02V between Vdc +20mV, the value of Vref2 is 100mV, the value of Vref3 is-250 mV to-10 mV, and the value of Vref4 is 2V. In addition, the microcontroller 1 monitors the feedback voltage V4 of the energy storage capacitor 4 in real time in the charging process, and when the charging voltage reaches 800V, the Charge changes to low level, so that the soft turn-off of the charging process is realized. The control pulse self-adaptive adjusting circuit compares feedback voltages V1, V2, V3 and V4 of the flyback high-voltage charging circuit and the energy storage capacitor with reference voltages Vref1, Vref2, Vref3 and Vref4 respectively, and outputs a pulse control signal Ctrl after passing through the logic control circuit to control the on-off of a switching tube in the flyback high-voltage charging circuit 3; the frequency and duty cycle of the Ctrl signal are adaptively adjusted according to the value of each feedback voltage during the charging process. The flyback high-voltage charging circuit 3 charges the energy storage capacitor to 800V quickly and efficiently by using the principle of a flyback switching power supply. The energy storage capacitor 4 is used for storing high-voltage energy, and is a capacitor C1 in fig. 2, and is required to bear high voltage and output large current pulses instantly. In this embodiment, the value is 100uF, and the maximum energy can be stored in 32J.
Referring to fig. 2, the flyback high-voltage charging circuit 3 includes a DC power supply DC, a transformer T1, a switching transistor Q1, a diode D1, a transformer primary current detection resistor R1, a transformer secondary current detection resistor R2, an energy storage capacitor high-side sampling resistor R3, and an energy storage capacitor low-side sampling resistor R4. One end (same name end) of the primary side of the transformer T1 is connected with the anode of the direct current power supply, and the other end is connected with the drain electrode of the switch tube Q1; the secondary of the transformer T1 is connected to one end of the resistor R2, and the other end is connected to the anode of the diode D1. The source of the switching tube Q1 is connected with one end of the resistor R1, and the gate is connected with the pulse control signal Ctrl output by the control pulse adaptive adjusting circuit. The cathode of the diode D1 is connected with the anode of the energy storage capacitor C1. One end of the resistor R3 is connected with the anode of the energy storage capacitor C1, and the other end is connected with one end of the resistor R4. The negative terminal of the direct current power supply DC, the negative terminal of the energy storage capacitor C1 and the other terminals of the resistors R1, R2 and R4 are connected together and grounded GND. The feedback voltage V1 is connected with the drain of the switch tube Q1; the feedback voltage V2 is connected with the source electrode of the switching tube Q1; the feedback voltage V3 is connected with the same-name end of the secondary side of the transformer T1; the feedback voltage V4 is connected with the connection ends of the resistors R3 and R4. The flyback high-voltage charging circuit 3 controls the on and off of the switching tube Q1 through Ctrl signals, and the working principle is as follows:
when the switch tube Q1 is turned on, the low-voltage DC power supply DC charges the transformer T1, the primary of the transformer T1 has current Ipri flowing through it, and the secondary has induced electromotive force, but since the diode D1 is turned off in the reverse direction, there is no current in the secondary, and energy is stored in the transformer T1; when the switching tube is turned off, the primary current of the transformer T1 is suddenly reduced to zero, but because the magnetic flux of the transformer cannot be suddenly changed, the secondary side can generate reverse electromotive force, so that the diode D1 is in forward conduction, and current Isec flows through, and the energy storage capacitor C1 is charged; the switching tube Q1 is repeatedly switched on and off to realize continuous charging, and finally the voltage on the energy storage capacitor C1 reaches the target voltage of 800V and stops charging. In the embodiment, the turns ratio of the transformer T1 is 1: N to 1:10, and the inductance of the primary coil is 5 uH; the resistance R1 takes the value of 10m omega; r2 takes the value 500m Ω; r3 takes the value of 10M omega; r4 takes the value 25.1k Ω.
Referring to fig. 3, the control pulse adaptive adjusting circuit 2 is composed of four comparators a1-a4, a falling edge monostable flip-flop M1, two rising edge monostable flip-flops M2 and M4, a pulse selection circuit M3, an inverter M5, two or gates M6 and M7, and an RS flip-flop M8. The positive input ends of the comparators A1-A4 are respectively connected with feedback voltages V1-V4, and the negative input ends are respectively connected with reference voltages Vref1-Vref 4. The output terminals of the comparators A1 and A3 are connected to the input terminals of M1 and M2, respectively. The outputs of M1 and M2 are connected with the input end of a pulse selection circuit M3, M3 switches on one of M1 and M2 through a switch, and the selection of the channel is controlled by the microcontroller 1. The Charge control signal Charge is connected to the input terminals of M4 and M5 simultaneously. The outputs of M3 and M4 are connected with the input end of an OR gate M6. The outputs of comparators A2, A4, and M5 are simultaneously connected to the input of OR gate M7. The output ends of the or gates M6 and M7 are respectively connected to the S input end and the R input end of the RS flip-flop M8. The pulse control signal Ctrl output by the RS flip-flop M8 is used to control the on/off of the switching tube Q1 in the flyback high-voltage charging circuit 3.
The working principle of the control pulse adaptive adjusting circuit 2 is as follows:
(1) at the initial charging time, the microcontroller controls the Charge to be high level, the M4 outputs a single pulse, the RS flip-flop M8 outputs high level, the switching tube Q1 is turned on, and charging is started. (2) When the switching tube Q1 is turned on, the primary current Ipri gradually increases, and when the primary coil current reaches the maximum value Ipri (max) V2/R1 is 10A, the output of the comparator a2 becomes high, the RS flip-flop M8 outputs low, and the switching tube Q1 is turned off. (3) After the switching tube Q1 is turned off, on one hand, the induced voltage Vsec of the secondary coil of the transformer T1 returns to the primary coil of T1, at this time, V1 is (Vdc + Vsec/N) > Vdc, the output of the comparator a1 becomes high level, when all secondary energy of the transformer is transferred to the energy storage capacitor C1, the value of V1 will quickly decay to Vref1 being 5.02V (this stage is called discontinuous mode detection state), the output of the comparator a1 will turn over again to low level, the falling edge monostable flip-flop M1 outputs a single pulse, if the pulse selection circuit M3 controls to send the single pulse output by M1 to the rear stage, the RS flip-flop M8 outputs high level, the switching tube Q1 is turned on again, at this time, the flyback high voltage charging circuit 3 works in a discontinuous mode close to the critical state; on the other hand, when the switching tube Q1 is turned off, the maximum secondary induction current Isec (max) ═ ipri (max)/N ═ 1A is present, at this time, V3 ═ Isec (max) × R2 ═ 500mV, the output of the comparator A3 becomes low level, the Isec gradually decreases as the secondary energy is transferred to the energy storage capacitor C1, when V3> Vref3, the output of the comparator A3 is inverted again to high level, the rising edge monostable flip-flop M2 outputs a single pulse, and when M3 controls to send the single pulse output by M2 to the subsequent stage, the RS flip-flop M8 outputs high level, the switching tube Q1 is turned on again, and at this time, the flyback high voltage charging circuit 3 operates in the continuous mode. (4) With the switching on and off of the switching tube Q1, the voltage of the energy storage capacitor C1 gradually rises; at the final charging time, the voltage of the energy storage capacitor C1 reaches 800V, V4 ═ Vc1 × R4/(R3+ R4) > Vref4, the comparator a4 outputs high level, the RS flip-flop M8 outputs low level, the switching tube Q1 is turned off, hard turn-off of the charging process is realized, and charging is finished. (5) During the charging process, the microcontroller 1 monitors the working state of each part of the circuit in real time, and the charging process can be terminated at any time by setting the Charge to be a low level.
Referring to fig. 4, when M3 selects to turn on M1, transformer T1 now operates in discontinuous mode near critical conditions. For convenience of calculation, the conduction voltage drop between the drain and the source of the switching tube Q1 and the conduction voltage drop of the diode D1 are ignored. In the Ton phase, the primary coil current Ipri rises linearly from zero to Ipri (max) 10A; in the Toff phase, the secondary coil current drops linearly from isec (max) 1A to zero; tdec is a discontinuous mode detection state time that is extremely short, negligible compared to Ton and Toff, but because of its presence, transformer T1 operates in a discontinuous mode very close to the critical state. Ton ═ ipri (max) × Lpri/Vdc ═ 10us, Toff ═ isec (max) × Lsec/Vc1 ═ 500/Vc1 (us).
During the whole charging process, the Ton phase is always 10us, and the Toff phase is inversely proportional to the voltage across the energy storage capacitor C1, so the frequency and duty ratio of the control pulse can be adaptively increased along with the increase of the charging voltage. In the initial charging period, the charge period is very long due to the small Vc1, for example, when Vc1 is 1V, Toff is 500us, so the charging process is very slow; when the charging voltage Vc1 reaches 800V, the Toff period is only 0.625us, and the charging speed is fast.
Referring to fig. 5, when M3 selects to turn on M2, taking Vref 3-10 mV, transformer T1 operates in continuous mode near critical state. In the Ton phase, the primary coil current rises linearly from ipri (min) to ipri (max) 10A; in the Toff phase, the secondary coil current drops linearly from isec (max) 1A to isec (min). When isec (min) ═ Vref3/R2 ═ 20mA, ipri (min) ═ N × isec (min) ═ 200mA, and after each cycle is completed, only 2% of energy remains in transformer T1, so the operating state of transformer T1 is very close to the critical state. Ton ═ 9.8us (ipri (max)) -ipri (min))/(Vdc/Lpri) ═ 9.8us, Toff ═ isec (max)) -isec (min))/(Vc1/500) ═ 490/Vc1 (us). Analysis shows that, similar to the charging process in fig. 4, the frequency and duty ratio of the control pulse are also adaptively increased as the charging voltage increases, and the charging process is slower at the initial moment.
Referring to fig. 6, when Vc1 is less than or equal to 50V, to shorten the early charging time, M3 selectively turns on M1, so that transformer T1 operates in a continuous mode; when Vref3 is-250 mV, isec (min) is 500mA, Ton is 5us, Toff is 250/Vc1, and 50% of energy of transformer T1 is transferred to storage capacitor C1 in each period. When Vc1 > 50V, M3 selectively turns on M2, so that transformer T1 operates in discontinuous mode, where Ton is 10us and Toff is 500/Vc 1. Compared with the operation mode that M3 is turned on by M1 or M2 alone, the hybrid charging mode in fig. 6 can effectively shorten the charging time while ensuring higher charging efficiency.
Fig. 1-3 illustrate the hardware circuit topology and basic operating principles of the present invention. Fig. 4-6 illustrate three exemplary modes of operation of the present invention, all of which enable the defibrillator to rapidly and efficiently charge the energy storage capacitor, are preferred embodiments of the present invention, but the scope of the present invention is not limited thereto, and any changes or substitutions that can be easily made by one skilled in the art within the technical scope of the present invention should be construed as being within the scope of the present invention. Therefore, the protection scope of the present invention should be subject to the protection scope defined by the claims.
Claims (4)
1. A high-voltage charging circuit with self-adaptive control pulse adjustment is characterized in that: the device comprises a microcontroller (1), a control pulse adaptive adjusting circuit (2), a flyback high-voltage charging circuit (3) and an energy storage capacitor (4), wherein the energy storage capacitor (4) is used for storing high-voltage energy, the microcontroller (1) can output a charging control signal and a plurality of paths of reference voltages to the control pulse adaptive adjusting circuit (2) and detect the feedback voltage of the energy storage capacitor (4) in real time; the control pulse self-adaptive adjusting circuit (2) can compare multi-channel feedback voltages of the flyback high-voltage charging circuit (3) and the energy storage capacitor (4) with corresponding reference voltages output by the microcontroller (1), and outputs pulse control signals after being analyzed by the logic control circuit to control the on-off of the flyback high-voltage charging circuit (3); the flyback high-voltage charging circuit (3) is used for charging the energy storage capacitor (4);
the flyback high-voltage charging circuit (3) comprises a direct-current power supply DC, a transformer T1, a switching tube Q1, a diode D1, a transformer primary current detection resistor R1, a transformer secondary current detection resistor R2, an energy storage capacitor high-end sampling resistor R3 and an energy storage capacitor low-end sampling resistor R4; the primary end of the transformer T1 is connected with the anode of a direct current power supply DC in the same name, and the other end of the primary end of the transformer T1 is connected with the drain electrode of a switching tube Q1; the same name of the secondary side of the transformer T1 is connected with one end of a secondary current detection resistor R2 of the transformer, and the other end is connected with the anode of a diode D1; the source electrode of the switching tube Q1 is connected with one end of a primary current detection resistor R1 of the transformer, and the grid electrode of the switching tube Q1 is connected with a pulse control signal Ctrl output by the control pulse adaptive adjusting circuit (2); the cathode of the diode D1 is connected with the anode of the energy storage capacitor (4); one end of the high-end sampling resistor R3 of the energy storage capacitor is connected with the anode of the energy storage capacitor (4), and the other end of the high-end sampling resistor R3 of the energy storage capacitor is connected with one end of the low-end sampling resistor R4 of the energy storage capacitor; the negative electrode of the direct current power supply DC, the negative electrode of the energy storage capacitor (4), the primary current detection resistor R1 of the transformer, the secondary current detection resistor R2 of the transformer and the other end of the low-end sampling resistor R4 of the energy storage capacitor are connected together and grounded GND; the feedback voltage V1 is connected with the drain of the switch tube Q1; the feedback voltage V2 is connected with the source electrode of the switching tube Q1; the feedback voltage V3 is connected with the same-name end of the secondary side of the transformer T1; the connection end of the energy storage capacitor high-end sampling resistor R3 and the energy storage capacitor low-end sampling resistor R4 is connected with the feedback voltage V4; the control pulse self-adaptive adjusting circuit (2) comprises four comparators, a falling edge monostable trigger, two rising edge monostable triggers, a pulse selection circuit, an inverter, two OR gates and an RS trigger; the positive input ends of the four comparators are respectively connected with feedback voltages V1-V4, and the negative input ends of the four comparators are respectively connected with reference voltages Vref1-Vref 4; the output ends of the comparator A1 and the comparator A3 are respectively connected with the input ends of a falling edge monostable trigger M1 and a rising edge monostable trigger M2; the output ends of the falling edge monostable trigger M1 and the rising edge monostable trigger M2 are connected with the input end of the pulse selection circuit M3, the pulse selection circuit M3 switches on one of the falling edge monostable trigger M1 and the rising edge monostable trigger M2 through a switch, the selection of the channel is controlled by the microcontroller (1), and the charging control signal Charge is simultaneously connected with the input ends of the rising edge monostable trigger M4 and the inverter M5; the output ends of the pulse selection circuit M3 and the rising edge monostable trigger M4 are connected with the input end of the OR gate M6; the output ends of the comparator A2, the comparator A4 and the inverter M5 are simultaneously connected with the input end of the OR gate M7; the output end of the OR gate M6 and the output end of the OR gate M7 are respectively connected with the S input end and the R input end of the RS trigger M8; the pulse control signal Ctrl output by the RS flip-flop M8 is used to control the on/off of the switching tube Q1 in the flyback high-voltage charging circuit (3).
2. The control pulse adaptive regulation high-voltage charging circuit according to claim 1, characterized in that: the microcontroller (1) outputs a charging control signal Charge through an I/O port, outputs reference voltages Vref1-Vref4 through digital-to-analog conversion or control of a reference voltage source, and detects the feedback voltage V4 of the energy storage capacitor (4) through analog-to-digital conversion.
3. The control pulse adaptive regulation high-voltage charging circuit according to claim 1, characterized in that: when a pulse selection circuit M3 in the control pulse adaptive adjusting circuit (2) is switched on a falling edge monostable trigger M1, a transformer T1 in the flyback high-voltage charging circuit (3) works in a discontinuous mode close to a critical state; when the pulse selection circuit M3 turns on the rising edge monostable flip-flop M2, the transformer T1 operates in the continuous mode, and at this time, the transformer T1 operates in different states of the continuous mode by adjusting the value of the reference voltage Vref 3; adjusting the value of the reference voltage Vref2 changes the maximum current flowing in the primary coil of the transformer T1; adjusting the value of the reference voltage Vref4 changes the target charging voltage of the energy storage capacitor (4).
4. The control pulse adaptive regulation high-voltage charging circuit according to claim 1, characterized in that: the output voltage of the direct current power supply DC is 2.0V-15.0V.
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| CN102437772A (en) * | 2012-01-06 | 2012-05-02 | 盐城工学院 | Bipolar modulation control device of high frequency pulse alternating current link inverter |
| CN102904446A (en) * | 2011-07-28 | 2013-01-30 | 电力集成公司 | Varying switching frequency and period of a power supply controller |
| CN203379486U (en) * | 2013-06-16 | 2014-01-08 | 复旦大学 | External defibrillator available for multi-shift discharge energy adjustment |
| CN103893914A (en) * | 2014-03-05 | 2014-07-02 | 复旦大学 | Program control multichannel electrophysiological stimulator |
| CN106301031A (en) * | 2015-06-23 | 2017-01-04 | 三垦电气株式会社 | Integrated circuit and switching power unit |
-
2018
- 2018-08-01 CN CN201810864509.9A patent/CN109038725B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102904446A (en) * | 2011-07-28 | 2013-01-30 | 电力集成公司 | Varying switching frequency and period of a power supply controller |
| CN102437772A (en) * | 2012-01-06 | 2012-05-02 | 盐城工学院 | Bipolar modulation control device of high frequency pulse alternating current link inverter |
| CN203379486U (en) * | 2013-06-16 | 2014-01-08 | 复旦大学 | External defibrillator available for multi-shift discharge energy adjustment |
| CN103893914A (en) * | 2014-03-05 | 2014-07-02 | 复旦大学 | Program control multichannel electrophysiological stimulator |
| CN106301031A (en) * | 2015-06-23 | 2017-01-04 | 三垦电气株式会社 | Integrated circuit and switching power unit |
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| CN109038725A (en) | 2018-12-18 |
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