CN108667337B - High-power pulse load power supply device with rapid dynamic response and control method thereof - Google Patents
High-power pulse load power supply device with rapid dynamic response and control method thereof Download PDFInfo
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- CN108667337B CN108667337B CN201810544487.8A CN201810544487A CN108667337B CN 108667337 B CN108667337 B CN 108667337B CN 201810544487 A CN201810544487 A CN 201810544487A CN 108667337 B CN108667337 B CN 108667337B
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- 239000003990 capacitor Substances 0.000 claims description 35
- 230000002457 bidirectional effect Effects 0.000 claims description 26
- 238000005070 sampling Methods 0.000 claims description 14
- 238000004146 energy storage Methods 0.000 claims description 10
- 238000007599 discharging Methods 0.000 claims description 2
- 230000001052 transient effect Effects 0.000 abstract 1
- 238000010586 diagram Methods 0.000 description 7
- 238000004088 simulation Methods 0.000 description 6
- 239000013589 supplement Substances 0.000 description 5
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K3/00—Circuits for generating electric pulses; Monostable, bistable or multistable circuits
- H03K3/01—Details
- H03K3/012—Modifications of generator to improve response time or to decrease power consumption
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
- H02J7/34—Parallel operation in networks using both storage and other dc sources, e.g. providing buffering
- H02J7/345—Parallel operation in networks using both storage and other dc sources, e.g. providing buffering using capacitors as storage or buffering devices
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Abstract
The invention discloses a high-power pulse load power supply device with quick dynamic response and a control method thereof. The invention can be used for electronic countermeasure equipment with random change of load pulse frequency and power, is suitable for any power supply system, and has the advantages that: the power supply has high utilization rate and strong adaptability; the control is simple and reliable, and the transient response speed is high.
Description
Technical Field
The invention relates to the technical field of pulse load power supplies, in particular to a high-power pulse load power supply device with a rapid dynamic response and a control method thereof.
Background
The output signal of an electronic countermeasure device generally has a wide-frequency, pulse-varying characteristic, which places higher demands on the stability of the power supply of its generator. When the duty ratio of the pulse change power capacity of the electronic countermeasure equipment to the output power capacity of the generator exceeds 40%, and the pulse change frequency is consistent with the closed-loop regulation frequency of the generator, the amplitude of the output voltage of the generator is unstable, the modulation factor exceeds the standard regulation requirement of the GJB181, and the stable and normal operation of the electronic countermeasure equipment is further affected.
In the prior art, an energy storage capacitor, a resistor, a switch and an inverter are added in a power supply system to eliminate adverse effects of a pulse load on a power supply, the energy storage capacitor is used for absorbing the pulse power change slope of electronic countermeasure equipment, and a loop formed by the resistor, the switch and the inverter is used for absorbing redundant output power.
Disclosure of Invention
In view of the above problems, the present invention aims to provide a high-power pulse load power supply with fast dynamic response and a control method thereof, which can absorb excessive power when the power supply power is greater than the pulse load power and supplement insufficient power when the power supply power is less than the pulse load power, and solve the problem of power supply adaptability of the high-power pulse load and the power supply. The technical proposal is as follows:
the high-power pulse load power supply with quick dynamic response is characterized in that alternating current of a power supply is rectified and converted into direct current through a power supply matching network and then is supplied to a pulse load, and pulse load characteristics are eliminated through an energy storage capacitor, a super capacitor, a bidirectional Buck/Boost converter and a control circuit of the bidirectional Buck/Boost converter; the energy storage capacitor is connected in parallel with the output end of the power supply matching network, and the bidirectional Buck/Boost converter comprises an inductorLSwitch tubeS 1 And a switching tubeS 2 The method comprises the steps of carrying out a first treatment on the surface of the InductanceLOne end of the switch tube is connected with the positive pole of the direct current bus, and the other end of the switch tube is connected with the switch tubeS 1 D pole of (2), switch tubeS 1 The S pole of the capacitor is connected to the negative pole of the direct current bus; switch tubeS 2 Is connected to the switch tubeS 1 D pole of (2), switch tubeS 2 Is connected to the positive plate of the super capacitor, and the negative plate of the super capacitor is connected to the switching tubeS 1 An S pole of (2); switch tubeS 1 And a switching tubeS 2 G poles of (2) are respectively connected to the control circuit.
Further, the control circuit comprises a second-order low-pass filter, a subtracter SU1, a subtracter SU2, a subtracter SU3, a PI regulator, a PWM controller, a comparator, an inverter, a multiplexer and a driving circuit;
the output current sampling end is simultaneously connected to the input end of the second-order low-pass filter and the negative input end of the subtracter SU1, the output end of the second-order low-pass filter is connected to the positive input end of the subtracter SU1, the output end of the subtracter SU1 is connected to the positive input end of the subtracter SU2, the negative input end of the subtracter SU2 is connected to the inductance current sampling end, and the output end of the subtracter SU2 is connected to the input end of the PI regulator; the output end of the PI regulator and the sawtooth wave output end are simultaneously connected to the input end of the PWM controller; one path of the output end of the PWM controller is connected to the multiplexer M1, and the other path of the output end of the PWM controller is connected to the multiplexer M2 after passing through the inverter;
the non-inverting input end of the comparator is connected to the output current sampling end, the inverting input end of the comparator is connected to the output end of the second-order low-pass filter, one path of the output end of the comparator passes through the inverter and then serves as a selection signal of the multiplexer M1, and the other path of the output signal of the comparator and the output signal of the subtracter SU3 pass through the AND gate and then serve as a selection signal of the multiplexer M2; the positive input end of the subtracter SU3 is connected with the output current sampling end, and the negative input end is connected with the output end of the second-order low-pass filter;
the output end of the multiplexer M1 is connected to the switching tube through a driving circuitS 1 The output end of the multiplexer M2 is connected to the switch tube through a driving circuitS 2 G pole of (c).
A method of controlling a high power pulsed load power supply with a fast dynamic response, comprising:
when the power supply is constant voltage output, the output current is sampled and then passes through a second-order low-pass filter to obtain the average value of the pulse load output currentI P_av Average value of output currentI P_av Subtracting the instantaneous value of the load output currenti p Obtaining a reference value of the inductance current of the bidirectional Buck/Boost converterI ref ；
In order to enable the inductor current of the bidirectional Buck/Boost converter to follow the reference value, the instantaneous value of the inductor current is sampled from the inductori L Reference value to currentI ref The subtraction is sent to a PI regulator, and the error signal after PI regulationv c Comparing the PWM driving signal with the sawtooth wave to obtain a PWM pulse driving signal;
feeding the PWM pulse driving signal into the multiplexer M1; meanwhile, the PWM pulse driving signal is inverted through an inverter and then is sent into a multiplexer M2;
the selection signal of multiplexer M1 is made up of output current transientsi p Average value with output currentI P_av The current comparison signal is obtained after passing through the comparator and then is generated after passing through the inverter;
will output the instantaneous value of currenti p Average value with output currentI P_av The current error signal is obtained after subtraction, and the current error signal and the current comparison signal are used as a selection signal of the multiplexer M2 after passing through an AND gate;
the output signals of the multiplexers M1 and M2 are respectively used as two groups of switch driving signals of the bidirectional Buck/Boost, and the charging and discharging of the super capacitor are controlled by generating the two groups of switch driving signals, so that the compensation of output power is realized.
The beneficial effects of the invention are as follows:
1) The invention combines the bidirectional Buck/Boost converter with the super capacitor, not only can absorb redundant power when the power supply power is larger than the pulse load power, but also can supplement insufficient power when the power supply power is smaller than the pulse load power, thereby solving the power adaptability problem of the high-power pulse load and the power supply;
2) When the electronic countermeasure equipment is in a standby state or a constant power state, the control loop does not output a driving signal, the super capacitor is disconnected from the bus, and at the moment, the load power represents constant power characteristics to the power supply power, and compensation power is not needed, so that the electronic countermeasure equipment is suitable for various power output modes of the electronic countermeasure equipment;
3) The redundant power supply is not consumed by other ways, but stored by the super capacitor for being used when the electronic countermeasure equipment works, so that the utilization rate of the power supply is improved, and the system efficiency is further improved;
4) When the power supply is directly connected with the pulse load after passing through the power supply matching network, the control loop can realize constant power control of the power supply only by sampling the output current and the inductance current of the bidirectional Buck/Boost converter, and the control loop is simple in design.
Drawings
Fig. 1 is a schematic diagram of a high-power pulse load power supply structure according to the present invention.
FIG. 2 is a schematic diagram of a bi-directional Buck/Boost converter and a control circuit thereof according to the present invention.
Fig. 3 is a block diagram of the operation of the high power pulse load adaptation circuit of the present invention.
Fig. 4 is a time-domain simulation waveform diagram of a switching power supply when a load is pulse power output in the first embodiment of the present invention.
Fig. 5 is a time-domain simulation waveform diagram of a switching power supply when a load is constant power output in the first embodiment of the present invention.
Detailed Description
The invention will now be described in further detail with reference to the drawings and to specific examples. Fig. 1 is a schematic block diagram of a circuit provided by the invention, alternating current of a power supply is rectified and converted into direct current through a power supply matching network to supply power to electronic countermeasure equipment, and pulse load characteristics of the electronic countermeasure equipment are eliminated through an energy storage capacitor, a super capacitor, a bidirectional Buck/Boost converter and a control circuit thereof, so that a power supply input end of the rectifying circuit presents constant power load characteristics, and the power supply adaptability problem of the electronic countermeasure equipment and the power supply is solved.
Fig. 2 is a schematic diagram of a bidirectional Buck/Boost converter and a control circuit thereof according to the present invention, wherein the energy storage capacitor is connected in parallel to an output end of the power matching network. As shown in fig. 2 (a), the bi-directional Buck/Boost converter includes an inductorLSwitch tubeS 1 And a switching tubeS 2 The method comprises the steps of carrying out a first treatment on the surface of the One end of the inductor L is connected with the positive pole of the direct current bus, and the other end is connected with the switching tubeS 1 D pole of (2), switch tubeS 1 The S pole of the capacitor is connected to the negative pole of the direct current bus; switch tubeS 2 Is connected to the switch tubeS 1 D pole of (2), switch tubeS 1 Is connected to the positive plate of the super capacitor, and the negative plate of the super capacitor is connected to the switching tubeS 1 An S pole of (2); switch tubeS 1 And a switching tubeS 2 G poles of (2) are respectively connected to the control circuit.
The bidirectional Buck/Boost converter is combined with the super capacitor, so that redundant power can be absorbed when the power supply power is larger than the pulse load power, insufficient power can be supplemented when the power supply power is smaller than the pulse load power, the dynamic response speed is improved, and meanwhile, the energy consumption of the system is reduced.
As shown in fig. 2 (b), the control circuit includes a second-order low-pass filter, a subtractor SU1, a subtractor SU2, a subtractor SU3, a PI regulator, a PWM controller, a comparator, an inverter, a multiplexer, and a drive circuit. The output current sampling end is simultaneously connected to the input end of the second-order low-pass filter and the negative input end of the subtracter SU1, the output end of the second-order low-pass filter is connected to the positive input end of the subtracter SU1, the output end of the subtracter SU1 is connected to the positive input end of the subtracter SU2, the negative input end of the subtracter SU2 is connected to the inductance current sampling end, and the output end of the subtracter SU2 is connected to the input end of the PI regulator; the output end of the PI regulator and the sawtooth wave output end are simultaneously connected to the input end of the PWM controller; one output end of the PWM controller is connected to the multiplexer M1, and the other output end of the PWM controller is connected to the multiplexer M2 after passing through the inverter. The non-inverting input end of the comparator is connected to the output current sampling end, the inverting input end of the comparator is connected to the output end of the second-order low-pass filter, one path of the output end of the comparator passes through the inverter and then is used as a selection signal of the multiplexer M1, and the other path of the output end of the comparator and the output signal of the subtracter SU3 pass through the inverter and then are used as a selection signal of the multiplexer M2; the positive input end of the subtracter SU3 is connected with the output current sampling end, and the negative input end is connected with the output end of the second-order low-pass filter; the output end of the multiplexer M1 is connected to the switching tube through a driving circuitS 1 The output end of the multiplexer M2 is connected to the switch tube through a driving circuitS 2 G pole of (c).
When the power supply is constant voltage output, the input constant power control can be realized only by controlling current, and the specific control principle is as follows: the output current is sampled and then passes through a second-order low-pass filter to obtain the average value of the pulse load output currentI P_av Average value of output currentI P_av Subtracting the instantaneous value of the load output currenti p Obtaining the reference value of the inductance current of the bidirectional Buck/Boost converterI ref . In order to enable the inductor current of the bidirectional Buck/Boost converter to follow the reference value, the instantaneous value of the inductor current is sampled from the inductori L With electric currentReference valueI ref The subtraction is sent to a PI regulator, and the error signal after PI regulationv c The PWM pulse driving signal obtained after the comparison with the sawtooth wave is sent to the multiplexer M1, the generated PWM pulse driving signal is inverted by the inverter and then sent to the multiplexer M2, and the selection signal of the M1 is sent to the instantaneous value of the output currenti p Average value with output currentI P_av The current comparison signal obtained by the comparator is generated by the inverter to output the instantaneous value of the currenti p Average value with output currentI P_av The current error signal is obtained after subtraction, the current error signal and the current comparison signal are used as selection signals of a multiplexer M2 after passing through an AND gate, output signals of the multiplexer M1 and the multiplexer M2 are respectively used as two groups of switch driving signals of a bidirectional Buck/Boost, and the charge and discharge of the super capacitor are controlled by generating the two groups of switch driving signals, so that the compensation of output power is realized.
As shown in fig. 3, when the electronic countermeasure equipment operates in a pulse load characteristic, its rated output power is periodically changed at a certain frequency and duty ratio D. When the electronic countermeasure equipment is in a light load state, the required load power is smaller than the power supply power, and the redundant power supply power delta P is at the moment 1 Charging the super capacitor; when the electronic countermeasure equipment is in a full-load state, the required power is larger than the power supply power, and the super capacitor is powered by delta P 2 The discharge supplements the power supply. The super capacitor absorbs excessive power and supplements insufficient power, the load pulse power requirement is constant power for the output end of the power supply matching network, so that the input power of the power supply is also constant, and the power adaptability problem of the high-power pulse load (electronic countermeasure equipment) and the power supply is solved. The energy storage capacitor C is used for compensating and smoothing the response time of the super capacitor compensation current and the bus voltage V change caused by the response time, so that the adaptability of the circuit is improved.
When the standby or constant power load of the electronic countermeasure equipment changes, the constant power control of the power supply can be realized without an additional control algorithm, and the electronic countermeasure equipment is suitable for various power output modes of the electronic countermeasure equipment. When the power supply is directly connected with the pulse load after passing through the power supply matching network, the control loop can realize constant power control of the power supply only by sampling the output current and the inductance current of the bidirectional Buck/Boost converter, and the control loop is simple in design.
Simulation result analysis:
FIGS. 4 and 5 are results of time domain simulations of the present invention using Psim software, with time being plotted on the horizontal axes in s for FIGS. 4 (a), (b), (c), (d) and (e); (a) The vertical axis of the voltage regulator is input current and load output current respectively, and the unit is A; the vertical axis of (b) is input current in a; the vertical axis of (c) is load output current in a; the vertical axis of (d) is inductor current, in a; (e) The vertical axis of (a) is the driving waveform of the switching tube of the bidirectional converter, and the unit is V. The horizontal axes of FIGS. 5 (a), (b), (c), (d) and (e) are all time in s; (a) The vertical axis of the voltage regulator is load output current and input current respectively, and the unit is A; the vertical axis of (b) is input current in a; the vertical axis of (c) is load output current in a; the vertical axis of (d) is inductor current, in a; (e) The vertical axis of (a) is the driving waveform of the switching tube of the bidirectional converter, and the unit is V. Simulation conditions: bus voltageV in =270V, inductanceL=400 uH, super capacitorC470uF, load frequency 200Hz, load full power 2000W, pulse power variation amplitude 10% -100%, switching frequency 100kHz.
As can be seen from fig. 4 (a), when the load pulse power jumps from 10% to 100%, the input current reaches a steady state after a dynamic response time of 0.0004s, the dynamic response speed is fast, and fig. 4 (b) and (c) are amplified waveforms of the input current and the load current, respectively. As can be seen from fig. 4 (d), when the load power is 10% of full load, the redundant power supply charges the super capacitor through the bidirectional Buck/Boost converter, and the inductor current is positive at this time, and the converter operates in Boost mode (fig. 4 (e)); when the load power is full load, the super capacitor discharges to supplement the power supply through the bidirectional Buck/Boost converter, the inductor current is negative at this time, and the converter works in the Buck mode (fig. 4 (e)). As can be seen from fig. 5 (a), when the load power jumps from the pulsating power to the constant power, the input current reaches a steady state after a dynamic response time of 0.031s, the dynamic response speed is fast, and when fig. 5 (b) and (c) are the amplified waveforms of the input current and the load current respectively, the input current is stable. As can be seen from fig. 5 (d) and (e), when the load is at a constant power, the switching tube is turned off, the inductor current is 0, and the bidirectional converter stops operating. Thus, from the simulation results, it can be seen that: the bidirectional energy storage converter can eliminate pulse load characteristics and solve the problem of power supply adaptability of electronic countermeasure equipment and a power supply. The pulse frequency and the power of the electronic countermeasure equipment can be changed at will when the electronic countermeasure equipment works, and the electronic countermeasure equipment can be suitable for any power supply system.
Claims (1)
1. A control method of a high-power pulse load power supply device with quick dynamic response is provided, wherein the alternating current of a power supply is rectified and converted into direct current through a power supply matching network and then is supplied to a pulse load, and the pulse load characteristic is eliminated through an energy storage capacitor, a super capacitor, a bidirectional Buck/Boost converter and a control circuit thereof; the energy storage capacitor is connected in parallel with the output end of the power supply matching network, and the bidirectional Buck/Boost converter comprises an inductor L and a switching tube S 1 And a switch tube S 2 The method comprises the steps of carrying out a first treatment on the surface of the One end of the inductor L is connected with the positive pole of the direct current bus, and the other end is connected with the switching tube S 1 D pole of (2), switch tube S 1 The S pole of the capacitor is connected to the negative pole of the direct current bus; switch tube S 2 Is connected to the switching tube S 1 D pole of (2), switch tube S 2 Is connected to the positive plate of the super capacitor, and the negative plate of the super capacitor is connected to the switching tube S 1 An S pole of (2); switch tube S 1 And a switch tube S 2 G poles of (2) are respectively connected to the control circuit; the control circuit comprises a second-order low-pass filter, a subtracter SU1, a subtracter SU2, a subtracter SU3, a PI regulator, a PWM controller, a comparator, an inverter, a multiplexer and a driving circuit; the output current sampling end is connected to the input end of the second-order low-pass filter and the negative input end of the subtracter SU1 at the same time, the output end of the second-order low-pass filter is connected to the positive input end of the subtracter SU1, the output end of the subtracter SU1 is connected to the positive input end of the subtracter SU2, the negative input end of the subtracter SU2 is connected to the inductance current sampling end, and the output end of the subtracter SU2 is connected toAn input of the PI regulator; the output end of the PI regulator and the sawtooth wave output end are simultaneously connected to the input end of the PWM controller; one path of the output end of the PWM controller is connected to the multiplexer M1, and the other path of the output end of the PWM controller is connected to the multiplexer M2 after passing through the inverter; the non-inverting input end of the comparator is connected to the output current sampling end, the inverting input end of the comparator is connected to the output end of the second-order low-pass filter, one path of the output end of the comparator passes through the inverter and then serves as a selection signal of the multiplexer M1, and the other path of the output signal of the comparator and the output signal of the subtracter SU3 pass through the AND gate and then serve as a selection signal of the multiplexer M2; the positive input end of the subtracter SU3 is connected with the output current sampling end, and the negative input end is connected with the output end of the second-order low-pass filter; the output end of the multiplexer M1 is connected to the switch tube S through a driving circuit 1 The output end of the multiplexer M2 is connected to the switch tube S through a driving circuit 2 G pole of (2); the method is characterized by comprising the following steps:
when the power supply is constant voltage output, the output current is sampled and then passes through a second-order low-pass filter to obtain a pulse load output current average value I P_av Average value I of output current P_av Subtracting the instantaneous value i of the load output current p Obtaining a reference value I of the inductance current of the bidirectional Buck/Boost converter ref ；
In order to enable the inductor current of the bidirectional Buck/Boost converter to follow the reference value, an instantaneous value i of the inductor current is sampled from the inductor L Reference value I of current ref The subtraction is sent to a PI regulator, and the error signal v after PI regulation c Comparing the PWM driving signal with the sawtooth wave to obtain a PWM pulse driving signal;
feeding the PWM pulse driving signal into the multiplexer M1; meanwhile, the PWM pulse driving signal is inverted through an inverter and then is sent into a multiplexer M2;
the selection signal of the multiplexer M1 is derived from the instantaneous value i of the output current p Average value I of output current P_av The current comparison signal is obtained after passing through the comparator and then is generated after passing through the inverter;
will output current instantaneous value i p Average value I of output current P_av The current error signal is obtained after subtraction, and the current error signal is compared with the currentThe comparison signal is used as a selection signal of the multiplexer M2 after passing through an AND gate;
the output signals of the multiplexers M1 and M2 are respectively used as two groups of switch driving signals of the bidirectional Buck/Boost, and the charging and discharging of the super capacitor are controlled by generating the two groups of switch driving signals, so that the compensation of output power is realized.
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