TWI460571B - Power factor control circuit and its control method - Google Patents
Power factor control circuit and its control method Download PDFInfo
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- TWI460571B TWI460571B TW100125374A TW100125374A TWI460571B TW I460571 B TWI460571 B TW I460571B TW 100125374 A TW100125374 A TW 100125374A TW 100125374 A TW100125374 A TW 100125374A TW I460571 B TWI460571 B TW I460571B
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02P—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
- Y02P80/00—Climate change mitigation technologies for sector-wide applications
- Y02P80/10—Efficient use of energy, e.g. using compressed air or pressurized fluid as energy carrier
Description
本發明是一種功率因數控制電路及其控制方法,特別是指依交換式電源電路目前電流模式而輸出對應脈寬調變訊號的控制電路與控制方法。The invention relates to a power factor control circuit and a control method thereof, in particular to a control circuit and a control method for outputting a corresponding pulse width modulation signal according to the current current mode of the switching power supply circuit.
請參考圖5所示,欲將市電的交流電源(Vac)轉換為直流電源以供負載60使用,係在交流電源(Vac)與負載60之間連接一整流器50與一交換式電源電路70。該整流器50將交流電源轉換為直流弦波電壓;該交換式電源電路70的輸入端連接該整流器50的輸出端,以將直流弦波電壓轉換為一穩定的直流電源並由其輸出端輸出至負載60,其中該交換式電源電路70包含有一功率因數校正電路71及一直流/直流轉換器72,由該直流/直流轉換器72將該功率因數校正電路71輸出的電壓(如380V)轉換為不同準位的直流電壓(如28V、12V)後再輸出給負載60。Referring to FIG. 5, in order to convert the commercial AC power supply (Vac) into a DC power supply for use by the load 60, a rectifier 50 and a switching power supply circuit 70 are connected between the AC power supply (Vac) and the load 60. The rectifier 50 converts the AC power to a DC sine wave voltage; the input of the switching power supply circuit 70 is connected to the output of the rectifier 50 to convert the DC sine wave voltage into a stable DC power source and outputted to the output terminal thereof. The load 60, wherein the switched power supply circuit 70 includes a power factor correction circuit 71 and a DC/DC converter 72. The DC/DC converter 72 converts the voltage (eg, 380V) output by the power factor correction circuit 71 into The DC voltages of different levels (such as 28V, 12V) are output to the load 60.
該功率因數校正電路71主要包含有一電感L、一輸出電容c及一主動開關711、一第一比例積分放大器81、一第二比例積分放大器82、一多工器83與一驅動器84;其中,該電感L與輸出電容C之間連接有該主動開關711,其中該主動開關711具有一控制端。The power factor correction circuit 71 mainly includes an inductor L, an output capacitor c and an active switch 711, a first proportional integral amplifier 81, a second proportional integral amplifier 82, a multiplexer 83 and a driver 84; The active switch 711 is connected between the inductor L and the output capacitor C. The active switch 711 has a control terminal.
上述第一比例積分放大器81具有兩輸入端且分別連接該功率因數校正電路71的輸出端以及一參考電壓Vref1 ,且具有一輸出端連接該多工器83,該多工器83連接該整流器50的輸出端。The first proportional integral amplifier 81 has two input terminals and is respectively connected to the output end of the power factor correction circuit 71 and a reference voltage V ref1 , and has an output terminal connected to the multiplexer 83, and the multiplexer 83 is connected to the rectifier 50 output.
上述第二比例積分放大器82具有兩輸入端且分別連接該整流器50輸出端以及該多工器83的輸出端。The second proportional integrating amplifier 82 has two input ends and is respectively connected to the output of the rectifier 50 and the output of the multiplexer 83.
該驅動器84具有兩輸入端且分別電連接該第二比例積分放大器82的輸出端與一參考電壓訊號Vref2 ,且驅動器84的輸出端連接該主動開關711的控制端。The driver 84 has two input terminals and is electrically connected to the output end of the second proportional integrating amplifier 82 and a reference voltage signal V ref2 , and the output end of the driver 84 is connected to the control end of the active switch 711 .
已知功率因數的控制方法配合上述電路結構加以說明如后。該第一比例積分放大器81依據該功率因數校正電路71實際輸出電壓與該參考電壓Vref1 的差異而輸出一電壓誤差信號Verror ;該第二比例積分放大器82依據電感電流IL 與電壓誤差信號Verror 輸出一代表電流誤差的電壓信號Ierror 至該驅動器84,又該驅動器84依據該電壓信號Ierror 與參考電壓訊號Vref2 輸出一脈寬調變訊號至主動開關711的控制端,以控制該主動開關711導通的責任週期(Duty cycle,D)。The control method of the known power factor is described in conjunction with the above circuit structure. The first proportional integral amplifier 81 outputs a voltage error signal V error according to the difference between the actual output voltage of the power factor correction circuit 71 and the reference voltage V ref1 ; the second proportional integral amplifier 82 is based on the inductor current I L and the voltage error signal V error outputs a voltage signal I error representing a current error to the driver 84, and the driver 84 outputs a pulse width modulation signal to the control terminal of the active switch 711 according to the voltage signal I error and the reference voltage signal V ref2 to control The duty cycle of the active switch 711 is turned on (Duty cycle, D).
承上述,欲使該功率因數校正電路71輸出一穩定的電壓Vout ,則責任週期、實際輸入電壓Vin,sense 與預設的輸出電壓Vout 存在一關係式:。因脈寬調變訊號的責任週期係依據電壓信號Ierror 而得,又電壓信號Ierror 包含有該功率因數校正電路71之實際輸入電壓、電感電流IL 與實際輸出電壓的成份,因此透過功率因數校正電路適當的配置,即可使功率因數獲得改善。In the above, if the power factor correction circuit 71 outputs a stable voltage V out , the duty cycle, the actual input voltage V in, sense and the preset output voltage V out have a relationship: . The duty cycle of the pulse width modulation signal is based on the voltage signal I error , and the voltage signal I error includes the actual input voltage of the power factor correction circuit 71, the component of the inductor current I L and the actual output voltage, and thus the transmission power. The proper configuration of the factor correction circuit results in an improved power factor.
綜合以上所述,只要該功率因數校正電路71實際輸出電壓與該參考電壓Vref1 之間有差異,以及該功率因數校正電路71的電感電流IL 電流與電壓誤差信號Verror 之間有差異時,該驅動器84即可對應輸出脈寬調變訊號。In summary, as long as there is a difference between the actual output voltage of the power factor correction circuit 71 and the reference voltage V ref1 , and the difference between the inductor current I L current of the power factor correction circuit 71 and the voltage error signal V error The driver 84 can correspond to the output pulse width modulation signal.
交換式電源電路會因負載狀態改變而操作在不同的電流模式,包含有連續電流模式(Continuous Current Mode,CCM)與不連續電流模式(Discrete Current Mode,DCM)。Switched power circuits operate in different current modes due to load state changes, including Continuous Current Mode (CCM) and Discrete Current Mode (DCM).
當交換式電源電路操作在連續電流模式時,於脈寬調變訊號的責任週期(Duty cycle)期間,該主動開關711被導通,使該電感L充電,且提升通過電感L的電流;於非脈寬調變訊號的責任週期期間,主動開關711截止,使該電感L放電,而在該電感L放電至零之前,該脈寬調變訊號即令主動開關711再度被導通,使電感L再充電至更高的電流準位,於電感L反覆充、放電的過程中,電感L的平均電流波形將追隨輸入的電壓波形。When the switching power supply circuit operates in the continuous current mode, during the duty cycle of the pulse width modulation signal, the active switch 711 is turned on, charging the inductor L, and boosting the current through the inductor L; During the duty cycle of the pulse width modulation signal, the active switch 711 is turned off to discharge the inductor L, and before the inductor L is discharged to zero, the pulse width modulation signal causes the active switch 711 to be turned on again to recharge the inductor L. To a higher current level, during the process of charging and discharging the inductor L, the average current waveform of the inductor L will follow the input voltage waveform.
當該功率因數校正電路71操作在不連續電流模式時,電流相對連續電流模式為低;於脈寬調變訊號的責任週期期間,該主動開關711被導通,使該電感L充電以提升通過電感L的電流;於非脈寬調變訊號的責任週期期間,電感L將放電到零,並於下一次責任週期期間被充電;因此通過電感L的平均電流相對連續電流模式低。When the power factor correction circuit 71 operates in the discontinuous current mode, the current is low relative to the continuous current mode; during the duty cycle of the pulse width modulation signal, the active switch 711 is turned on, so that the inductor L is charged to boost the through inductor The current of L; during the duty cycle of the non-pulse width modulated signal, the inductor L will discharge to zero and be charged during the next duty cycle; therefore the average current through inductor L is lower than the continuous current mode.
如圖5揭示改善功率因數的電路結構中,假使脈寬調變訊號的責任週期已經設計為符合連續電流模式,雖然確實可以改善操作在連續電流模式時的功率因數,但卻也使得當該功率因數校正電路71操作在不連續電流模式時,脈寬調變訊號仍沿用連續電流模式時的責任週期;脈寬調變訊號在非責任週期的期間,且當電感L放電到零時,該功率因數校正電路71上的儲能元件(如二極體、升壓電容C等)所儲存的電容能量將反饋到該功率因數校正電路71的輸入端,導致輸入端嚴重的諧波失真。As shown in FIG. 5, in the circuit structure for improving the power factor, if the duty cycle of the pulse width modulation signal has been designed to conform to the continuous current mode, although it is indeed possible to improve the power factor when operating in the continuous current mode, it also makes the power When the factor correction circuit 71 operates in the discontinuous current mode, the pulse width modulation signal still follows the duty cycle when the continuous current mode is used; the pulse width modulation signal is during the non-responsibility period, and when the inductance L is discharged to zero, the power The capacitive energy stored by the energy storage elements (e.g., diode, boost capacitor C, etc.) on the factor correction circuit 71 is fed back to the input of the power factor correction circuit 71, causing severe harmonic distortion at the input.
為了改善上述缺點,請參考圖6所示,係一功率因數校正電路71’之改良,其特徵在於,該功率因數校正電路71’中的主動開關711’並聯一緩振單元73,該緩振單元73包含有一二極體730、一電阻731與一電容732,該二極體730與電阻731並聯後再共同串接至該電容732,其中該二極體730的陽極端連接電感L,其陰極端連接電容732。藉此,若該功率因數校正電路71’操作在不連續電流模式時,於脈寬調變訊號在非責任週期的期間,升壓式電源電路上儲能元件(如電感L、二極體D、升壓電容C)所儲存的部分能量將由緩振單元73吸收,係有效降低升壓式電源電路在其輸入端諧波失真的情況。In order to improve the above disadvantages, please refer to FIG. 6, which is a modification of the power factor correction circuit 71'. The active switch 711' in the power factor correction circuit 71' is connected in parallel with a vibration relief unit 73. The unit 73 includes a diode 730, a resistor 731 and a capacitor 732. The diode 730 is connected in parallel with the resistor 731 and then connected in series to the capacitor 732. The anode end of the diode 730 is connected to the inductor L. The cathode end is connected to a capacitor 732. Thereby, if the power factor correction circuit 71' operates in the discontinuous current mode, during the non-responsibility period of the pulse width modulation signal, the energy storage component (such as the inductor L and the diode D) on the boosting power supply circuit The part of the stored energy of the boosting capacitor C) will be absorbed by the vibration absorbing unit 73, which effectively reduces the harmonic distortion of the boosting power supply circuit at its input end.
惟,該緩振單元73中的二極體730、電阻731與電容732係屬被動元件,將在該功率因數校正電路71轉換的過程中耗損能量,導致降低升壓式電源電路的轉換效率,並會使輸入電流產生低頻振盪。However, the diode 730, the resistor 731 and the capacitor 732 in the buffer unit 73 are passive components, which will consume energy during the conversion of the power factor correction circuit 71, thereby reducing the conversion efficiency of the boost power supply circuit. It will cause low frequency oscillations in the input current.
請參考圖7所示,現有研究人員提出一控制電路,主要先判斷交換式電源電路目前所操作的電流模式,再根據目前電流模式對應改變脈寬調變訊號的責任週期。Please refer to FIG. 7 , the existing researcher proposes a control circuit, which firstly determines the current mode of the current operation of the switching power supply circuit, and then changes the duty cycle of the pulse width modulation signal according to the current current mode.
此一控制電路同樣包含有一整流器90及一功率因數校正電路91;其中該整流器90的輸入端連接交流市電(Vac),該功率因數校正電路91的輸入端電連接該整流器90的輸出端,且該功率因數校正電路91包含有一電感L、一電容C、一主動開關910及一功率因數控制器92。The control circuit also includes a rectifier 90 and a power factor correction circuit 91; wherein the input of the rectifier 90 is connected to an AC mains (Vac), the input of the power factor correction circuit 91 is electrically connected to the output of the rectifier 90, and The power factor correction circuit 91 includes an inductor L, a capacitor C, an active switch 910, and a power factor controller 92.
上述整流器90係接收交流市電(Vac),並將該交流市電轉換為一直流弦波電源後並輸出。The rectifier 90 receives AC mains (Vac), converts the AC mains into a continuous stream power supply, and outputs it.
上述功率因數校正電路91的輸入端Vin 電連接該整流器90的輸出端,其可操作在連續電流模式或不連續電流模式;該功率因數校正電路91以升壓式電路舉例說明之。The input terminal V in of the power factor correction circuit 91 is electrically coupled to the output of the rectifier 90, which is operable in a continuous current mode or a discontinuous current mode; the power factor correction circuit 91 is illustrated by a boost circuit.
該功率因數控制器92的輸入端電連接該功率因數校正電路91的輸入端與輸出端,以擷取該功率因數校正電路91的輸入電壓Vin,sense 、輸出電壓Vout,sense 與該電感電流IL,sense ,且該功率因數控制器92具有一輸出控制端電連接該主動開關910。The input end of the power factor controller 92 is electrically connected to the input end and the output end of the power factor correction circuit 91 to extract the input voltage V in, sense , the output voltage V out, sense and the inductance of the power factor correction circuit 91 The current I L, sense , and the power factor controller 92 has an output control terminal electrically connected to the active switch 910.
請參考圖8所示,該功率因數控制器92內建有一運算單元923,且功率因數控制器92包含有一連續電流模式921與一不連續電流模式922。Referring to FIG. 8 , the power factor controller 92 has an operation unit 923 built therein, and the power factor controller 92 includes a continuous current mode 921 and a discontinuous current mode 922 .
根據功率因數校正的特性關係式,該運運算單元923係依據兩運算式以及之間的大小,若D2<D1,則判斷為連續電流模式,該功率因數控制器92則切換到連續電流模式921,而可自其輸出控制端輸出一責任週期為的脈寬調變信號,其中係一理論值,係一補償參數;若D1<D2,則判斷為不連續電流模式,該功率因數控制器92則切換到不連續電流模式921,而可自其輸出控制端輸出一責任週期為的脈寬調變信號,而係一理論值:According to the characteristic relationship of the power factor correction, the operation unit 923 is based on two arithmetic expressions. as well as The size between the two, if D2 < D1, it is judged as continuous current mode, the power factor controller 92 is switched to the continuous current mode 921, and a duty cycle can be output from the output control terminal thereof. Pulse width modulation signal, wherein a theoretical value, A compensation parameter is determined; if D1 < D2, it is determined to be a discontinuous current mode, and the power factor controller 92 is switched to the discontinuous current mode 921, and a duty cycle can be output from the output control terminal thereof. Pulse width modulation signal, and A theoretical value:
L:電感值;L: inductance value;
Vin,sense :輸入電壓;V in,sense : input voltage;
Vout,sense :輸出電壓;V out, sense : output voltage;
Vout :額定輸出電壓;V out : rated output voltage;
Ts :脈寬調變訊號的週期。T s : the period of the pulse width modulation signal.
iREF :輸出電壓Vout,sense 與一參考電壓之間的誤差值經比例積分放大後的參數。i REF : The parameter obtained by proportionally integrating the error value between the output voltage V out, sense and a reference voltage.
是以,該功率因數控制器92即可根據目前功率因數校正電路91的操作模式,主動改變輸出的脈寬調變信號,藉此改善脈寬調變信號與功率因數校正電路91無法對應而導致諧波的狀況。Therefore, the power factor controller 92 can actively change the output pulse width modulation signal according to the operation mode of the current power factor correction circuit 91, thereby improving the inability of the pulse width modulation signal to correspond to the power factor correction circuit 91. The state of the harmonics.
當功率因數校正電路91操作在連續電流模式時,責任週期係包含有一理論值與一補償參數,由補償參數補足理論值的不足;雖然如此,當功率因數校正電路91操作在不連續電流模式時,功率因數控制器92輸出的責任週期僅是一理論值,想當然爾,當功率因數控制器92切換到不連續電流模式922時,僅將理論值直接套用在實際的電路,故改善諧波失真的效果有限(如圖9所示的輸入電壓、電流波形圖),尚有改良的空間。When the power factor correction circuit 91 operates in the continuous current mode, the duty cycle includes a theoretical value and a compensation parameter, and the compensation parameter complements the theoretical value; however, when the power factor correction circuit 91 operates in the discontinuous current mode , the duty cycle of the output of the power factor controller 92 It is only a theoretical value. Of course, when the power factor controller 92 switches to the discontinuous current mode 922, only the theoretical value is directly applied to the actual circuit, so the effect of improving the harmonic distortion is limited (as shown in FIG. 9). Input voltage, current waveform diagram), there is room for improvement.
因此本發明的主要目的是提供一種功率因數控制電路,以改善已知控制電路的諧波失真缺陷。It is therefore a primary object of the present invention to provide a power factor control circuit to improve harmonic distortion defects of known control circuits.
為達前揭目的,本發明採用的技術手段係令該功率因數控制電路包含一電感、一輸出電容、一二極體、一主動開關及一功率因數控制器;其中,該功率因數控制器電連接該功率因數控制電路的輸入端與輸出端,且具有一輸出控制端電連接該主動開關;該功率因數控制器根據該功率因數控制電路操作在連續電流模式或不連續電流模式而對應輸出不同脈寬調變信號;其中:對應連續電流模式輸出的脈寬調變信號之責任週期係為一前饋控制參數與一電流補償參數的總合;對應不連續電流模式輸出的脈寬調變信號之責任週期係為一前饋控制參數與一電流補償參數的總合;其中該電流補償參數係包含有一參考電流與該電感電流之誤差值。In order to achieve the above, the technical means adopted by the present invention is that the power factor control circuit comprises an inductor, an output capacitor, a diode, an active switch and a power factor controller; wherein the power factor controller is electrically Connecting the input end and the output end of the power factor control circuit, and having an output control end electrically connected to the active switch; the power factor controller operates according to the power factor control circuit in a continuous current mode or a discontinuous current mode, and the corresponding output is different a pulse width modulation signal; wherein: the duty cycle of the pulse width modulation signal corresponding to the continuous current mode output is a sum of a feedforward control parameter and a current compensation parameter; and a pulse width modulation signal corresponding to the discontinuous current mode output The duty cycle is a sum of a feedforward control parameter and a current compensation parameter; wherein the current compensation parameter includes an error value between the reference current and the inductor current.
本發明尚提供一種功率因數控制方法,其步驟包含:判斷目前電流操作模式為連續電流模式或不連續電流模式;若判斷為連續電流模式,則對應連續電流模式輸出一脈寬調變信號,其責任週期係為一前饋控制參數與一電流補償參數的總合,其中該電流補償參數係包含有一參考電流與該電感電流之誤差值;若判斷為不連續電流模式,則對應不連續電流模式輸一脈寬調變信號,其責任週期係為一前饋控制參數與一電流補償參數的總合,其中該電流補償參數係包含有一參考電流與該電感電流之誤差值。The present invention further provides a power factor control method, the method comprising: determining that the current current operation mode is a continuous current mode or a discontinuous current mode; if the continuous current mode is determined, outputting a pulse width modulation signal corresponding to the continuous current mode, The duty cycle is a sum of a feedforward control parameter and a current compensation parameter, wherein the current compensation parameter includes an error value of the reference current and the inductor current; if the discontinuous current mode is determined, the corresponding discontinuous current mode The duty cycle is a sum of a feedforward control parameter and a current compensation parameter, wherein the current compensation parameter includes an error value between the reference current and the inductor current.
本發明之控制方法會隨著交換式電源電路所操作不同電流模式,輸出對應的脈寬調變訊號至交換式電源電路,以同時滿足當交換式電源電路所連接的負載為重載或輕載的需求,因此有效改善諧波。The control method of the present invention outputs a corresponding pulse width modulation signal to the switching power supply circuit according to different current modes operated by the switching power supply circuit, so as to simultaneously satisfy the load connected to the switching power supply circuit as a heavy load or a light load. The demand is therefore effective in improving harmonics.
圖1係為本發明功率因數控制電路之電路圖,其中該功率因數控制電路20係透過一整流器10連接一交流電源(Vac),藉由該整流器10將該交流電源轉換為一直流弦波電源,於輸入端取得直流弦波電源。該功率因數控制電路20可為一升壓式電源架構(Boost converter)或降壓式電源架構(Buck converter),均可操作在連續電流模式或不連續電流模式;本實施例係以升壓式電源架構舉例說明,該功率因數控制電路20係包含有一電感L、一二極體D、一輸出電容C、一電阻R、一主動開關21與一功率因數控制器30。1 is a circuit diagram of a power factor control circuit of the present invention, wherein the power factor control circuit 20 is connected to an alternating current power supply (Vac) through a rectifier 10, and the alternating current power is converted into a constant stream power supply by the rectifier 10. Get the DC sine wave power supply at the input. The power factor control circuit 20 can be a boost converter or a buck converter, and can operate in a continuous current mode or a discontinuous current mode. This embodiment is a boost type. For example, the power factor control circuit 20 includes an inductor L, a diode D, an output capacitor C, a resistor R, an active switch 21, and a power factor controller 30.
該電感L、二極體D、輸出電容C與電阻R串接並與該整流器10構成一迴路;該主動開關21電連接於該二極體D的陽極端與該電阻R之間,且該主動開關21具有一控制端;該輸出電容C的兩端作為電壓的輸出端Vout ;功率因數控制器30連接該功率因數控制電路20的輸入端與輸出端之間,且具有一輸出控制端連接主動開關21的控制端。The inductor L, the diode D, and the output capacitor C are connected in series with the resistor R and form a loop with the rectifier 10; the active switch 21 is electrically connected between the anode end of the diode D and the resistor R, and the active switch 21 having a control terminal; ends of the capacitor C is output as a voltage output terminal V out; the power factor controller 30 is connected between the input power factor control circuit 20 and the output terminal, and having an output control terminal The control terminal of the active switch 21 is connected.
請參考圖2所示,該功率因數控制器30包含有一電壓迴路控制模組31、一電流迴路控制模組32與一前饋控制模組33。Referring to FIG. 2 , the power factor controller 30 includes a voltage loop control module 31 , a current loop control module 32 , and a feedforward control module 33 .
該電壓迴路控制模組31包含一CCM比例積分放大單元310與一DCM比例積分放大單元311;該CCM比例積分放大單元310具有在連續電流模式下的比例參數KP,CCM 、積分參數KI,CCM ,該DCM比例積分放大單元311具有在不連續電流模式下的比例參數KP,DCM 、積分參數KI,DCM ;該電壓迴路控制模組31輸入端電連接一參考電壓Vref 以及該功率因數控制電路20的輸入端與輸出端,用以取得參考電壓Vref 與功率因數控制電路20輸出電壓Vout,sense 的差值,並將差值透過CCM比例積分放大單元310或DCM比例積分放大單元311進行比例積分放大後,與功率因數控制電路20實際的輸入電壓Vin,sense 相乘,以形成一代表參考電流iREF 的信號輸出。The voltage loop control module 31 includes a CCM proportional integral amplification unit 310 and a DCM proportional integral amplification unit 311; the CCM proportional integral amplification unit 310 has a proportional parameter K P, CCM and an integral parameter K I in the continuous current mode . CCM , the DCM proportional integral amplification unit 311 has a proportional parameter K P, DCM , integral parameter K I, DCM in the discontinuous current mode; the input end of the voltage loop control module 31 is electrically connected to a reference voltage V ref and the power The input end and the output end of the factor control circuit 20 are used to obtain the difference between the reference voltage V ref and the output voltage V out, sense of the power factor control circuit 20, and the difference is transmitted through the CCM proportional integral amplification unit 310 or the DCM proportional integral. After the unit 311 performs proportional integral amplification, it is multiplied by the actual input voltage V in, sense of the power factor control circuit 20 to form a signal output representative of the reference current i REF .
該電流迴路控制模組32電連接該電壓迴路控制模組31的輸出端以及該功率因數控制電路20的電阻R,且具有所述的輸出控制端,由電阻R反應功率因數控制電路20的電感電流IL,sense ,該電流迴路控制模組32接收參考電流iREF 與電感電流IL,sense 並進行相減,以取得其差值iREF -IL,sense ;該電流迴路控制模組32包含一連續電流補償單元321與一不連續電流補償單元322,各個補償單元321、322根據前述差值而分別產生一電流補償參數;根據功率因數校正的特性關係式,以升壓式電源電路而言,連續電流補償單元321產生的電流補償參數為,該不連續電流補償單元322產生的電流補償參數為F m (i REF -I L , sense ),其中:The current loop control module 32 is electrically connected to the output end of the voltage loop control module 31 and the resistor R of the power factor control circuit 20, and has the output control terminal, and the resistance of the power factor control circuit 20 is reflected by the resistor R. Current I L, sense , the current loop control module 32 receives the reference current i REF and the inductor current I L, sense and subtracts to obtain the difference i REF -I L, sense ; the current loop control module 32 A continuous current compensation unit 321 and a discontinuous current compensation unit 322 are included, and each of the compensation units 321, 322 respectively generates a current compensation parameter according to the difference; according to the characteristic relationship of the power factor correction, the boost power supply circuit The current compensation parameter generated by the continuous current compensation unit 321 is The current compensation parameter generated by the discontinuous current compensation unit 322 is F m ( i REF - I L , sense ), where:
L:電感值;L: inductance value;
Vout :額定輸出電壓;V out : rated output voltage;
IL,sense :電感電流;I L, sense : inductor current;
Fm :補償常數;F m : compensation constant;
iREF :包含輸出電壓Vout,sense 成份的參考電流。i REF : Contains the reference current of the output voltage V out, sense component.
該前饋控制模組33的輸入端電連接該電壓迴路控制模組31的輸出端以及該功率因數控制電路20的輸出端與輸入端,該前饋控制模組33的一輸出控制端電連接該電流迴路控制模組32,另一輸出控制端則連接該電壓迴路控制模組33;該前饋控制模組33係根據功率因數控制電路20的輸入電壓Vin,sense 、輸出電壓Vout,sense 與該電壓迴路控制模組31輸出的參考電流iREF 判斷該功率因數控制電路20操作於連續電流模式或不連續電流模式,並依各電流模式對應切換該電壓迴路控制模組31中的CCM比例積分放大電路310與DCM比例積分放大電路,以及對應切換電流迴路控制模組32中的連續電流補償單元321與不連續電流補償單元322;該前饋控制模組33並產生一對應電流模式的前饋控制參數至該電流迴路控制模組32;該電流迴路控制模組32輸出一脈寬調變訊號至主動開端21,其中該脈寬調變訊號的責任週期即為該前饋控制參數與該電流迴路控制模組31所產生的電流補償參數之總和。The input end of the feedforward control module 33 is electrically connected to the output end of the voltage loop control module 31 and the output end of the power factor control circuit 20 and the input end. The output control end of the feedforward control module 33 is electrically connected. The current loop control module 32 is connected to the voltage loop control module 33. The feedforward control module 33 is based on the input voltage Vin , sense and the output voltage Vout of the power factor control circuit 20 . Sense and the reference current i REF output by the voltage loop control module 31 determine that the power factor control circuit 20 operates in a continuous current mode or a discontinuous current mode, and correspondingly switch the CCM in the voltage loop control module 31 according to each current mode. The proportional integral amplification circuit 310 and the DCM proportional integral amplification circuit, and the continuous current compensation unit 321 and the discontinuous current compensation unit 322 in the corresponding switching current loop control module 32; the feedforward control module 33 generates a corresponding current mode Feeding control parameters to the current loop control module 32; the current loop control module 32 outputs a pulse width modulation signal to the active start end 21, wherein the pulse width adjustment Duty cycle signals that is the sum of the feedforward control and the current parameters of the current loop compensation parameter control module 31 generating the front.
如先前技術所述,一般的判斷方式,該前饋控制模組33係依據兩運算式以及之間的大小,若D1<D2,則判斷該升壓式電源電路操作於不連續電流模式,根據功率因數校正的特性關係式,所產生的前饋控制參數為;若D2<D1 ,則判斷為連續電流模式,且產生的前饋控制參數為。其中:As described in the prior art, in the general judgment mode, the feedforward control module 33 is based on two arithmetic expressions. as well as The size between the two, if D1 < D2, it is judged that the boost power supply circuit operates in the discontinuous current mode, and according to the characteristic relationship of the power factor correction, the generated feedforward control parameter is If D2<D 1 , it is judged as continuous current mode, and the generated feedforward control parameter is . among them:
L:電感值;L: inductance value;
Vin,sense :輸入電壓;V in,sense : input voltage;
Vout,sense :輸出電壓;V out, sense : output voltage;
Vout :額定輸出電壓;V out : rated output voltage;
Ts :脈寬調變訊號的週期。T s : the period of the pulse width modulation signal.
舉例而言,當該前饋控制模組33判斷功率因數控制電路20操作在連續電流模式時,係將電壓迴路控制模組31切換至CCM比例積分放大單元310,使電壓迴路控制模組31輸出比例參數KP,CCM 與積分參數KI,CCM ,及將該電流迴路控制模組32切換至連續電流補償單元321,令連續電流補償單元321產生電流補償參數為,該前饋控制模組33並產生前饋控制參數,且將前饋控制參數輸出到該電流迴路控制模組32,該電流迴路控制模組32將前饋控制參數與電流補償參數相加後,輸出一責任週期為的脈寬調變訊號至該主動開關21的控制端,責任週期即前饋控制參數與電流補償參數的總和。For example, when the feedforward control module 33 determines that the power factor control circuit 20 is operating in the continuous current mode, the voltage loop control module 31 is switched to the CCM proportional integral amplification unit 310 to output the voltage loop control module 31. The proportional parameter K P, CCM and the integral parameter K I, CCM , and the current loop control module 32 are switched to the continuous current compensation unit 321 , so that the continuous current compensation unit 321 generates the current compensation parameter as The feedforward control module 33 generates feedforward control parameters And feeding the feedforward control parameter to the current loop control module 32, the current loop control module 32 adds the feedforward control parameter and the current compensation parameter, and outputs a duty cycle of The pulse width modulation signal is sent to the control end of the active switch 21, and the duty cycle is the sum of the feedforward control parameter and the current compensation parameter.
同理,當該前饋控制模組33判斷功率因數控制電路20操作在不連續電流模式時,前饋控制模組33切換該電壓迴路控制模組31至DCM比例積分放大單元311,且切換電流迴路控制模組32至不連續電流補償單元322,則電流迴路控制模組32輸出一責任週期為的脈寬調變訊號至該主動開關21的控制端。Similarly, when the feedforward control module 33 determines that the power factor control circuit 20 is operating in the discontinuous current mode, the feedforward control module 33 switches the voltage loop control module 31 to the DCM proportional integral amplification unit 311, and switches the current. The loop control module 32 to the discontinuous current compensation unit 322, the current loop control module 32 outputs a duty cycle of The pulse width modulation signal is to the control end of the active switch 21.
綜合以上所述,該前饋控制器33可判斷出該功率因數控制電路20操作在何種電流模式,並對應切換電壓迴路控制模組31內的比例積分放大單元以及電流迴路控制模組32內的電流補償單元,使電流迴路控制模組32依據各電流模式輸出對應的脈寬調變訊號至主動開關21,其中又以各電流模式下的脈寬調變訊號中,主要是透過檢測功率因數控制電路20的電感電流IL,sense ,及該電壓迴路控制模組31輸出的參考電流iREF 之間的差值(iREF -IL,sense )關係以產生電流補償參數;請搭配參考圖3、圖9(先前技術的波形圖)與如下表1所示,圖3係本發明電路於不連續電流模式中的交流電壓、電流波形圖,由圖中可以見及,本發明電路的輸入電流Iac 較接近輸入電壓Vac 的波形,相較於先前技術,本發明在不連續電流模式中,脈寬調變訊號的責任週期為,因根據實際的電感電流IL,sense 與參考電流iREF 之間的差值而得,責任週期非僅為理論值,故可更有效改善功率因數與諧波的問題。In summary, the feedforward controller 33 can determine which current mode the power factor control circuit 20 operates in, and corresponding to the proportional integral amplification unit and the current loop control module 32 in the switching voltage loop control module 31. The current compensation unit causes the current loop control module 32 to output a corresponding pulse width modulation signal to the active switch 21 according to each current mode, wherein the pulse width modulation signal in each current mode is mainly used to detect the power factor. The difference between the inductor current I L, sense of the control circuit 20 and the reference current i REF output by the voltage loop control module 31 (i REF - I L, sense ) to generate a current compensation parameter; 3, Figure 9 (waveform diagram of the prior art) and Table 1 below, Figure 3 is the AC voltage and current waveform diagram of the circuit of the present invention in the discontinuous current mode, as can be seen from the figure, the input of the circuit of the present invention The current I ac is closer to the waveform of the input voltage V ac . Compared with the prior art, in the discontinuous current mode, the duty cycle of the pulse width modulation signal is According to the difference between the actual inductor current I L, sense and the reference current i REF , the duty cycle is not only the theoretical value, so the problem of power factor and harmonics can be more effectively improved.
請參考圖4所示,於另一較佳實施例中,功率因數控制電路20’為降壓式電源架構(Buck converter),包含有一主動開關21’、一二極體D、一電感L、一輸出電容C與一功率因數控制器30’;該主動開關21’、該電感L、該輸出電容C串接並與整流器10’構成一迴路,且該主動開關21’具有一控制端,該二極體D的陽極端連接整流器10’的輸出端,其陰極端連接於主動開關30’與電感L之間,該功率因數控制器30’連接該功率因數控制電路20’的輸出端與輸入端,且具有一輸出控制端連接該主動開關21’的控制端。Referring to FIG. 4, in another preferred embodiment, the power factor control circuit 20' is a buck converter, including an active switch 21', a diode D, and an inductor L. An output capacitor C and a power factor controller 30'; the active switch 21', the inductor L, the output capacitor C are connected in series and form a loop with the rectifier 10', and the active switch 21' has a control end, The anode end of the diode D is connected to the output end of the rectifier 10', and the cathode end thereof is connected between the active switch 30' and the inductor L. The power factor controller 30' is connected to the output and input of the power factor control circuit 20'. And an output control terminal is connected to the control end of the active switch 21'.
本較佳實施例之控制方法用於判斷的連續、不連續電流模式的運算式係,若D1<D2,則判斷功率因數控制電路20’操作在不連續電流模式,若D2<D1,則判斷功率因數控制電路20’操作在連續電流模式;又若功率因數控制電路20’操作在不連續電流模式時,功率因數控制器30’中前饋控制器產生的前饋控制參數為,該電流補償參數為F m (i REF -I L , sense ),因此脈寬調變訊號的責任週期為;若功率因數控制電路20’操作在連續電流模式時,功率因數控制器30’中前饋控制器產生的前饋控制參數為,而該電流補償參數為,因此脈寬調變訊號的責任週期為。其中:The control method of the preferred embodiment is used to determine the continuous, discontinuous current mode of the operating system If D1 < D2, it is determined that the power factor control circuit 20' operates in the discontinuous current mode. If D2 < D1, it is determined that the power factor control circuit 20' operates in the continuous current mode; and if the power factor control circuit 20' operates in In the discontinuous current mode, the feedforward control parameter generated by the feedforward controller in the power factor controller 30' is The current compensation parameter is F m ( i REF - I L , sense ), so the duty cycle of the pulse width modulation signal is If the power factor control circuit 20' operates in the continuous current mode, the feedforward control parameter generated by the feedforward controller in the power factor controller 30' is And the current compensation parameter is Therefore, the duty cycle of the pulse width modulation signal is . among them:
L:電感值;L: inductance value;
Vin,sense :輸入電壓;V in,sense : input voltage;
Vout,sense :輸出電壓;V out, sense : output voltage;
Vout :額定輸出電壓;V out : rated output voltage;
Ts:脈寬調變訊號的週期;Ts: the period of the pulse width modulation signal;
iREF :包含輸出電壓Vout,sense 成份的參考電流。i REF : Contains the reference current of the output voltage V out, sense component.
10...整流器10. . . Rectifier
10’...整流器10’. . . Rectifier
20...功率因數控制電路20. . . Power factor control circuit
20’...功率因數控制電路20’. . . Power factor control circuit
21...主動開關twenty one. . . Active switch
21’...主動開關twenty one'. . . Active switch
30...功率因數控制器30. . . Power factor controller
30’...功率因數控制器30’. . . Power factor controller
31...電壓迴路控制模組31. . . Voltage loop control module
310...CCM比例積分放大單元310. . . CCM proportional integral amplification unit
311...DCM比例積分放大單元311. . . DCM proportional integral amplification unit
32...電流迴路控制模組32. . . Current loop control module
321...連續電流補償單元321. . . Continuous current compensation unit
322...不連續電流補償單元322. . . Discontinuous current compensation unit
33...前饋控制模組33. . . Feedforward control module
50、50’...整流器50, 50’. . . Rectifier
60...負載60. . . load
70...交換式電源電路70. . . Switched power supply circuit
71、71’...功率因數校正電路71, 71’. . . Power factor correction circuit
711、711’...主動開關711, 711’. . . Active switch
72...直流/直流轉換器72. . . DC/DC converter
73...緩振單元73. . . Vibration relief unit
730...二極體730. . . Dipole
731...電阻731. . . resistance
732...電容732. . . capacitance
81...第一比例積分放大器81. . . First proportional integral amplifier
82...第二比例積分放大器82. . . Second proportional integral amplifier
83...多工器83. . . Multiplexer
84...驅動器84. . . driver
90...整流器90. . . Rectifier
91...交換式電源電路91. . . Switched power supply circuit
910...主動開關910. . . Active switch
92...功率因數控制器92. . . Power factor controller
921...連續電流模式921. . . Continuous current mode
922...不連續電流模式922. . . Discontinuous current mode
923...運算單元923. . . Arithmetic unit
圖1:升壓式電源電路及功率因數控制器連接示意圖。Figure 1: Schematic diagram of the connection of the boost power supply circuit and the power factor controller.
圖2:功率因數控制器詳細示意圖。Figure 2: Detailed schematic diagram of the power factor controller.
圖3:經電流補償的輸入電壓、電流波形圖。Figure 3: Current-compensated input voltage and current waveforms.
圖4:降壓式電源電路及功率因數控制器連接示意圖。Figure 4: Connection diagram of the buck power supply circuit and power factor controller.
圖5:已知的交換式電源電路及功率因數控制電路連接示意圖。Figure 5: Schematic diagram of the known switched power supply circuit and power factor control circuit connection.
圖6:另一已知的交換式電源電路及功率因數控制器連接示意圖。Figure 6: Schematic diagram of another known switched power supply circuit and power factor controller connection.
圖7:再一已知的交換式電源電路及功率因數控制器連接示意圖。Figure 7: A schematic diagram of another known switched power supply circuit and power factor controller connection.
圖8:圖7中的功率因數控制器示意圖。Figure 8: Schematic diagram of the power factor controller in Figure 7.
圖9:圖7中的交換式電源電路輸入電壓、電流波形示意圖。Figure 9: Schematic diagram of the input voltage and current waveforms of the switched power supply circuit in Figure 7.
21...主動開關twenty one. . . Active switch
30...功率因數控制器30. . . Power factor controller
31...電壓迴路控制模組31. . . Voltage loop control module
310...CCM比例積分放大單元310. . . CCM proportional integral amplification unit
311...DCM比例積分放大單元311. . . DCM proportional integral amplification unit
32...電流迴路控制模組32. . . Current loop control module
321...連續電流補償單元321. . . Continuous current compensation unit
322...不連續電流補償單元322. . . Discontinuous current compensation unit
33...前饋控制模組33. . . Feedforward control module
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TW100125374A TWI460571B (en) | 2011-07-19 | 2011-07-19 | Power factor control circuit and its control method |
CN201110213894.9A CN102904433B (en) | 2011-07-19 | 2011-07-28 | Power-factor control circuit and control method thereof |
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CN104348349B (en) * | 2013-08-09 | 2017-06-13 | 台达电子工业股份有限公司 | Suppress the control method of input current waveform harmonic distortion |
CN103746558B (en) * | 2013-12-25 | 2016-03-16 | 北京天诚同创电气有限公司 | Wind-force generating converter BOOST circuit DCM mode control method |
CN106332379B (en) * | 2015-06-16 | 2019-01-15 | 华硕电脑股份有限公司 | The driving circuit and its operation method of flash lamp light emitting diode |
CN106787668A (en) * | 2015-11-20 | 2017-05-31 | 南京理工大学 | A kind of power factor correcting converter of loading range wide |
CN109921621B (en) * | 2017-12-13 | 2020-09-04 | 爱士惟新能源技术(江苏)有限公司 | Bus voltage secondary ripple suppression method and device |
CN111256281B (en) * | 2018-11-30 | 2021-10-22 | 广东美的制冷设备有限公司 | Operation control method and system, compressor and air conditioner |
CN111614247B (en) * | 2020-03-26 | 2021-01-22 | 深圳市鑫翊新能源科技有限公司 | DCM control method and circuit of PFC converter and rectifier |
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TWI556564B (en) * | 2015-09-18 | 2016-11-01 | 強弦科技股份有限公司 | Converter control system |
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