CN108234375A - The launching technique and device of single carrier data - Google Patents
The launching technique and device of single carrier data Download PDFInfo
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- CN108234375A CN108234375A CN201611156147.5A CN201611156147A CN108234375A CN 108234375 A CN108234375 A CN 108234375A CN 201611156147 A CN201611156147 A CN 201611156147A CN 108234375 A CN108234375 A CN 108234375A
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2626—Arrangements specific to the transmitter only
- H04L27/2627—Modulators
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/0014—Carrier regulation
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2626—Arrangements specific to the transmitter only
- H04L27/2627—Modulators
- H04L27/2637—Modulators with direct modulation of individual subcarriers
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/0014—Carrier regulation
- H04L2027/0018—Arrangements at the transmitter end
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- Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
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Abstract
The present invention relates to the communications fields, disclose the launching technique and device of a kind of single carrier data.It in embodiment of the present invention, is modulated to sent the first data, obtains single carrier data to be sent；To the cyclic prefix of single carrier data addition preset length, the second data are obtained；By digital synthesizer DDS, second data are carried out with subcarrier maps and frequency deviation adjusts；Data after being adjusted to frequency deviation carry out pulse shape filter, and emit filtered data.Embodiment of the present invention, subcarrier maps are carried out to the single carrier data for adding the cyclic prefix of preset length by DDS and frequency deviation adjusts, it not only greatly reduces in conventional method and completes the complexity and calculation amount that subcarrier maps and frequency deviation adjust using IFFT and the adjustment of corresponding frequency deviation, and requirement and the power consumption of chip to realizing the calculating are reduced, thereby reduce the power consumption of terminal device.
Description
Technical field
The present invention relates to the communications field, the launching technique and device of more particularly to a kind of single carrier data.
Background technology
NB-IoT (Narrow Band Internet of Things, narrowband Internet of Things) is 3GPP (3rd
Generation Partnership Project, third generation partner program) the newest proposition of tissue specifically in object
The newest protenchyma networking protocol of networking, the agreement is based on ripe LTE (Long Term Evolution, long term evolution)
System, and significantly function and performance are carried out to protocol layer and physical layer according to the communication feature of Internet of Things on this basis
Cut out, so as to which NB-IoT terminals be enable preferably to realize wide covering, low-power consumption, low cost and the targets such as connect greatly.
It is provided according to 3GPP agreements, the uplink of NB-IoT is there are two types of form definition, and one kind is single carrier form, including sub- load
Wave spacing is two kinds of situations of 3.75kHz and 15kHz, and another kind is overloading waveshape, subcarrier spacing 15kHz, wherein, it can
The number of sub carrier wave of configuration has several situations such as 1,3,6,12 respectively, and NB-IoT downlinks only have a kind of form, i.e., between subcarrier
It is divided into the situation of 15kHz.NB-IoT system bandwidths are 180kHz, can be according to money in the case of subcarrier spacing is 3.75kHz
Source is dispatched and configuration, there is 48 sub-carrier configuring conditions, can be according to scheduling of resource in the case of subcarrier spacing is 15kHz
And configuration, there are a 12 sub-carrier configuring conditions, before the subcarrier spacing of two kinds of situations of 3.75kHz and 15kHz and corresponding cycle
Sew length, as represented shown in 1, wherein, when group intercarrier is divided into 3.75kHz, the length of a time slot is 61440Ts, i.e.,
2ms, when group intercarrier is divided into 15kHz, the length of a time slot is 15360Ts, i.e. 0.5ms, the time slot knot of single carrier data
Structure is as shown in Figure 1.
Table 1
Usually during hardware realization, in order to reduce computation complexity and reduce power consumption, for different bandwidth and sampling
Frequency can use the FFT (Fast Fourier Transformation, Fast Fourier Transform (FFT)) of different points to be calculated.
According to the protocol parameter of NB-IoT, 1.92MHz sample frequencys can be used in system and 128 point FFT are calculated, i.e., count FFT
Carry out 16 times of drop points processing.When group intercarrier is divided into 3.75kHz, according to table 1, the length of cyclic prefix is 4, works as subcarrier
Between when being divided into 15kHz, the length of cyclic prefix is respectively 10 (corresponding first Slot symbol) and 9 (correspondences second to the 7th
Slot symbol).Because the number of cyclic prefix is still integer, using the sample frequency, it is ensured that OFDM
The length of (Orthogonal Frequency Division Multiplexing, Orthogonal Frequency Division Multiplexing) symbol meets NB-IoT
The symbol lengths and frame length of protocol definition, using the transmitting processing of this conventional method as shown in Fig. 2, receiving processing such as Fig. 3
It is shown.Wherein, for transmitter, channel data to be transmitted first passes through IFFT (Inverse after ovennodulation maps
Fast Fourier Transform) transform to time domain because in NB-IoT agreements single carrier form only use 1 subcarrier into
Row data transmission, so in 128 data of progress IFFT transformation, only 1 data really transmitted, remaining 127 are
Zero, the reference by location table 1 of this data really transmitted can be configured by system, then according to table 1, for 3.75kHz and
The cyclic prefix of corresponding length is added at the different sub-carrier interval of 15kHz, a time slot is formed, then, by the single carrier of generation
The data of form carry out the adjustment of 1/2 subcarrier frequency deviation and pulse shape filter processing, you can are emitted.Receiver is come
It says, need first to find frame head according to the data received and is timed adjustment, cyclic prefix is then removed according to agreement, then
Data are subjected to 128 FFT transform, 1 data of needs are selected from the data after transformation can obtain the number of channel of transmission
According to.
However, during invention is realized, the inventors of the present application found that the transmitting processing of above-mentioned conventional method, is
Realization subcarrier maps need to carry out IFFT operations, are added to a large amount of invalid datas and carry out occupy-places, to the transmitter strap of terminal
Huge computation complexity is carried out, the requirement of the calculation amount for increasing terminal and the chip for realizing above-mentioned operation, so as to increase
The cost and power consumption of terminal.
Invention content
The launching technique and device that are designed to provide a kind of single carrier data of embodiment of the present invention, it is complete by DDS
It is handled into subcarrier maps and frequency deviation adjustment, so as to adjust the calculating of module instead of IFFT in conventional method and corresponding frequency deviation,
Not only greatly reduce terminal device transmitting single carrier data when computation complexity and calculation amount, but also reduce for realize
The requirement of the chip of the calculating and power consumption thereby reduce the cost and power consumption of terminal device.
In order to solve the above technical problems, embodiments of the present invention provide a kind of launching technique of single carrier data, packet
It includes：
It is modulated to sent the first data, obtains single carrier data to be sent；
To the cyclic prefix of single carrier data addition preset length, the second data are obtained；
By digital synthesizer DDS, second data are carried out with subcarrier maps and frequency deviation adjusts；
Data after being adjusted to frequency deviation carry out pulse shape filter, and emit filtered data.
Embodiments of the present invention additionally provide a kind of emitter of single carrier data, including：
Modulation mapper for being modulated to sent the first data, obtains single carrier data to be sent；
Cyclic prefix adder for the cyclic prefix to single carrier data addition preset length, obtains the second number
According to；
Digital synthesizer DDS, for second data to be carried out with subcarrier maps and frequency deviation adjustment；
Pulse shaping filter carries out pulse shape filter for the data after being adjusted to frequency deviation；
Transmitter, for emitting filtered data.
Embodiment of the present invention in terms of existing technologies, is modulated to sent the first data, is obtained pending
The single carrier data sent so as to the general process according to terminal transmission data, generates single carrier frequency numeric field data to be sent；To list
Carrier data adds the cyclic prefix of preset length, the second data is obtained, so as to generate the single carrier for meeting agreement specific length
Frequency domain data；By digital synthesizer DDS, second data are carried out with subcarrier maps and frequency deviation adjusts, frequency deviation is adjusted
Data afterwards carry out pulse shape filter, and emit filtered data, realize the transmitting of single carrier data, pass through DDS pairs
The single carrier data for adding the cyclic prefix of preset length carries out subcarrier maps and frequency deviation adjustment, not only greatly reduces terminal
Computation complexity and calculation amount when equipment emits single carrier data, and reduce chip to realizing the calculating requirement and
Power consumption thereby reduces the power consumption of terminal device.
In addition, it is described according to digital synthesizer DDS, second data are carried out with subcarrier maps and frequency deviation adjusts, tool
Body includes：The sinusoidal signal and cosine signal of frequency needed for the DDS generations；The sinusoidal signal and cosine signal difference
Complex multiplication is carried out with second data, obtains the data after subcarrier maps and frequency deviation adjustment.By required frequency just
String signal, cosine signal respectively with the simple complex multiplication of the second data, you can obtain subcarrier maps and frequency deviation adjustment after
Data thus greatly reduce in conventional method and complete subcarrier maps and frequency deviation tune with IFFT and corresponding frequency deviation adjustment module
Whole complexity and calculation amount.
In addition, the sinusoidal signal and cosine signal of frequency needed for the DDS generations, specifically include：According to fDDS=(k+1/
2) Δ f calculates the required frequency fDDS, wherein, Δ f is subcarrier spacing, and k is subcarrier maps position；According to the fDDS,
Calculate the target phase increment of the DDSAccording to describedPreset sine and cosine look-up table is searched, obtains the sinusoidal letter
Number and the cosine signal.The mode for searching sine and cosine look-up table obtains sinusoidal signal and cosine signal, simple and practicable, further
Reduce computation complexity.
It is in addition, described according to the fDDS, calculate the target phase increment of the DDSIt specifically includes：According toThe digit N of the phase accumulator of the DDS is calculated, wherein, resolution ratio of the Δ for the DDS, fclkFor institute
The working frequency of DDS is stated, N is positive integer；According to the fDDS, the fclkWith the N, the initial phase for calculating the DDS increases
Δ θ is measured, wherein,According to the phase accumulator, the Δ θ of the preset times that add up L is obtained describedWherein, L is positive integer so thatCalculating process it is simple, it is easy to accomplish.
Description of the drawings
Fig. 1 is the structure of time slot schematic diagram of single carrier data in the prior art；
Fig. 2 is the transmitting processing schematic diagram of single carrier data in the prior art；
Fig. 3 is the reception processing schematic diagram of single carrier data in the prior art；
Fig. 4 is the launching technique flow chart according to a kind of single carrier data of first embodiment of the invention；
Fig. 5 is the launching technique flow chart according to a kind of single carrier data of second embodiment of the invention；
Fig. 6 is the structure diagram according to a kind of emitter of single carrier data of third embodiment of the invention；
Fig. 7 is the structure diagram according to a kind of emitter of single carrier data of four embodiment of the invention.
Specific embodiment
To make the object, technical solutions and advantages of the present invention clearer, below in conjunction with attached drawing to each reality of the present invention
The mode of applying is explained in detail.However, it will be understood by those skilled in the art that in each embodiment of the present invention,
In order to make the reader understand this application better, many technical details are proposed.But even if without these technical details and base
In the various changes and modifications of following embodiment, the application technical solution claimed can also be realized.
First embodiment of the invention is related to a kind of launching technique of single carrier data.Idiographic flow is as shown in Figure 4.
In step 401, it modulates.
Specifically, being modulated to sent the first data, single carrier data to be sent is obtained, the step is with showing
There is technology identical, details are not described herein.
In step 402, cyclic prefix is added.
Specifically, to sent the cyclic prefix of single carrier data addition preset length, the second data are obtained,
In, the length of cyclic prefix is associated with used subcarrier spacing type, referring specifically to table 1, when base band use frequency for
When 1.92MHz and subcarrier spacing are 3.75KHz, corresponding circulating prefix-length is 4, when base band uses frequency as 1.92MHz
And subcarrier spacing is when being 15KHz, corresponding circulating prefix-length be respectively 10 (corresponding first Slot symbol) and 9 (correspondences
Second to the 7th Slot symbol).Further say, since the mapping of single carrier data carries out in a frequency domain, so
Data after mapping are still frequency domain data, so the cyclic prefix is to be added to single-carrier frequency-domain number to be sent in a frequency domain
According to.
In step 403, frequency f needed for calculatingDDS。
Specifically, the IFFT calculating process such as formula (1) in the conventional method of transmitting single carrier data is shown, work as progress
During the IFFT operations of M=128 points, since only there are one valid data (data of the point are set as X (k)), other 127 points are
Zero, then formula (1) formula (2) can be reduced to, wherein, it by IFFT operational transformations is data and one that the essence of formula (2), which is,
The complex multiplication operation of a sinusoidal signal and cosine signal has carried out data frequency deviation operation, formula (1) and formula
(2) it is as follows respectively：
According to formula (2) and protocol requirement, the frequency of above-mentioned sinusoidal signal and cosine signal is at least the integer of 3.75KHz
Again with 1/2 sub-carrier offset, therefore, DDS and f can be passed throughDDS=(k+1/2) Δ f, frequency f needed for calculatingDDS, and then generate
The sinusoidal signal and cosine signal of required frequency, wherein, Δ f is subcarrier spacing, and k is sub-carrier frequency domain position, and the specific of k takes
Value is configured by system according to table 1, when using the subcarrier spacing of 3.75KHz, i.e. during Δ f=3.75KHz, and the value of k
It can be -24, -23 ..., 22,23, that is, have 48 sub-carrier configuring conditions namely frequency needs to generate needed for sharing 48 kinds,
When using the subcarrier spacing of 15KHz, i.e. during Δ f=15KHz, the value of k can be -6, -5 ..., 4,5, that is, have 12 kinds
Sub-carrier configuration situation namely frequency needed for sharing 12 kinds need to generate.
In step 404, the digit of phase accumulator is calculated.
Specifically, according toThe digit N of the phase accumulator of DDS is calculated, wherein, Δ is DDS's
Resolution ratio, fclkFor the working frequency of DDS, N is positive integer, it is assumed that fclkThe digit N of=100MHz, then required phase accumulator
It is 16.
In step 405, initial phase increment Delta θ is calculated.
Specifically, according to fDDS、fclkWith N, the initial phase increment Delta θ of DDS is calculated, wherein,
According to the different values of k, fDDSDifferent values is had, then Δ θ also has different values, stores in a register successively
The Δ θ calculated every time, subsequently directly invokes, further reduces calculation amount.
Further say, according to the configuration of parameter k in table 1 and the requirement of agreement, there is several required frequency to need to generate,
Then necessarily there are one corresponding initial phase increment Delta θ for each required frequency, when realizing, can store the Δ θ calculated,
Subsequently according to the configuration of parameter k, the Δ θ of the storage can be directly invoked, without computing repeatedly again, further reduces meter
Calculation amount.
In a step 406, target phase increment is calculated
Specifically, by phase accumulator, the Δ θ of the preset times that add up L obtains target phase incrementWherein, L
For positive integer,Calculating process it is simple, it is easy to accomplish.
In step 407, it obtainsHigh-order significance bit.
Specifically, according toDigit N, take out several successively since Far Left as high-order significance bit, it is practical
In, when digit N is 16, digit needed for 8,5,10 or other can be taken out successively since Far Left as high
Position significance bit when digit N is 32, can take out digit needed for 16,10,20 or other successively since Far Left and make
For high-order significance bit.
In a step 408, sinusoidal signal and cosine signal are obtained.
Specifically, according to high-order significance bit, preset sine and cosine look-up table is searched, obtains corresponding sinusoidal signal and remaining
String signal, wherein, sinusoidal signal and cosine signal areN is sampling number, for a complete waveform, institute
The sine or cosine depth needed is 16, it is contemplated that sinusoidal and cosine waveform symmetry, when storage only need four points of storage this
One wavelength, that is, the address depth stored are 14.The mode for searching sine and cosine look-up table obtains sinusoidal signal and cosine letter
Number, it is simple and practicable, it further reduced computation complexity.
In step 409, complex multiplication is carried out.
Specifically, carrying out complex multiplication with the second data respectively by sinusoidal signal and cosine signal, realize to second
Subcarrier maps and the frequency deviation adjustment of data, sinusoidal signal, the real part of cosine signal and the second data and imaginary part are answered respectively
Number multiplyings, by the sinusoidal signal of required frequency, cosine signal respectively with the simple complex multiplication operation of the second data, i.e.,
The data after subcarrier maps and frequency deviation adjustment are can obtain, thus greatly reduces and IFFT and corresponding frequency deviation is used in conventional method
It adjusts module and completes subcarrier maps and the complexity and calculation amount of frequency deviation adjustment.
In step 410, pulse shape filter is carried out.
Specifically, the data after being adjusted to frequency deviation carry out pulse shape filter, the aliasing of signal is avoided, the step is with showing
There is technology identical, details are not described herein.
In step 411, emit the data after pulse shape filter.
Specifically, by the transmitting antenna of terminal device, the data after pulse shape filter are launched, the step
Same as the prior art, details are not described herein.
It is received and is demodulated it should be noted that conventional method still can be used in the receiving terminal of base station, do not need to do any
Adjustment and change so as to ensure there is preferable applicability and compatibility while terminal computation complexity is reduced, have
There is very big actual application value.Further, by taking M=128 points IFFT as an example, brief analysis is carried using conventional method transmitting is single
The complexity of wave number evidence and the complexity using the technology in embodiment of the present invention, in conventional methods where, for 128 point IFFT
Operation, complex multiplication are commonThe common N of complex addition × log2N=896 times carries out 1/2 subcarrier frequency deviation
The common complex multiplication of operation is N=128 times common, i.e., needs 576 complex multiplications and 896 complex additions in total, of the invention real
Applying only needs 128 complex multiplications in mode.
Compared with prior art, in the present embodiment, first according to fDDSFrequency f needed for=(k+1/2) Δ f calculatingDDS, then
According toThe digit N of the phase accumulator of DDS is calculated, then according to fDDS、fclkWith N, the initial phase of DDS is calculated
Position increment Delta θ, and the Δ θ of cumulative preset times L, obtain target phase incrementSo thatCalculating process it is simple, be easy to
It realizes, fromFar Left start to take out several successively as high-order significance bit, and according to the high-order significance bit, search pre-
If sine and cosine look-up table, obtain sinusoidal signal and cosine signal, search sine and cosine look-up table mode obtain sinusoidal signal and
Cosine signal, it is simple and practicable, further reduced computation complexity, last sinusoidal signal and cosine signal respectively with the second data
Complex multiplication is carried out, obtains the data after frequency adjustment, is counted respectively with second by the sinusoidal signal of required frequency, cosine signal
According to simple complex multiplication operation, you can obtain subcarrier maps and frequency deviation adjustment after data, thus greatly reduce tradition
In method the complexity and calculation amount that subcarrier maps and frequency deviation adjust are completed with IFFT and corresponding frequency deviation adjustment module.
Second embodiment of the invention is related to a kind of launching technique of single carrier data.Second embodiment is implemented first
It is further improved on the basis of mode, mainly thes improvement is that：In second embodiment of the invention, to frequency deviation tune
Data after whole carry out amplitude fading so that the requirement of the data fit pulse shape filter after frequency deviation adjusts, so that
Data symbol launch requirements, idiographic flow are as shown in Figure 5.
In step 501, it modulates.
In step 502, cyclic prefix is added.
In step 503, frequency f needed for calculatingDDS。
In step 504, the digit of phase accumulator is calculated.
In step 505, initial phase increment Delta θ is calculated.
In step 506, target phase increment is calculated
In step 507, obtainHigh-order significance bit.
In step 508, sinusoidal signal and cosine signal are obtained.
In step 509, complex multiplication is carried out.
In step 510, amplitude fading is carried out.
Specifically, amplitude fading is carried out by the data after being adjusted to frequency deviation, so as to generate the amplitude during IFFT
Decay namely so that the amplitude of the data after frequency deviation adjusts is consistent with the data amplitude in conventional method after IFFT, and then
Cause data fit launch requirements.
In step 511, pulse shape filter is carried out.
Specifically, pulse shape filter is carried out to the data after amplitude fading.
In step 512, emit the data after pulse shape filter.
In the present embodiment, amplitude fading is carried out by the data after being adjusted to frequency deviation so that after frequency deviation adjusts
The requirement of data fit pulse shape filter, so that data symbol launch requirements.
The step of various methods divide above, be intended merely to describe it is clear, when realization can be merged into a step or
Certain steps are split, are decomposed into multiple steps, as long as comprising identical logical relation, all in the protection domain of this patent
It is interior；To inessential modification is either added in algorithm in flow or introduces inessential design, but do not change its algorithm
Core design with flow is all in the protection domain of the patent.
Third embodiment of the invention is related to a kind of emitter of single carrier data, as shown in fig. 6, including：Modulation is reflected
Emitter 61, cyclic prefix adder 62, digital synthesizer 63, pulse shaping filter 64 and transmitter 65, wherein, digit synthesis
Device 63 specifically includes：Cosine and sine signal generator 631 and complex multiplier 632, cosine and sine signal generator 631 specifically include：
Frequency calculator 6311,6312 and first finder 6313 of target phase increment calculator, target phase increment calculator 6312
It specifically includes：Digit calculator 63121, initial phase increment calculator 63122 and accumulator 63123, the first finder 6313
It specifically includes：63131 and second finder 63132 of high-order significance bit interceptor.
Modulator 61 for being modulated to sent the first data, obtains single carrier data to be sent.
Cyclic prefix adder 62 for the cyclic prefix to single carrier data addition preset length, obtains the second data.
Digital synthesizer 63, for the second data to be carried out with subcarrier maps and frequency deviation adjustment.
Cosine and sine signal generator 631, for generating the sinusoidal signal and cosine signal of required frequency.
Frequency calculator 6311, for according to fDDS=(k+1/2) Δ f, frequency f needed for calculatingDDS, wherein, Δ f is carried for son
Wave spacing, k are subcarrier maps position.
Target phase increment calculator 6312, for according to fDDS, calculate the target phase increment of DDS
Digit calculator 63121, for basisThe digit N of the phase accumulator of DDS is calculated, wherein,
Resolution ratio of the Δ for DDS, fclkFor the working frequency of DDS, N is positive integer.
Initial phase increment calculator 63122, for according to fDDS、fclkWith N, the initial phase increment Delta θ of DDS is calculated,
Wherein,
Accumulator 63123 for the Δ θ for the preset times L that adds up, obtainsWherein, L is positive integer.
First finder 6313, for basisPreset sine and cosine look-up table is searched, obtains sinusoidal signal and cosine
Signal.
High-order significance bit interceptor 63131, for basisDigit, take out several works successively since Far Left
For high-order significance bit.
Second finder 63132, for according to high-order significance bit, searching preset sine and cosine look-up table, obtaining sinusoidal letter
Number and cosine signal.
Complex multiplier 632, for sinusoidal signal and cosine signal to be counted respectively with the second of cyclic prefix adder 62
According to complex multiplication is carried out, the data after subcarrier maps and frequency adjustment are obtained.
Pulse shaping filter 64 carries out pulse shape filter for the data after sub-carrier mapping and frequency deviation adjustment.
Transmitter 65, for emitting filtered data.
It is not difficult to find that present embodiment be with the corresponding system embodiment of first embodiment, present embodiment can be with
First embodiment is worked in coordination implementation.The relevant technical details mentioned in first embodiment still have in the present embodiment
Effect, in order to reduce repetition, which is not described herein again.Correspondingly, the relevant technical details mentioned in present embodiment are also applicable in
In first embodiment.
It is noted that each module involved in present embodiment is logic module, and in practical applications, one
A logic unit can be a part for a physical unit or a physical unit, can also be with multiple physics lists
The combination of member is realized.In addition, in order to protrude the innovative part of the present invention, it will not be with solving institute of the present invention in present embodiment
The technical issues of proposition, the less close unit of relationship introduced, but this does not indicate that there is no other single in present embodiment
Member.
Four embodiment of the invention is related to a kind of emitter of single carrier data.4th embodiment is implemented in third
It is further improved on the basis of mode, mainly thes improvement is that：In four embodiment of the invention, width is further included
Attenuator 66 is spent, as shown in Figure 7.
Modulator 61 for being modulated to sent the first data, obtains single carrier data to be sent.
Cyclic prefix adder 62 for the cyclic prefix to single carrier data addition preset length, obtains the second data.
Digital synthesizer 63, for the second data to be carried out with subcarrier maps and frequency deviation adjustment.
Cosine and sine signal generator 631, for generating the sinusoidal signal and cosine signal of required frequency.
Frequency calculator 6311, for according to fDDS=(k+1/2) Δ f, frequency f needed for calculatingDDS, wherein, Δ f is carried for son
Wave spacing, k are subcarrier maps position.
Target phase increment calculator 6312, for according to fDDS, calculate the target phase increment of DDS
Digit calculator 63121, for basisThe digit N of the phase accumulator of DDS is calculated, wherein,
Resolution ratio of the Δ for DDS, fclkFor the working frequency of DDS, N is positive integer.
Initial phase increment calculator 63122, for according to fDDS、fclkWith N, the initial phase increment Delta θ of DDS is calculated,
Wherein,
Accumulator 63123 for the Δ θ for the preset times L that adds up, obtainsWherein, L is positive integer.
First finder 6313, for basisPreset sine and cosine look-up table is searched, obtains sinusoidal signal and cosine
Signal.
High-order significance bit interceptor 63131, for basisDigit, take out several works successively since Far Left
For high-order significance bit.
Second finder 63132, for according to high-order significance bit, searching preset sine and cosine look-up table, obtaining sinusoidal letter
Number and cosine signal.
Complex multiplier 632, for sinusoidal signal and cosine signal to be counted respectively with the second of cyclic prefix adder 62
According to complex multiplication is carried out, the data after subcarrier maps and frequency adjustment are obtained.
Amplitude fading device 66 carries out amplitude fading for the data after sub-carrier mapping and frequency deviation adjustment.
Pulse shaping filter 64, for the data (data after the adjustment of the data, that is, frequency deviation) after amplitude fading into
Row pulse shape filter.
Transmitter 65, for emitting filtered data.
Since second embodiment is corresponded with present embodiment, present embodiment can be mutual with second embodiment
Match implementation.The relevant technical details mentioned in second embodiment are still effective in the present embodiment, implement second
The attainable technique effect of institute can similarly be realized in the present embodiment in mode, no longer superfluous here in order to reduce repetition
It states.Correspondingly, the relevant technical details mentioned in present embodiment are also applicable in second embodiment.
It will be appreciated by those skilled in the art that all or part of the steps of the method in the foregoing embodiments are can to pass through
Program is completed to instruct relevant hardware, which is stored in a storage medium, is used including some instructions so that one
A equipment (can be microcontroller, chip etc.) or processor (processor) perform each embodiment the method for the application
All or part of step.And aforementioned storage medium includes：USB flash disk, mobile hard disk, read-only memory (ROM, Read-Only
Memory), random access memory (RAM, Random Access Memory), magnetic disc or CD etc. are various can store journey
The medium of sequence code.
It will be understood by those skilled in the art that the respective embodiments described above are to realize specific embodiments of the present invention,
And in practical applications, can to it, various changes can be made in the form and details, without departing from the spirit and scope of the present invention.
Claims (12)
1. a kind of launching technique of single carrier data, which is characterized in that applied to the terminal device based on protenchyma networking protocol,
Including：
It is modulated to sent the first data, obtains single carrier data to be sent；
To the cyclic prefix of single carrier data addition preset length, the second data are obtained；
By digital synthesizer DDS, second data are carried out with subcarrier maps and frequency deviation adjusts；
Data after being adjusted to frequency deviation carry out pulse shape filter, and emit filtered data.
2. the launching technique of single carrier data according to claim 1, which is characterized in that described to pass through digital synthesizer
DDS, carries out second data subcarrier maps and frequency deviation adjusts, and specifically includes：
The sinusoidal signal and cosine signal of frequency needed for the DDS generations；
The sinusoidal signal and the cosine signal carry out complex multiplication with second data respectively, obtain corresponding subcarrier
Data after mapping and frequency deviation adjustment.
3. the launching technique of single carrier data according to claim 2, which is characterized in that frequency needed for the DDS generations
Sinusoidal signal and cosine signal, specifically include：
According to fDDS=(k+1/2) Δ f calculate the required frequency fDDS, wherein, Δ f is subcarrier spacing, and k is reflected for subcarrier
Penetrate position；
According to the fDDS, calculate the target phase increment of the DDS
According to describedPreset sine and cosine look-up table is searched, obtains the sinusoidal signal and the cosine signal.
4. the launching technique of single carrier data according to claim 3, which is characterized in that described according to the fDDS, calculate
The target phase increment of the DDSIt specifically includes：
According toThe digit N of the phase accumulator of the DDS is calculated, wherein, Δ is the resolution ratio of the DDS,
fclkFor the working frequency of the DDS, N is positive integer；
According to the fDDS, the fclkWith the N, the initial phase increment Delta θ of the DDS is calculated, wherein,
By the phase accumulator, the Δ θ of the preset times that add up L is obtained describedWherein, L is positive integer.
5. the launching technique of single carrier data according to claim 3, which is characterized in that described in the basisIt searches
Preset sine and cosine look-up table, obtains the sinusoidal signal and the cosine signal, specifically includes：
According to describedDigit, take out several successively since Far Left as high-order significance bit；
According to the high-order significance bit, preset sine and cosine look-up table is searched, obtains the sinusoidal signal and the cosine signal.
6. the launching technique of single carrier data according to claim 2, which is characterized in that in the sinusoidal signal and described
Cosine signal carries out complex multiplication with second data respectively, after obtaining the data after subcarrier maps and frequency deviation adjustment,
It further includes：
Data after being adjusted to the frequency deviation carry out amplitude fading；
Data after the adjustment to frequency deviation carry out pulse shape filter, specifically include：Data after amplitude fading are carried out
Pulse shape filter.
7. the launching technique of single carrier data according to claim 4, which is characterized in that described according to the fDDS, institute
State fclkWith the N, after the initial phase increment Delta θ for calculating the DDS, further include：
Store the Δ θ.
8. a kind of emitter of single carrier data, which is characterized in that applied to the terminal device based on protenchyma networking protocol,
Including：
Modulation mapper for being modulated to sent the first data, obtains single carrier data to be sent；
Cyclic prefix adder for the cyclic prefix to single carrier data addition preset length, obtains the second data；
Digital synthesizer DDS, for second data to be carried out with subcarrier maps and frequency deviation adjustment；
Pulse shaping filter carries out pulse shape filter for the data after being adjusted to frequency deviation；
Transmitter, for emitting filtered data.
9. the emitter of single carrier data according to claim 8, which is characterized in that the digital synthesizer DDS tools
Body includes：Cosine and sine signal generator and complex multiplier；
The cosine and sine signal generator, for generating the sinusoidal signal and cosine signal of required frequency；
The complex multiplier, for the sinusoidal signal and the cosine signal to be carried out plural number with second data respectively
It is multiplied, obtains the data after subcarrier maps and frequency deviation adjustment.
10. the emitter of single carrier data according to claim 9, which is characterized in that the cosine and sine signal occurs
Implement body includes：Frequency calculator, target phase increment calculator and the first finder；
The frequency calculator, for according to fDDS=(k+1/2) Δ f calculate the required frequency fDDS, wherein, Δ f is carried for son
Wave spacing, k are subcarrier maps position；
Target phase increment calculator, for according to the fDDS, calculate the target phase increment of the DDS
First finder, for according toPreset sine and cosine look-up table is searched, obtains the sinusoidal signal and described remaining
String signal.
11. the emitter of single carrier data according to claim 10, which is characterized in that the target phase increment meter
Implement body is calculated to include：Digit calculator, initial phase increment calculator and accumulator；
The digit calculator, for basisThe digit N of the phase accumulator of the DDS is calculated, wherein,
Resolution ratio of the Δ for the DDS, fclkFor the working frequency of the DDS, N is positive integer；
The initial phase increment calculator, for according to the fDDS, the fclkWith the N, the initial phase of the DDS is calculated
Position increment Delta θ, wherein,
The accumulator for the Δ θ for the preset times L that adds up, obtains describedWherein, L is positive integer.
12. the emitter of single carrier data according to claim 10, which is characterized in that described first searches implement body
Including：High-order significance bit interceptor and the second finder；
High-order significance bit interceptor, for according toDigit, take out several successively since Far Left as high-order
Significance bit；
Second finder, for according to the high-order significance bit, searching preset sine and cosine look-up table, obtaining the sine
Signal and the cosine signal.
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| CN1303543A (en) * | 1998-06-29 | 2001-07-11 | 诺基亚网络有限公司 | Power control in multi-carrier radio transmitter |
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| CN103200145A (en) * | 2013-04-03 | 2013-07-10 | 北京大学 | Orthogonal frequency division multiplexing (OFDM) transmitter implementing method based on DDS principle |
| CN103685128A (en) * | 2013-12-27 | 2014-03-26 | 湖北民族学院科技学院 | Orthogonal Frequency Division Multiplexing (OFDM) transmitter based Inverse Fast Fourier Transform (IFFT) processor and IFFT implementation method |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1303543A (en) * | 1998-06-29 | 2001-07-11 | 诺基亚网络有限公司 | Power control in multi-carrier radio transmitter |
| CN1781271A (en) * | 2003-02-28 | 2006-05-31 | Rgb网络有限公司 | Cost-effective multi-channel quadrature amplitude modulation |
| CN1838539A (en) * | 2006-04-24 | 2006-09-27 | 南京东大宽带通信技术有限公司 | Application method for frequency synthesizer in OFDM system |
| CN103200145A (en) * | 2013-04-03 | 2013-07-10 | 北京大学 | Orthogonal frequency division multiplexing (OFDM) transmitter implementing method based on DDS principle |
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