CN107846164B - Motor driving system based on MMC and discrete control method thereof - Google Patents

Motor driving system based on MMC and discrete control method thereof Download PDF

Info

Publication number
CN107846164B
CN107846164B CN201711096226.6A CN201711096226A CN107846164B CN 107846164 B CN107846164 B CN 107846164B CN 201711096226 A CN201711096226 A CN 201711096226A CN 107846164 B CN107846164 B CN 107846164B
Authority
CN
China
Prior art keywords
axis
bridge arm
mmc
motor
mathematical model
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
CN201711096226.6A
Other languages
Chinese (zh)
Other versions
CN107846164A (en
Inventor
黄允凯
夏天琦
彭飞
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Southeast University
Original Assignee
Southeast University
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Southeast University filed Critical Southeast University
Priority to CN201711096226.6A priority Critical patent/CN107846164B/en
Publication of CN107846164A publication Critical patent/CN107846164A/en
Application granted granted Critical
Publication of CN107846164B publication Critical patent/CN107846164B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/0003—Control strategies in general, e.g. linear type, e.g. P, PI, PID, using robust control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H02P27/14—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation with three or more levels of voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P2201/00—Indexing scheme relating to controlling arrangements characterised by the converter used

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)
  • Inverter Devices (AREA)
  • Other Investigation Or Analysis Of Materials By Electrical Means (AREA)

Abstract

The invention discloses a motor driving system based on a modular multilevel converter and a discrete control method thereof, wherein the system comprises the modular multilevel converter and a motor, and the output end of the modular multilevel converter is connected with the motor; the three-phase bridge comprises three phases, wherein each phase comprises an upper bridge arm and a lower bridge arm, the upper bridge arm and the lower bridge arm respectively comprise N identical submodules and bridge arm inductors which are connected in series, the input end of a first submodule of the upper bridge arm and the output end of a last submodule of the lower bridge arm are respectively connected with a direct current bus, the output end of the last submodule is connected with the input end of the next submodule, and the output end of the last submodule of the upper bridge arm is connected with the input end of the first submodule of the lower bridge arm through the upper bridge arm inductor and the lower bridge arm; the connection point of the upper bridge arm inductor and the lower bridge arm inductor of each phase is the output end of the bridge, and the three output ends are connected with the three phases of the motor. The invention discretizes the motor driving system based on the modular multilevel converter, and realizes the stable operation of the motor under multilevel driving.

Description

Motor driving system based on MMC and discrete control method thereof
Technical Field
The invention relates to a motor drive control technology, in particular to a motor drive system discrete control method based on a Modular Multilevel Converter (MMC).
Background
The Modular Multilevel Converter (MMC) is a novel Multilevel Converter, has a highly Modular structure and high efficiency, is convenient for expanding system voltage and capacity, and realizes industrial production. The modular multilevel converter drives the high-speed permanent magnet motor, a high-voltage multilevel output can be realized by the low-voltage-resistant switch without a large-capacity transformer, the equivalent switching frequency is high, the waveform is closer to a sine wave, and the system loss can be reduced.
For digital control technology, the conventional design of a motor drive controller usually adopts a zero-order keeper method, and the controller is designed in a frequency domain on the assumption that parameters such as voltage, current and the like of a system are kept unchanged in one period. For the motor driving system based on the modular multilevel converter, the data volume is large, and especially in the high-frequency stage, the assumption that the parameters are kept unchanged in one sampling period does not exist. A more accurate mathematical model needs to be established, and a corresponding controller needs to be designed according to the state equation of the model.
Disclosure of Invention
The purpose of the invention is as follows: a Modular Multilevel Converter (MMC) -based motor driving system and a discrete control method thereof are provided to solve the disadvantages of the prior art.
The technical scheme is as follows: the invention discloses a motor driving system based on a modular multilevel converter, which comprises the modular multilevel converter and a motor, wherein the output end of the modular multilevel converter is connected with the motor;
the modular multilevel converter comprises three phases, each phase comprises an upper bridge arm and a lower bridge arm, the upper bridge arm and the lower bridge arm respectively comprise N identical sub-modules SMi, i is 1,2, 1, N and a bridge arm inductor L which are connected in series, the input end of the first sub-module of the upper bridge arm and the output end of the last sub-module of the lower bridge arm are respectively connected with a direct current bus, the output end of the last sub-module of the upper bridge arm is connected with the input end of the next sub-module, and the output end of the last sub-module of the upper bridge arm is connected with the input end of the first sub-module of the lower bridge arm through the upper bridge arm inductor and the lower bridge arm; and the connection point of the upper bridge arm inductor and the lower bridge arm inductor of each phase is the output end of the modular multilevel converter, and the three output ends are connected with three phases of the motor.
Furthermore, the sub-module is a half-bridge module and comprises high-power controllable power electronic switches T1 and T2, two diodes and a capacitor C, wherein T1 and T2 are connected with one diode in anti-parallel, then connected in series and finally connected with the capacitor C in parallel respectively.
Further, the high-power controllable power electronic switches T1 and T2 are insulated gate bipolar transistors.
Furthermore, the number of the upper bridge arm sub-modules and the number of the lower bridge arm sub-modules are even numbers respectively.
In another embodiment, a modular multilevel converter-based motor driving system discrete control method includes the following steps:
(1) establishing MMC output mathematical model equation
According to kirchhoff's law, the bridge arm voltage can be expressed as:
Figure BDA0001462275080000021
wherein E is the DC bus voltage vpj、vnjJ-phase upper and lower bridge arm voltages, ipj、injJ phases of upper and lower bridge arm currents, ijJ phase current on the AC side, L bridge arm inductance, LsIs the inductance of the motor winding, RsIs the motor winding resistance, ejJ ═ a, b, c for each opposite potential of the motor;
therefore, the MMC output mathematical model equation can be obtained by the bridge arm voltage mathematical model equation:
Figure BDA0001462275080000022
definition of
Figure BDA0001462275080000023
The MMC outputs a mathematical model equation as follows:
Figure BDA0001462275080000024
(2) clarke and Park conversion is carried out on an MMC output mathematical model equation (2) to obtain an MMC output mathematical model under a dq coordinate system:
Figure BDA0001462275080000025
wherein v isd、vqAre each vjD-and q-axis components transformed into dq-coordinate system, ed、eqAre each ejD-and q-axis components, i, transformed into dq-coordinate systemd、iqAre respectively ijTransforming to d-axis and q-axis components in a dq coordinate system;
according to the MMC output mathematical model equation (4), the following can be obtained:
Figure BDA0001462275080000031
wherein, ω iseThe angular velocity of the motor;
discretizing (5) to establish a discrete domain model:
Figure BDA0001462275080000032
wherein the content of the first and second substances,
Figure BDA0001462275080000033
Figure BDA0001462275080000034
Figure BDA0001462275080000035
wherein id(tn)、iq(tn) Are each tnD-axis and q-axis currents v obtained by sampling and calculating at any momentd(tn)、vq(tn) Are each tnD-axis and q-axis voltages calculated at times, ed(tn)、eq(tn) Are each tnMoment motor d-axis and q-axis back-emf, TsIs the current loop sampling period, omegaeThe angular velocity of the motor;
(3) MMC current loop design
The discrete controller design is as follows:
Figure BDA0001462275080000036
wherein the content of the first and second substances,
Figure BDA0001462275080000037
d-axis and q-axis current instruction values are respectively obtained, K is a control coefficient, and a transfer function under a z domain can be further obtained:
Figure BDA0001462275080000041
wherein, IdIs id(tn+Ts) In the form of expression in the Z domain,
Figure BDA0001462275080000042
is composed of
Figure BDA0001462275080000043
In the Z domain, in order to ensure system stability, and all poles are within the unit circle, K is in the range of 0<K<1；
By the formulae (6) and (10), it is possible to obtain:
Figure BDA0001462275080000044
therefore, the first and second electrodes are formed on the substrate,
Figure BDA0001462275080000045
so MMC is t under dq coordinate systemnD-axis and q-axis currents i obtained by sampling and calculating at momentd(tn)、iq(tn) And d-axis and q-axis output voltages v at the next timed(tn+Ts)、vq(tn+Ts) The relationship is as follows:
Figure BDA0001462275080000046
wherein the content of the first and second substances,
Figure BDA0001462275080000047
Figure BDA0001462275080000048
Figure BDA0001462275080000049
ΦPMis a permanent magnet flux linkage of the motor;
(4) v is to bed(tn+Ts)、vq(tn+Ts) Obtaining three-phase output voltage v through dq/abc conversiona(tn+Ts)、vb(tn+Ts) And vc(tn+Ts) And as a three-phase modulation signal of the MMC, carrying out carrier phase shift modulation on the MMC.
Has the advantages that: compared with the prior art, the motor driving system based on the modular multilevel converter is discretized, a discrete mathematical model is established, the discrete controller of the driving system is designed according to the delay one-beat characteristic of the digital signal processor, and stable operation of the motor under multilevel driving is realized. The discrete control method has the following advantages:
(1) each bridge arm of the modularized multi-level is composed of N sub-modules, the bearing voltage of each sub-module is Vdc/N (Vdc is direct-current bus voltage), the specification requirements on power electronic switching devices are reduced for medium-high voltage high-power occasions, and system capacity expansion is easy to realize;
(2) the modularized multi-level converter has high equivalent switching frequency, reduces the requirement of a motor on high switching frequency of a switching device and system loss, and saves hardware resources;
(3) the designed discrete controller has strong dynamic characteristics and is suitable for actual operation by adopting a digital signal processor;
(4) the stable operation of the motor driving system based on the MMC is realized, and the reliability is high.
Drawings
FIG. 1 is a schematic diagram of a modular multilevel converter based motor drive system topology;
FIG. 2 is a circuit diagram of a modular multilevel converter based motor drive system;
fig. 3 is a schematic diagram of discrete sampling and duty cycle updating of a digital signal processor.
Detailed Description
The invention is further described below with reference to the accompanying drawings.
Fig. 1 is a topological diagram of a motor driving system based on a modular multilevel converter, which is composed of the modular multilevel converter and a motor, and the output end of the modular multilevel converter is connected with the motor. The modular multilevel converter comprises A, B phases and C phases, each phase is formed by connecting an upper bridge arm, a lower bridge arm and a bridge arm inductor L in series, the upper bridge arm and the lower bridge arm respectively comprise N sub-modules SM 1-SMn, and in order to enable the modular multilevel converter to output zero level, the number of the bridge arm sub-modules is even; the connection point of the upper bridge arm inductor L and the lower bridge arm inductor L is an alternating current side electrical interface of the modular multilevel converter, three alternating current nodes are externally connected with the motor, and the circuit topologies of all the submodules SM 1-SMn are the same and are all half-bridge modules.
Each sub-module comprises high-power controllable power electronic switches T1 and T2, and T1 and T2 can be insulated gate bipolar transistors (IGBT for short); anti-parallel diodes of T1, T2; a submodule direct-current capacitor C; each submodule is in a half-bridge structure; the switching devices T1 and T2 are connected in parallel with a diode in reverse, then in series, and then in parallel with the capacitor C. The upper bridge arm and the lower bridge arm are formed by connecting N sub-modules in series, the input end of the first sub-module of the upper bridge arm and the output end of the last sub-module of the lower bridge arm are respectively connected with a direct current bus, and the output end of the last sub-module is connected with the input end of the next sub-module.
A method for discrete control of a motor driving system based on a modular multilevel converter comprises the steps of establishing an MMC output mathematical model equation, establishing a discrete domain model in a discretization mode, designing a discrete controller, calculating a modulation voltage signal of an MMC required at the next moment according to current sampled at the current moment, and carrying out carrier phase shift modulation on the MMC. The method specifically comprises the following steps:
(1) establishing MMC output mathematical model equation
Fig. 2 is a circuit diagram of a motor driving system based on a modular multilevel converter, and according to kirchhoff's law, bridge arm voltages can be expressed as:
Figure BDA0001462275080000061
wherein E is the DC bus voltage vpj、vnjJ-phase upper and lower bridge arm voltages, ipj、injJ phases of upper and lower bridge arm currents, ijJ phase current on the AC side, L bridge arm inductance, LsIs the inductance of the motor winding, RsIs the motor winding resistance, ejThe motor has opposite potentials, j ═ a, b and c.
Therefore, the MMC output mathematical model equation can be obtained by the bridge arm voltage mathematical model equation:
Figure BDA0001462275080000062
definition of
Figure BDA0001462275080000063
The MMC outputs a mathematical model equation as follows:
Figure BDA0001462275080000064
(2) clarke and Park conversion is carried out on an MMC output mathematical model equation (2) to obtain an MMC output mathematical model under a dq coordinate system:
Figure BDA0001462275080000065
wherein v isd、vqAre each vjD-and q-axis components transformed into dq-coordinate system, ed、eqAre each ejD-and q-axis components, i, transformed into dq-coordinate systemd、iqAre respectively ijTransformed to d-axis and q-axis components in the dq coordinate system.
FIG. 3 is a schematic diagram of discrete sampling and duty cycle updating of a digital signal processor, showing a carrier period start tnCurrent sampling is carried out at any moment, and the duty ratio obtained by the calculation of the sampling current value is at the next sampling point tn+TsThe time is updated, i.e. there is a delay of one carrier period (current loop sampling period).
According to the state space equation under the continuous time domain:
Figure BDA0001462275080000071
where X (t) is an n-dimensional state vector, U (t) is an r × 1 input column vector, A is an n × n square matrix, and B is an n × r control matrix.
Discretizing the vector to obtain:
X(tn+Ts)＝F(Ts)X(tn)+G(Ts)V (6)；
wherein, F (T)s) Is an m × n output matrix, G (T)s) Is an m x r direct transfer matrix.
Rewriting formula (4) as:
Figure BDA0001462275080000072
wherein, ω iseIs the angular velocity of the motor.
Discretizing the formula (7) to establish a discrete domain model:
Figure BDA0001462275080000073
wherein the content of the first and second substances,
Figure BDA0001462275080000074
Figure BDA0001462275080000075
Figure BDA0001462275080000081
wherein id(tn)、iq(tn) Are each tnD-axis and q-axis currents v obtained by sampling and calculating at any momentd(tn)、vq(tn) Are each tnD-axis and q-axis voltages calculated at times, ed(tn)、eq(tn) Are each tnMoment motor d-axis and q-axis back-emf, TsIs the current loop sampling period, omegaeIs the angular velocity of the motor.
(3) MMC current loop design
The discrete controller design is as follows:
Figure BDA0001462275080000082
wherein the content of the first and second substances,
Figure BDA0001462275080000083
d-axis and q-axis current instruction values are respectively obtained, K is a control coefficient, and a transfer function under a z domain can be further obtained:
Figure BDA0001462275080000084
wherein, IdIs id(tn+Ts) In the form of expression in the Z domain,
Figure BDA0001462275080000085
is composed of
Figure BDA0001462275080000086
In the Z domain, in order to ensure the stability of the system, all poles should be within the unit circle, so the range of K is 0<K<1。
By the formulae (8) and (12), it is possible to obtain:
Figure BDA0001462275080000087
therefore, the first and second electrodes are formed on the substrate,
Figure BDA0001462275080000088
so MMC is t under dq coordinate systemnD-axis and q-axis currents i obtained by sampling and calculating at momentd(tn)、iq(tn) And d-axis and q-axis output voltages v at the next timed(tn+Ts)、vq(tn+Ts) The relationship is as follows:
Figure BDA0001462275080000091
wherein the content of the first and second substances,
Figure BDA0001462275080000092
Figure BDA0001462275080000093
Figure BDA0001462275080000094
ΦPMis a permanent magnet flux linkage of the motor.
(4) V is to bed(tn+Ts)、vq(tn+Ts) Obtaining three-phase output voltage v through dq/abc conversiona(tn+Ts)、vb(tn+Ts) And vc(tn+Ts) Namely, the three-phase modulation signal of the MMC.
V required by the next moment is obtaineda(tn+Ts)、vb(tn+Ts) And vc(tn+Ts) The phase shift modulation is carried out on the MMC as a modulation signal of the MMC, so that the modular multilevel converter for the motor driving system can stably operate in practical engineering application adopting a digital signal processor.
The foregoing is only a preferred embodiment of the present invention, and it should be noted that, for those skilled in the art, various modifications and decorations can be made without departing from the principle of the present invention, and these modifications and decorations should also be regarded as the protection scope of the present invention.

Claims (1)

1. A discrete control method of a motor driving system based on a modular multilevel converter is characterized by comprising the following steps:
(1) establishing MMC output mathematical model equation
According to kirchhoff's law, the bridge arm voltage can be expressed as:
Figure FDA0002257168840000011
wherein E is the DC bus voltage vpj、vnjJ-phase upper and lower bridge arm voltages, ipj、injJ phases of upper and lower bridge arm currents, ijJ phase current on the AC side, L bridge arm inductance, LsIs the inductance of the motor winding, RsIs the motor winding resistance, ejJ ═ a, b, c for each opposite potential of the motor;
therefore, the MMC output mathematical model equation can be obtained by the bridge arm voltage mathematical model equation:
Figure FDA0002257168840000012
definition of
Figure FDA0002257168840000013
The MMC outputs a mathematical model equation as follows:
Figure FDA0002257168840000014
(2) clarke and Park conversion is carried out on an MMC output mathematical model equation (2) to obtain an MMC output mathematical model under a dq coordinate system:
Figure FDA0002257168840000015
wherein v isd、vqAre each vjD-and q-axis components transformed into dq-coordinate system, ed、eqAre each ejD-and q-axis components, i, transformed into dq-coordinate systemd、iqAre respectively ijTransforming to d-axis and q-axis components in a dq coordinate system;
according to the MMC output mathematical model equation (4), the following can be obtained:
Figure FDA0002257168840000021
wherein, ω iseThe angular velocity of the motor;
discretizing (5) to establish a discrete domain model:
Figure FDA0002257168840000022
wherein the content of the first and second substances,
Figure FDA0002257168840000023
Figure FDA0002257168840000024
Figure FDA0002257168840000025
wherein id(tn)、iq(tn) Are each tnD-axis and q-axis currents v obtained by sampling and calculating at any momentd(tn)、vq(tn) Are each tnD-axis and q-axis voltages calculated at times, ed(tn)、eq(tn) Are each tnMoment motor d-axis and q-axis back-emf, TsIs the current loop sampling period, omegaeThe angular velocity of the motor;
(3) MMC current loop design
The discrete controller design is as follows:
Figure FDA0002257168840000026
wherein，
Figure FDA0002257168840000027
D-axis and q-axis current instruction values are respectively obtained, K is a control coefficient, and a transfer function under a z domain can be further obtained:
Figure FDA0002257168840000031
wherein, IdIs id(tn+Ts) In the form of expression in the Z domain,
Figure FDA0002257168840000032
is composed of
Figure FDA0002257168840000033
In the expression form under the Z domain, in order to ensure the stability of the system, all poles are in a unit circle, so that the range of K is more than 0 and less than 1;
by the formulae (6) and (10), it is possible to obtain:
Figure FDA0002257168840000034
therefore, the first and second electrodes are formed on the substrate,
Figure FDA0002257168840000035
so MMC is t under dq coordinate systemnD-axis and q-axis currents i obtained by sampling and calculating at momentd(tn)、iq(tn) And d-axis and q-axis output voltages v at the next timed(tn+Ts)、vq(tn+Ts) The relationship is as follows:
Figure FDA0002257168840000036
wherein the content of the first and second substances,
Figure FDA0002257168840000037
Figure FDA0002257168840000038
Figure FDA0002257168840000039
ΦPMis a permanent magnet flux linkage of the motor;
(4) v is to bed(tn+Ts)、vq(tn+Ts) Obtaining three-phase output voltage v through dq/abc conversiona(tn+Ts)、vb(tn+Ts) And vc(tn+Ts) And as a three-phase modulation signal of the MMC, carrying out carrier phase shift modulation on the MMC.
CN201711096226.6A 2017-11-09 2017-11-09 Motor driving system based on MMC and discrete control method thereof Active CN107846164B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN201711096226.6A CN107846164B (en) 2017-11-09 2017-11-09 Motor driving system based on MMC and discrete control method thereof

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN201711096226.6A CN107846164B (en) 2017-11-09 2017-11-09 Motor driving system based on MMC and discrete control method thereof

Publications (2)

Publication Number Publication Date
CN107846164A CN107846164A (en) 2018-03-27
CN107846164B true CN107846164B (en) 2020-03-31

Family

ID=61681801

Family Applications (1)

Application Number Title Priority Date Filing Date
CN201711096226.6A Active CN107846164B (en) 2017-11-09 2017-11-09 Motor driving system based on MMC and discrete control method thereof

Country Status (1)

Country Link
CN (1) CN107846164B (en)

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN109004814B (en) * 2018-08-13 2020-03-24 南昌工程学院 Submodule capacitor voltage balance control system for MMC
CN109039124B (en) * 2018-08-13 2020-06-09 南昌工程学院 MMC capacitor voltage balance control method based on phase-shift space vector modulation
CN109830995B (en) * 2018-12-28 2021-03-02 浙江华云清洁能源有限公司 Island control strategy based on energy router

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN104811069A (en) * 2015-05-13 2015-07-29 山东大学 Prediction control method for modularized multi-level inverter
GB2538270A (en) * 2015-05-13 2016-11-16 Offshore Renewable Energy Catapult Power converter
CN106329979A (en) * 2016-10-08 2017-01-11 东南大学 MMC double circulation suppression method for high-speed permanent magnet motor system
CN106385214A (en) * 2016-09-29 2017-02-08 东南大学 High-speed permanent magnet synchronous motor control method based on modular multilevel converter
CN106451531A (en) * 2016-09-09 2017-02-22 湖南大学 Multi-phase and high-power generation-conversion integrated system and control method thereof

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN104811069A (en) * 2015-05-13 2015-07-29 山东大学 Prediction control method for modularized multi-level inverter
GB2538270A (en) * 2015-05-13 2016-11-16 Offshore Renewable Energy Catapult Power converter
CN106451531A (en) * 2016-09-09 2017-02-22 湖南大学 Multi-phase and high-power generation-conversion integrated system and control method thereof
CN106385214A (en) * 2016-09-29 2017-02-08 东南大学 High-speed permanent magnet synchronous motor control method based on modular multilevel converter
CN106329979A (en) * 2016-10-08 2017-01-11 东南大学 MMC double circulation suppression method for high-speed permanent magnet motor system

Also Published As

Publication number Publication date
CN107846164A (en) 2018-03-27

Similar Documents

Publication Publication Date Title
JP5457449B2 (en) Power converter
Tarisciotti et al. Modulated predictive control for indirect matrix converter
CN107846164B (en) Motor driving system based on MMC and discrete control method thereof
Wang et al. A novel SVPWM for three-level NPC inverter based on m-mode controllability
Hussein et al. Detailed Simulink implementation for induction motor control based on space vector pulse width modulation SVPWM
Can et al. A novel SSPWM controlling inverter running nonlinear device
Záskalický Mathematical model of a five-phase voltage-source PWM-controlled inverter
Lee et al. Improved sensorless vector control for induction motor drives fed by a matrix converter using nonlinear modeling and disturbance observer
CN107482940B (en) Modular multilevel converter for high-speed permanent magnet motor driving system
JP5800133B2 (en) Power conversion device and inverter device using the same
CN103944433B (en) A kind of three-phase tri-level inverter circuit and uninterrupted power source
Mohamed et al. Power quality of dual two-level inverter fed open end winding induction motor
Solanki et al. A modular multilevel converter based high-power high-current power supply
Ammar et al. A simple hybrid PWM algorithm for a five-phase indirect matrix converter topology
Sekhar et al. Novel multilevel inverter with minimum number of switches
WO2014141398A1 (en) Pwm control method and power conversion apparatus using same
Abbasi et al. A new topology of embedded Z-source inverter with low voltage stress on capacitors
Halabi et al. Integrated voltage Vector–Based SVPWM for reliability and performance enhancement of Five-Level HANPC inverters
Ammar et al. The original DSP Technique implemented on a five-phase indirect matrix converter 5P-IMC
JP3326790B2 (en) Control device for power converter
Mirazimi et al. Space vector PWM method for two-phase three-leg inverters
Darwish et al. Operation and control design of new Three-Phase inverters with reduced number of switches
JP2014007854A (en) Power conversion system
CN113783441A (en) Three-phase vienna rectifier carrier discontinuous pulse width modulation
Swamy et al. Speed control of space vector modulated inverter driven induction motor

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant